WO2015030547A1

WO2015030547A1 - Method and apparatus for receiving signal in wireless access system supporting fdr transmission

Info

Publication number: WO2015030547A1
Application number: PCT/KR2014/008135
Authority: WO
Inventors: 노광석; 정재훈; 김진민; 김기태; 최국헌
Original assignee: 엘지전자 주식회사
Priority date: 2013-08-31
Filing date: 2014-09-01
Publication date: 2015-03-05

Abstract

The present invention relates to a wireless access system supporting a full duplex radio (FDR) transmission environment. A method for receiving a signal by a terminal in a wireless access system according to an embodiment of the present invention comprises: calculating a first signal (αA) including a first partial signal (A) and first noise (N1) corresponding to a target signal among encoded reception signals (Q); calculating a second signal (βB') including a second partial signal (B') and second noise (N2) corresponding to a parity signal of the target signal among the encoded reception signals (Q); calculating a third signal (α'A) by decoding the first signal (αA) and the second signal (βB'); calculating a fourth signal (α'A') by decoding the third signal (α'A); calculating a fifth signal (β'B) by XORing the fourth signal (α'A') with the second signal (βB'); calculating the target signal using the third signal (α'A) and the fifth signal (β'B), wherein the second signal (βB') may be generated by XORing a signal (A') obtained by encoding the target signal and the parity signal (B) of the target signal.

Description

【Specification】

[Name of invention]

Method and device for receiving signal in wireless access system supporting FDR transmission

[ One ] . The present invention relates to a radio access system that supports a FDR (Ful l Duplex Radio) transmission environment, and a method for efficiently receiving a signal when applying the FDR, and an apparatus for supporting the same.

Background Art

[2] Wireless access systems are widely deployed to provide various kinds of communication services such as voice and data. In general, a wireless access system is a multiple iple access system capable of supporting communication with multiple users by sharing available system resources (bandwidth, transmission power, etc.). Examples of multiple access systems include code division mult iple access (CDMA) systems, frequency division mult iple access (FDMA) systems, time division mult iple access (TDMA) systems, orthogonal frequency division mult iple access (0FDMA) systems And single-carrier frequency division mult access (SC-FDMA) systems.

[Detailed Description of the Invention]

[Technical problem]

An object of the present invention is to provide a method for efficiently transmitting and receiving data in a wireless access system supporting FDR transmission.

Another object of the present invention is to provide an apparatus supporting these methods.

[5] The technical objects to be achieved in the present invention are not limited to the above-mentioned matters, and other technical problems not mentioned above are common in the art to which the present invention belongs from the embodiments of the present invention to be described below. It can be considered by those who have knowledge.

Technical Solution

In order to solve the above problem, according to an embodiment of the present invention, in a wireless communication system, a signal receiving method of receiving a signal by a terminal includes: a first partial signal that stands for a target signal among the encoded reception signals (Q); Calculating a first signal [alpha] A consisting of A) and a first noise N1; Parity of the target signal among the encoded received signals Calculating a second signal β [beta] 'composed of a second partial signal [beta'] and a second noise [N2] for the call; Calculating a third signal α'Α by decoding based on the first signal αΑ and the second signal ββ '; Calculating a fourth signal α'Α by encoding the third signal α′Α; Calculating a fifth signal β′Β by performing an X0R operation on the fourth signal α′Α ′ with the second signal ββ '; And calculating the target signal using the third signal α Ά and the fifth signal β ′ Β, wherein the second partial signal β is a signal obtained by encoding the target signal ( A ′) and the parity signal (β) of the target signal can be generated by X0R operation.

[7] A terminal for receiving a signal in a wireless communication system according to another embodiment of the present invention includes: a radio frequency (RF) unit; And a processor, wherein the processor is configured to calculate a first signal αA consisting of a first partial signal A and a first noise N1 that amplify the target signal among the encoded reception signals Q, and And calculating a second signal β [beta] 'constituted by a second partial signal [beta'] and a second noise [N2], which are applied to the parity signal of the target signal among the encoded received signals. A third signal α'Α is calculated by decoding on the basis of αα and the second signal ββ ', and the fourth signal α′Α is encoded by encoding the third signal α′Α. Calculates a fifth signal β′Β by calculating the fourth signal α′Α ′ with the second signal ββ 'and X0R, and calculates the third signal αα and 5th. The target signal is calculated using the signal β'β, and the second partial signal β is a signal A 'encoding the target signal and the target signal. Can be generated by X0R operation of the parity signal [beta] of the signal.

[8] The followings may be commonly applied to the above embodiments according to the present invention.

The encoded reception signal Q may be composed of the first signal αΑ, the second signal ββ ', a third partial signal C, and a third noise N3.

The third partial signal C may include a parity signal including information about the first partial signal Α.

The third partial signal C may include a parity signal including information about the second partial signal Β.

The bit length of the first signal αΑ may be the same as the bit length of the target signal. The bit length of the first signal αΑ may be determined as the length from the most significant bit (MSB) to the start point of the parity signal.

The bit length of the second signal ββ 'may be the same as the parity signal bit length.

The foregoing general description and the following detailed description of the invention are exemplary and intended for further explanation of the invention as described in the claims.

Advantageous Effects

According to the embodiments of the present invention, the following effects can be obtained.

First, data can be efficiently transmitted and received in a wireless access system supporting FDR transmission.

[18] Effects obtained in the embodiments of the present invention are not limited to the above-mentioned effects, and other effects not mentioned above are described in the following description of the embodiments of the present invention. It can be clearly derived and understood by those skilled in the art. In other words, unintended effects of practicing the present invention can also be derived by those skilled in the art from the embodiments of the present invention.

[Brief Description of Drawings]

FIG. 1 schematically illustrates an E-UMTS network structure as an example of a wireless communication system.

2 illustrates a structure of a control plane and a user plane of a radio interface protocol between a terminal and an E-UTRAN based on the 3GPP radio access network standard.

3 illustrates physical channels used in a 3GPP system and a general signal transmission method using the same.

4 illustrates a structure of a radio frame used in an LTE system.

5 illustrates a structure of a downlink radio frame used in an LTE system.

6 illustrates a structure of an uplink subframe used in an LTE system.

7 illustrates a configuration of a general multiple antenna (MIM0) communication system.

8 through 9 illustrate periodic reporting of channel state information.

[27] 10 is a diagram illustrating an example of an interference situation in an FDR scheme.

11 shows an example of interference signal cancellation in a situation in which the interference signal has a much larger power than the desired signal.

12 shows an example of a case where an interference signal has a smaller power than a desired signal.

13 shows an example of application of the three interference cancellation methods described above in a transmission / reception system.

14 shows an example of a baseband signal after the ADC according to the amount of magnetic interference remaining after using an analog og cancellation method.

15 illustrates a parameter for a baseband signal at a transmitter.

16 illustrates parameters for a baseband signal at a receiving end.

17 shows an example of a signal transmission and reception method in an FDR system.

18 shows a signal encoding method according to the present invention, in which the encoding step 1703 in FIG. 17 is specified.

19 illustrates a decoding step 1761 of FIG. 17 illustrating a signal decoding method according to the present invention.

20 illustrates a base station and a terminal that can be applied to an embodiment of the present invention.

[Form for implementation of invention]

The following embodiments combine the components and features of the present invention in a predetermined form. Each component or feature may be considered optional unless stated otherwise. Each component or feature may be embodied in a form that is not combined with other components or features. In addition, some components and / or features may be combined to form an embodiment of the present invention. The order of the operations described in the embodiments of the present invention may be changed. Some configurations or features of one embodiment may be included in another embodiment or may be substituted for components or features of another embodiment.

In the present specification, embodiments of the present invention will be described with reference to a relationship between data transmission and reception between a base station and a terminal. Here, the base station has a meaning as a terminal node of a network that directly communicates with a terminal. In this document The specific operation described as being performed by the base station may in some cases be performed by an upper node of the base station.

[41] that is, in a network which is made up of ⁱ number of network nodes including a base station (network nodes), various operations performed for communication with the terminal can be performed by the BS, or network nodes other than the base station Is self explanatory. A 'base station (BS)' may be replaced by terms such as a fixed station, a Node B, an eNode B (eNB), an access point (AP), and the like. The repeater may be replaced by terms such as relay node (RN) and relay station (RS). In addition, the term 'terminal' may be replaced with terms such as a user equipment (UE), a mobile station (MS), an MSSC mobile subscriber station (MS), and a subscriber station (SS).

Specific terms used in the following descriptions are provided to help the understanding of the present invention, and the use of the specific terms may be changed into other forms without departing from the technical spirit of the present invention.

In some cases, in order to avoid obscuring the concepts of the present invention, well-known structures and devices may be omitted or shown in block diagram form centering on the core functions of the structures and devices. In addition, the same components throughout the present specification will be described using the same reference numerals.

Embodiments of the present invention may be supported by standard documents disclosed in at least one of the wireless access systems IEEE 802 system, 3GPP system, 3GPP LTE and LTE—L (LTE-Advanced) system and 3GPP2 system . That is, steps or parts which are not described to clearly reveal the technical spirit of the present invention among the embodiments of the present invention may be supported by the above documents. In addition, all terms disclosed in this document can be described by the above standard document.

[0045] The following techniques include Code Division Multiple Access (CDMA), Frequency Division Multiple Access (FDMA), Time Division Multiple Access (TDMA), Orthogonal Frequency Division Multiple Access (0FDMA), and Single Carrier Frequency Division Multiple Access (SC-FDMA). It can be used in various wireless access systems. CDMA can be implemented with radio technologies such as UTRA Universal Terrestrial Radio Access) or CDMA2000. TDMA may be implemented in a wireless technology such as Global System for Mobile Communications (GSM) / General Packet Radio Service (GPRS) / Enhanced Data Rates for GSM Evolution (EDGE). (FDMA Wireless technology such as IEEE 802.11 (Wi-Fi), IEEE 802.16 (WiMAX), IEEE 802-20, Evolved UTRA (E-UTRA). UTRA is part of the UMTS Jniversal Mobile Telecomncat Mis System. 3rd Generation Generat Ion Partnership Project (3GPP) long term evolut ion (LTE) is part of E-UMTS (Evolved UMTS) using EHJTRA, employing 0FDMA in downlink and SC-FDMA in uplink. LTE-A (Advanced) is an evolution of 3GPP LTE. WiMAX can be described by the IEEE 802.16e standard (WirelessMAN-OFDMA Reference System) and the advanced IEEE 802.16m standard (WirelessMAN-OFDMA Advanced system). For clarity, the following description focuses on the 3GPP LTE and LTE-A standards, but the technical spirit of the present invention is not limited thereto.

A structure of a downlink radio frame will be described with reference to FIG. 1.

In a Cellular 0FDM wireless packet communication system, uplink / downlink data packet transmission is performed in subframe units, and one subframe is defined as a predetermined time interval including a plurality of 0FDM symbols. The 3GPP LTE standard supports a type 1 radio frame structure applicable to frequency division duplex (FDD) and a type 2 radio frame structure applicable to time division duplex (TDD).

[48] Figure 1 is a view showing a structure of a type 1 None ^"line frame. The downlink radio frame consists of 10 subframes, and one subframe consists of two slots in the time domain. The time it takes for one subframe to be transmitted is referred to as a TTKtransmission time interval). For example, one subframe may have a length of 1 ms, and one slot may have a length of 0.5 ms. One slot includes a plurality of 0FDM symbols in the time domain and includes a plurality of resource blocks (RBs) in the frequency domain. In the 3GPP LTE system, since 0FDMA is used in downlink, the 0FDM symbol represents one symbol period. The 0FDM symbol may also be referred to as an SC-FDMA symbol or symbol period. A resource block (RB) is a resource allocation unit and may include a plurality of consecutive subcarriers in one slot.

The number of 0FDM symbols included in one slot may vary depending on the configuration (conf igurat ion) of CP Cyclic Pref ix). CPs include extended CPs and normal CPC normal CPs. For example, if the 0FDM symbol is configured by a generic CP, The number of OFDM symbols included in my slot may be seven. When the OFDM symbol is configured by an extended CP, since the length of one OFDM symbol is increased, the number of OFDM symbols included in one slot is smaller than that of the normal CP. The number of OFDM symbols included in, for example, a ^', and my slots for the extended CP may be six days. If the channel state is unstable, such as when the terminal is moving at a high speed, an extended CP may be used to further reduce intersymbol interference.

When a normal CP is used, one slot includes 7 OFDM symbols, and thus, one subframe includes 14 OFDM symbols. In this case, the first two or three OFDM symbols of each subframe may be allocated to a physical downl ink control channel (PDCCH), and the remaining 0FDM symbols may be allocated to a physical downl ink shared channel (PDSCH).

The structure of the radio frame is merely an example, and the number of subframes included in the radio frame, the number of slots included in the subframe, and the number of symbols included in the slot may be changed in various ways.

FIG. 2 is an exemplary diagram illustrating an example of a resource grid for one downlink slot. This is the case where the 0FDM symbol is composed of a normal CP. Referring to FIG. 2, the downlink slot includes a plurality of 0FDM symbols in the time domain and includes a plurality of resource blocks in the frequency domain. Here, one downlink slot includes 70 FDM symbols, and one resource block includes 12 subcarriers as an example, but is not limited thereto. Each element on the resource grid is called a resource element (RE). For example, the resource element a (k, l) becomes a resource element located at the k th subcarrier and the first 0FDM symbol. In case of a normal CP, one resource block includes 12 X 7 resource elements (in the case of an extended CP, it includes 12 X 6 resource elements). Since the interval of each subcarrier is 15 kHz, one resource block includes about 180 kHz in the frequency domain. NDL is the number of resource blocks included in a downlink slot. The value of NDL may be determined according to a downlink transmission bandwidth set by scheduling of a base station.

3 shows a structure of a downlink subframe. A maximum of three 0FDM symbols in the front part of the first slot in one subframe corresponds to a control region to which a control channel is allocated. The remaining 0FDM symbols correspond to a data region to which a Physical Downlink Shared Channel (PDSCH) is allocated. The basic unit of transmission is one subframe. That is, PDCCH and PDSCH are allocated over two slots. Downlink control channels used in the 3GPP LTE system include, for example, a physical control format indicator channel (PCFICH) and a physical downlink ink control channel (PDCCH). There is a Q Q indicator channel (Physi cal Hybr id automat ic repeat request Indicator Channel; PHICH). The PCFICH is transmitted in the first OFDM symbol of a subframe and includes information on the number of OFDM symbols used for control channel transmission in the subframe. PHICH includes HARQ ACK / NACK signal as a male answer of uplink transmission. Control information transmitted through the PDCCH is called Downlink Control Information (DCI). DCI includes uplink or downlink scheduling information or an uplink transmit power control command for a certain terminal group. The PDCCH includes a resource allocation and transmission format of a downlink shared channel (DL-SCH), resource allocation information of an uplink shared channel (UL-SCH), paging information of a paging channel (PCH), system information on a DL-SCH, and a PDSCH. Resource allocation of upper layer control messages, such as random access response transmitted to the network, a set of transmit power control commands for individual terminals within a random and terminal group, transmit power control information, VoIP over IP (Voice over IP) Activation and the like. A plurality of PDCCHs may be transmitted in the control region. The UE may monitor the plurality of PDCCHs. The PDCCH is transmitted in a combination of one or more consecutive Control Channel Elements (CCEs). CCE is a logical allocation unit used to provide a PDCCH with a coding rate based on the state of a radio channel. CCE responds to multiple resource element groups. The format of the PDCCH and the number of available bits are determined according to the correlation between the number of CCEs and the coding rate provided by the CCEs. The base station determines the PDCCH format according to the DCI transmitted to the terminal, and adds a Cyclic Redundancy Check (CRC) to the control information. The CRC is masked with an identifier called Radio Network Temporary Ident if ier (RNTI), depending on the owner or purpose of the PDCCH. If the PDCCH is for a specific UE, the eel 卜 RNTKC-RNTI) identifier of the UE may be masked to the CRC. Alternatively, if the PDCCH is for a paging message, a paging indicator identifier (P-RNTI) may be masked to the CRC. If the PDCCH is for system information (more specifically, system information block (SIB)), the system information identifier and system information R TI (SI-RNTI) are CRC. Can be masked on. In order to indicate a random access response, which is a response to the transmission of the random access preamble of the UE, random access -RNTKRA-RNTI may be masked to the CRC.

4 illustrates a structure of an uplink subframe. The uplink subframe may be divided into a control region and a data region in the frequency domain. In the control region, a physical uplink control channel (PUCCH) including uplink control information is allocated. In the data area, a physical uplink shared channel (PUSCH) including user data is allocated. In order to maintain a single carrier characteristic, one UE does not simultaneously transmit a PUCCH and a PUSCH. PUCCH for one UE is allocated to an RB pair in a subframe. Resource blocks belonging to a resource block pair occupy different subcarriers for two slots. The resource block pair allocated to the PUCCH is said to be frequency-hopped at the slot boundary.

[55] Modeling of Multiple Antenna (MIM0) Systems

[56] The Multiple Input Multiple Output (MIM0) system is a system that improves the transmission and reception efficiency of data by using multiple transmission antennas and multiple reception antennas.MIM0 technology does not rely on a single antenna path to receive an entire message. The entire data can be received by combining multiple pieces of data received through multiple antennas.

[57] The MIM0 technology includes a spatial diversity technique and a spatial multiplexing technique. Spatial diversity scheme can increase the transmission reliability (reHability) or widen the cell radius through the diversity gain, and is suitable for data transmission for a mobile terminal moving at high speed. Spatial multiplexing can increase the data transmission without increasing the bandwidth of the system by simultaneously transmitting different data.

5 is a configuration diagram of a wireless communication system having multiple antennas. As shown in FIG. 5 (a), if the number of transmit antennas is increased to NT and the number of receive antennas is increased to NR, theoretical channel transmission is proportional to the number of antennas, unlike when the transmitter or receiver uses multiple antennas. increased ^capacities. Therefore, the transmission rate can be improved and the frequency efficiency can be significantly improved. As the channel transmission capacity increases, the transmission rate may theoretically increase as the rate of increase rate Ri multiplied by the maximum transmission rate Ro when using a single antenna. [59] [Equation 1]

[60] ^ = min (V _r , A ^)

For example, in the MIM0 communication system using four transmitting antennas and four receiving antennas, a theoretical transmission rate of four times that of a single antenna system can be obtained. Since the theoretical capacity increase of multi-antenna systems was proved in the mid-90s, various techniques to lead this to substantial data rate improvement have been actively studied to date. In addition, some technologies are already being reflected in various wireless communication standards such as 3G mobile communication and next generation WLAN.

[62] The current trends in multi-antenna research have been studied in terms of information theory related to the calculation of multi-antenna communication capacity in various channel and multi-access environments, wireless channel establishment and model derivation of multi-antenna systems. Research is being actively conducted from various viewpoints, such as research on space-time signal processing technology for improving data rate.

[63] The method of communication in a multi-antenna system is described in more detail using mathematical modeling. It is assumed that there are NT transmit antennas and NR receive antennas in the system.

[64] Referring to the transmission signal, when there are NT transmission antennas, the maximum information that can be transmitted is NT. The transmission information may be expressed as follows.

[65] [Equation 2] 1 ， ¾ ， ... ， ¾. 』

[67] Each transmission information "^ ' ^■ ^''''' Nr may have a different transmission power.If each transmission power is ， ^ ， ^' ， ^, the transmission information whose transmission power is adjusted is as follows. The same can be expressed.

[68] [3]

[69] ^s

In addition, S may be expressed as follows using a diagonal matrix i ³ of transmit power.

[71] [Equation 4]

[73] Consider a case where a weight matrix W is applied to an information vector S whose transmission power is adjusted so that NT transmission signals P '''''N _{r that} are actually transmitted are formed. The weight matrix W plays a role in properly distributing transmission information to each antenna according to a transmission channel situation. ， ^^ ， ^^^ can be expressed using vector X as

[74] [Equation 5]

Where, denotes a weight between the i th transmit antenna and the j th information. W is also called a precoding matrix.

On the other hand, the transmission signal X can be considered in other ways depending on the case of 2 Λ (for example, spatial diversity and spatial multiplexing). In the case of spatial multiplexing, the elements of the information vector (s) have different values since different signals are multiplexed and the multiplexed signal is transmitted to the receiving side. On the other hand, in the case of spatial diversity, the same signal is repeatedly transmitted through a plurality of channel paths so that the elements of the information vector (s) have the same value. Of course, a combination of spatial multiplexing and spatial diversity techniques can also be considered. That is, the same signal may be transmitted through, for example, three transmit antennas according to a spatial diversity scheme, and the remaining signals may be spatially multiplexed and transmitted to the receiver.

When there are NR reception antennas, the reception signals θ ^^^ and ^^ of each antenna may be expressed as vectors as follows.

[79] [Equation 6]

In the case of modeling a channel in a multi-antenna wireless communication system, channels may be classified according to transmit / receive antenna indexes. The channel passing through the receiving antenna i from the transmitting antenna j will be denoted by. Note that in the order of the index, the receiving antenna index is first, and the index of the transmitting antenna is later.

FIG. 5 (b) shows a channel from NT transmit antennas to receive antenna i. The channels may be bundled and displayed in the form of a vector and a matrix. In FIG. 5 (b), a channel arriving from a total of NT transmit antennas to a receive antenna i may be represented as follows.

[83] [Equation 7]

[84] = ί ΐ ， ¾2 ， · " ^* '¾Vr J

Accordingly, all channels arriving from NT transmit antennas to NR receive antennas may be expressed as follows.

The real channel is added with white noise (GN) after passing through the channel matrix H. The white noise "1," ² , ^"' ," ^ added to each of the NR receiving antennas may be expressed as follows.

[89] [Equation 9]

_[90] η = [« ₁ , η ₂ _,. ··, ¾ _ί ] ^Γ

Through the mathematical modeling described above, the received signal may be expressed as follows.

[92] [Equation 10]

The number of rows and columns of the channel matrix H indicating the channel state is determined by the number of transmit and receive antennas. The number of rows in the channel matrix H is equal to the number of receive antennas NR, and the number of columns is equal to the number NT of transmit antennas. That is, the channel matrix H is NRXNT matrix.

The rank of a matrix is defined as the minimum number of rows or columns that are independent of each other. Thus, the rank of the matrix cannot be greater than the number of rows or columns. The tank (ra «:( H)) of the channel matrix H is limited as follows.

[96] [Equation 11]

[97] rank H) ≤ min (N _T , N _R )

In the ΜΙΜΟ transmission, 'Rank' represents the number of paths that can independently transmit a signal, and 'Number of layers' represents the number of signal streams transmitted through each path. In general, since the transmitting end transmits a number of layers corresponding to the number of tanks used for signal transmission, unless otherwise specified, a tank has the same meaning as the number of layers.

[99] Reference Signal (RS)

When a packet is transmitted in a wireless communication system, a signal may be distorted during the transmission process because the transmitted packet is transmitted through a wireless channel. In order to directly receive the distorted signal from the receiver, distortion of the received signal must be corrected using the channel information. In order to find out the channel information, a method of transmitting the signal known to both the transmitting side and the receiving side, and finding the channel information with the distortion degree when the signal is received through the channel is mainly used. The signal is called a pilot signal or a reference signal.

In case of transmitting / receiving data using multiple antennas, it is necessary to know the channel condition between each transmitting antenna and the receiving antenna to receive the correct signal. Therefore, a separate reference signal must exist for each transmit antenna.

In a mobile communication system, RSs can be classified into two types according to their purpose. One is RS used for channel information acquisition and the other is RS used for data demodulation. Since the former is an RS for allowing the terminal to acquire downlink channel information, it should be transmitted over a wide band and should be able to receive and measure the corresponding RS even if the terminal does not receive downlink data in a specific subframe. Such RS is also used for measurement such as handover. The latter is an RS that is transmitted together with the corresponding resource when the base station transmits a downlink, and the terminal can estimate the channel by receiving the corresponding RS, and thus can demodulate the data. This RS should be transmitted in the area where data is transmitted.

In the existing 3GPP LTE (eg, 3GPP LTE Release-8) system, two types of downlink RSs are defined for unicast service. One of them is a common reference signal (Common RS; CRS), and the other is a dedicated reference signal (Dedi cated RS; DRS). The CRS is used for obtaining information on channel state, measuring for handover, and the like, and may be referred to as cell-specific (cel l-speci f i) RS. The DRS is used for data demodulation and may be referred to as UE-specific RS. In the existing 3GPP LTE system, DRS is used only for data demodulation, and CRS can be used for two purposes of channel information acquisition and data demodulation.

The CRS is a Sal-specific RS, and is transmitted every subframe for a wide bandwidth. The CRS may be transmitted for up to four antenna ports according to the number of transmit antennas of the base station. For example, if the number of transmit antennas of the base station is two, CRSs for antenna ports 0 and 1 are transmitted, and if four, CRSs for antenna ports 0-3 are transmitted.

6 shows the pattern of CRS and DRS on one resource block (12 subcarriers on 14 OFDM symbols X frequencies in time in case of a normal CP) in a system in which a base station supports four transmit antennas. Drawing. In FIG. 6, resource elements RE denoted by 'R0', 'R1', ^• R2 ', and' R3 'indicate positions of CRSs with respect to antenna port indexes 0, 1, 2, and 3, respectively. Meanwhile, the resource element denoted as 'D' in FIG. 6 indicates the position of the DRS defined in the LTE system.

Evolution of the LTE System In an advanced LTE-A system, up to eight transmit antennas can be supported in downlink. Therefore, RS for up to eight transmit antennas should also be supported. Since the downlink RS in the LTE system is defined only for up to four antenna ports, if the base station has four or more up to eight downlink transmit antennas in the LTE-A system, the RS for these antenna ports is additionally added. Should be defined as As RS for up to eight transmit antenna ports, both RS for channel measurement and RS for data demodulation shall be considered.

One of the important considerations in designing LTE-A system is backward compatibility. Backward compatibility means that the existing LTE terminal supports to operate properly even in LTE-A system. From the point of view of RS transmission, RS overhead is excessive when CRS defined in the LTE standard adds RS for up to eight transmit antenna ports in the time-frequency domain transmitted in every subframe over the entire band. It becomes bigger. Therefore, in designing RS for up to 8 antenna ports, consideration should be given to reducing RS overhead.

In the LTE-A system, new RSs can be broadly classified into two types. One of them is RS, the channel state information-reference signal (RS) for channel measurement purposes for the selection of transmission tanks, Modulation and Coding Schemes (MCS), Precoding Matrix Index (PMI), etc. Channel State Informat ion RS (CSI? RS) and the other is a demodulation-reference signal (DM RS), which is an RS for demodulating data transmitted through up to eight transmit antennas.

[109] CSI-RS for channel measurement purposes is designed for channel measurement-oriented purposes, whereas CRS in the existing LTE system is used for data demodulation at the same time as channel measurement, handover, etc. There is a characteristic. Of course, CSI-RS can also be used for the purpose of measuring the handover. Since the CSI-RS is transmitted only for the purpose of obtaining information about the channel state, unlike the CRS in the existing LTE system, the CSI-RS does not need to be transmitted every subframe. Therefore, to reduce the overhead of the CSI-RS, the CSI-RS may be designed to be transmitted intermittently (eg, periodically) on the time axis.

If data is transmitted on a downlink subframe, a dedicated DM RS is transmitted to a terminal scheduled for data transmission. The DM RS dedicated to a specific terminal may be designed to be transmitted only in a resource region in which the terminal is scheduled, that is, in a time-frequency region in which data for the terminal is transmitted.

FIG. 7 is a diagram illustrating an example of a DM RS pattern defined in an LTE-A system. In FIG. 7, a position of a resource element for transmitting a DM RS on one resource block in which downlink data is transmitted (12 subcarriers over 14 0FDM symbol X frequencies in time in the case of a general CP) is illustrated. DM RS is additionally defined in LTE-A system. 4 antenna ports (antenna port indexes 7, 8, 9 and 10) can be transmitted. DM RSs for different antenna ports can be distinguished by being located in different frequency resources (subcarriers) and / or different time resources (OFDM symbols) (ie they can be multiplexed in FDM and / or TDM schemes). In addition, DM RSs for different antenna ports located on the same time-frequency resource may be distinguished from each other by orthogonal codes (ie, may be multiplexed by the CDM scheme). In the example of FIG. 7, DM RSs for antenna ports 7 and 8 may be located in resource elements (REs) indicated as DM RS CDM group 1, which may be multiplexed by an orthogonal code. Likewise, DM RSs for antenna ports 9 and 10 may be located in resource elements indicated as DM RS group 2 in the example of FIG. 7, and they may be multiplexed by orthogonal codes.

8 is a diagram illustrating examples of a CSI-RS pattern defined in an LTE-A system. FIG. 8 shows the location of a resource element in which a CSI-RS is transmitted on one resource block in which downlink data is transmitted (12 subcarriers on 14 0FDM symbol X frequencies in time in case of a general CP). In any downlink subframe, one of the CSI-RS patterns of FIGS. 8 (a) to 8 (e) may be used. The CSI-RS may be transmitted for eight antenna ports (antenna port indexes 15, 16, 17, 18, 19, 20, 21, and 22) which are additionally defined in the LTE-A system. CSI-RSs for different antenna ports may be distinguished by being located in different frequency resources (subcarriers) and / or different time resources (0 FDM symbols) (ie, may be multiplexed in FDM and / or TDM schemes). . In addition, CSI-RSs for different antenna ports located on the same time-frequency resource may be distinguished from each other by orthogonal codes (i.e., may be multiplexed by the CDM scheme). In the example of FIG. 8 (a), CSI-RSs for antenna ports 15 and 16 may be located in resource elements (REs) indicated as CSI-RS CDM group 1 and they may be multiplexed by an orthogonal code. In the example of FIG. 8A, CSI-RSs for antenna ports 17 and 18 may be located in resource elements indicated as CSI-RS CDM group 2, which may be multiplexed by an orthogonal code. In the example of FIG. 8 (a), CSI-RSs for antenna ports 19 and 20 may be located in resource elements indicated as CSI-RS CDM group 3, which may be multiplexed by an orthogonal code. Resource elements indicated as CSI-RS CDM group 4 in the example of FIG. 8 (a) include antenna ports 21 and 22. The CSI-RSs for may be located and they may be multiplexed by orthogonal codes. The same principle described with reference to FIG. 8 (a) may be applied to FIGS. 8 (b) to 8 (e).

FIG. 9 is a diagram illustrating an example of a zero power (ZP) CSI-RS pattern defined in an LTE-A system. There are two main uses of ZP CSI-RS. Firstly, it is used to improve CSI-RS performance. That is, one network mutes the CSI-RS RE of the other network to improve the CSI-RS measurement performance of the other network and mute the UE to perform rate mating correctly. Set RE can be informed by setting ZP CSI-RS. Secondly, it is used as an interference measurement for CoMP CQI calculation. That is, some networks perform muting on the ZP CRS-RS RE, and the UE can calculate CoMP CQI by measuring interference from the ZP CSI-RS.

6 to 9 are merely exemplary and are not limited to a specific RS pattern in applying various embodiments of the present invention. That is, even when RS patterns different from those of FIGS. 6 to 9 are defined and used, various embodiments of the present invention may be equally applied.

[115] FDR Transmission (Ful l Du lex Radio Transmission)

The FDR refers to a transmitting end receiver technology that enables a base station and / or a terminal to transmit an uplink / downlink by frequency / time and the like without duplexing.

FIG. 10 is a diagram illustrating an example of an interference situation in an FDR scheme. FIG.

Referring to FIG. 10, UE 1 and UE 2 perform communication on an uplink / downlink using the same frequency / time resource. Accordingly, each terminal may receive a signal transmitted from another base station or terminal while transmitting. That is, as shown in the dotted line of FIG. 10, a communication environment in which its own transmission signal directly causes magnetic interference to its reception modules (or receivers) is formed.

In consideration of the multi-cell deployment environment in the system, the new interference or the increased ^' interference expected by the introduction of the FDR is summarized as follows.

[120] (1) int ra devi ce sel f-inter interference

[121] (2) UE to UE inter-l ink inter ference

[122] (3) BS to BS inter-l ink interference

Magnetic interference means that its own transmission signal causes interference directly to its receiver as shown in FIG. In general, a self f interference signal It is received stronger than the desired signal that it wants to receive. Therefore, it is important to completely eliminate the interference cancellation work.

Secondly, multi-user interference refers to interference occurring between terminals. For example, it means that a signal transmitted by a terminal is received by an adjacent terminal and acts as interference. In the conventional communication system, since half-duplex (e.g., FDD, TDD) for separating uplink / downlink by frequency or time is implemented, no interference occurs between uplink and downlink. However, in the FDR transmission environment, since uplink and downlink share the same frequency / time resource, interference occurs between the base station transmitting data and neighboring terminals as shown in FIG. 10.

Finally, inter-cell interference means interference occurring between base stations. For example, in a heterogeneous base station, it means that a signal transmitted by one base station is received by a receiving antenna of another base station and acts as interference. This means the same communication situation as that of multi-user interference, and means that interference occurs due to uplink resource sharing between base stations. In other words, FDR can increase the frequency efficiency by sharing the same time / frequency resources on the uplink and downlink, but the increase in interference may cause a limitation in improving the frequency efficiency.

[126] Among these three interferences, (1) magnetic interference is the first problem to be solved in order to operate FDR due to the influence of interference occurring only in FDR. 10 shows an example of FDR in a magnetic interference situation. That is, a signal transmitted from one terminal is received as it is by the receiving antenna of the same terminal to act as interference.

[127] This interference is unique unlike other interferences.

[128] The first is that a signal acting as an interference is a hardware implementation and can be regarded as a signal perfectly known by wire. However, due to the non-linearity of the RF element, the change of the channel between the transmitting and receiving antennas of the interference signal, the signal received from the antenna and the signal received by wire are almost the same, but not equal to 100¾>. Therefore, even if the signal acting as interference is perfectly known, the receiver cannot completely eliminate the interference.

[129] Secondly, the power of the interfering signal is significantly higher than the desired signal. The receiver uses an analog to digital converter (ADC) to convert the received signal into a digital signal. Typically, the ADC measures the power of the received signal The power level of the received signal is adjusted, quantized, and converted into a digital signal. However, if the interference signal is received at a much higher power than the desired signal, the signal characteristic of the desired signal is buried at the quantization level at the time of quantization, and thus it cannot be restored. 11 illustrates that when quantization is performed in a situation in which an interference signal has a much larger power than a desired signal, even if the interference signal is removed, the desired signal is very distorted. 12 illustrates an example in which an interference signal has a smaller power than a desired signal, and shows that a desired signal is recovered after removing the interference signal.

11 and 12, the better the magnetic interference cancellation, the better the reception of the desired signal.

[131] Self-interference cancellation can be divided into three methods: antenna, analog and digital removal.

13 shows an example of applying the three interference cancellation methods described above in a transmission / reception system.

[133] First, the antenna removal method is a simple passive method of antenna position setting with respect to the wavelength length.

The analog cancellation method is an active method of removing interference from a receiver by using an additional radio frequency (RF) chain.

The digital rejection method is also an active method and removes interference from the baseband signal passing through the ADC. At this time, since the transmitting / receiving stage where self-interference occurs is the same, a method of subtracting a known transmission signal from the signal passing through the ADC is used.

The antenna removal method may largely belong to an analog removal method. FIG. 11 shows a form in which interference is less removed than in FIG. 12 in terms of analog signals.

As shown in FIGS. 11 and 12, since the digital removal method handles the baseband signal through the ADC, the digital removal method can be applied only when a certain level of interference cancellation is performed in the analog terminal.

The present invention relates to a signal reception method applied after all interference is removed by a digital cancellation method, and more particularly, to a signal transmission and reception method resistant to quantization error and channel noise for a baseband signal. 14 shows an example of a baseband signal after the ADC according to the amount of magnetic interference remaining after the use of the analog ( _ana ₀ g) cancellation method. Specifically, FIG. 14 illustrates a baseband signal after the transmission device 1 receives the signals transmitted from the transmission device 1 and the transmission device 2, and performs analog end interference cancellation and ADC.

In FIG. 14 (a), since the interference is not removed in the analog stage, the transmission signals of the transmitter 1 and the transmitter 2 are superimposed on the lower 3 bits.

In FIG. 14 (b), the lower 8 bits are overlapped due to a lot of interference cancellation.

In FIG. 14, a baseband signal represents most significant bits (MSB), and the MSB represents a sign bit.

[143] Signal Transmission / Reception Method According to the Present Invention in FDR

Methods for efficiently transmitting and receiving signals in an FDR system have been proposed. For example, an improved digital removal method using channel estimation using FIR filters has been proposed. However, channel estimation through the FIR filter requires a more reliable channel estimation method because there may be errors.

According to the present invention, in order to use a channel estimation method using a pilot, each transmitter transmits a pilot, and through the channel estimation, a recovery performance of a desired signal can be improved in the digital terminal.

In addition, the present invention is not about a method for removing interference by using a known signal known in the digital stage, but after removing the interference, a desired signal is obtained. To make it more resistant to errors. That is, it is a main object of the present invention to design a desired signal resistant to quantization error and channel noise.

In the present invention, after performing an ADC using a known signal and performing a digital cancellation method for removing self-interference, the present invention is resistant to quantization error and channel noise of a baseband signal. We propose a method of designing a desired signal.

First, FIG. 15 illustrates a parameter for a baseband signal at a transmitter.

Q 'denotes a quantization bit length Ns denotes a signal bit length to be protected, and Np denotes a bit length in which signals overlap each other. Also, Pts sets the starting point of the bit you want to protect. Indicates. A, B, (: represents the bit values corresponding to Ns, Ns + Np, and Q 'from the MSB, respectively.

16 illustrates parameters for a baseband signal at a receiving end.

Q denotes a quantization bit length, Nd denotes a length of a quantized desired signal included in a baseband, Ns denotes a bit length to be protected among desired signals, and Np denotes a bit length of overlapping signals among desired signals. Ns and Np have the same value at the transmitting and receiving end. Pts denotes the starting point of the bit to be protected, and Ptp denotes the starting point of the overlapping signal. That is, Pts represents the starting point of a desired signal at the receiving end. W, X, Y, and Z represent bit values corresponding to where they are located in FIG. 16, respectively.

The present invention is a technique in which a part of a desired signal is encoded at a transmitting end and transmitted with a parity superimposed on a part of the remaining desired signal, and the receiving end may use a parity to improve a recovery performance of a desired signal. In particular, according to the present invention, it is possible to improve the recovery performance of the portion close to the MSB, which is the most important portion of the desired signal.

Referring to FIG. 17, the transmitter performs encoding on the prepared transmission signal 1701 (1703). A digital-to-analog convert (DAC) is performed on the encoded signal (1705), and the baseband signal is converted into an RF signal (1707). The generated RF analog signal 1709 is then transmitted via an antenna (1711).

When the receiver receives the signal transmitted from the transmitter (1751), it removes the analog interference (1753). Thereafter, the RF signal is converted into a baseband signal (1755) and the ADC is performed (1757). Next, after the digital interference is removed (1759), decoding and signal processing for the desired signal is performed (Γ761 ᅳ 1763).

Since self-interference occurs in all receivers of the FDR system as shown in FIG. 10, for convenience of description, the signal is transmitted from the receiver of the transmitter 1 as shown in FIG. Assume a situation that results in a desired signal. Although the following embodiments are described based on the above-described assumptions, the method according to the present invention can be applied to all receivers in which self-interference occurs.

18 shows a signal encoding method according to the present invention, in which the encoding step 1703 in FIG. 17 is specified. First, the length of A to be protected (i.e., Ns) for the transmission signal A (1801) is determined (1803). As an example of how to determine Ns, feedback, etc. can be used to find the optimal Ns.

In addition, encoding is performed on A to generate parity A '(length Np) (1805). At this time, Np (≤ Ns) is determined according to the coding rate, and the coding method may use channel coding, simple repetition, or the like. For example, when A '= A (Np = Ns), encoding that simply repeats a part of A can be used. The signal transmission method according to the present invention is not limited to a specific encoding method.

Next, B 'is generated through X0R operations of A' and B (1807) and replaced with a B 'value at the B position (1809). Therefore, no additional transmission resource due to parity transmission is required as in the following equation.

[161] [Equation 12]

[162] B '= A' + B

Meanwhile, a pilot to be used for estimating a channel at the receiver is inserted into an RB (Resource Block). When using a pilot, the channel environment is similar for a certain period, so that transmission data of the transmitter can be estimated. Since the present invention assumes baseband in a channel estimation state, the present invention is not limited to a specific pilot setting method.

In the present invention, since C has a high probability of disappearing or being inaccurate due to self-interference and quantization level, a technique for improving the reconstruction performance of A and B values is proposed.

19 illustrates a signal decoding method according to the present invention, in which the decoding step 1701 in FIG. 17 is specified.

[166] First, W ', X', Y ', and Z' are generated by removing known self-interference signals A, B, and C for the transmission device 1 through digital removal from the received signal. (1901).

Next, the pilot estimates a channel between the transmission device 1 and the transmission device 2, and thus the signal transmitted from the transmission device 2 can be known (1903). At this time, since the magnitude of the received desired signal is known, the starting position Pts of the desired signal is determined. X ', Y', and Z 'can be represented by the following equation.

[168] [Equation 13]

[169] X ， = Α + Ν1≡αΑ [170] [Equation 14]

[171] Υ '= Β' + Ν2≡βΒ '

[172] [Equation 15]

[173] Z '= C + N3

In this case, error information due to quantization interval and channel noise, analog and digital removal method error, etc. are represented by N1, N2, and N3. The error information becomes smaller as Pts gets closer to the MSB. α and β represent the accuracy for each signal A and Β and have a value of 0 ≦ a 3 ≦ l. If _α and β are 1, it represents a signal in which no error occurs.

Considering Equation 12, B 'of Equation 13 may be regarded as a signal in which noise B is added to A' at the receiving end. Therefore, A can be restored using the received signal A of Equation 13 and parity A 'of Equation 12. The restoration process can be performed as follows.

First, decoding is performed using ββ 'and αΑ. A 'A is restored due to parity. (α '> α). Encoding is performed again on the reconstructed a 'A. This produces a 'A'. Then, a 'A' is performed with Equation 14 and X0R. Since X0R is performed using a 'A closer to A than aA, β' β can be obtained (β '> β). . Next, use C = Z '. On the other hand, if the position of Ptp is greater than Q, the receiving end does not perform the decoding process and immediately uses aA.

Meanwhile, the transmission method of C according to the present invention will be described below.

C of FIG. 15 is less important than A and B, and may not be received due to self-interference and quantization level. Although C = Z 'was used in the above-described signal reception process, the transmission method for the data C can be performed as follows.

First, C may be used to transmit information about A. Specifically, C is replaced with a parity including information about A such as A, A ', A + B, and transmitted, and then the receiving terminal may utilize the parity to increase reconstruction performance for A.

[180] Next, C may be used to transmit information about B. Specifically, C is replaced with parity including information about B and B + A and B, and then transmitted, and then the receiving terminal may utilize the parity to increase the recovery performance of B. If for b In the case where B ″ is generated by performing encryption and transmitted by replacing C, the receiver may perform decoding by using β ′ Β and Β ″.

When a relay is included in the wireless communication system, communication is performed between the base station and the relay in the backhaul link, and communication is performed between the relay and the terminal in the access link. Therefore, the base station or the terminal illustrated in the figure may be replaced with a relay according to the situation.

Referring to FIG. 20, a wireless communication system includes a base station 2010 and a terminal 2020. The base station 2010 includes a processor 2013, a memory 2014, and a radio frequency (RF) unit (2011, 2012). The processor 2013 may be configured to implement the procedures and / or methods proposed in the present invention. The memory 2014 is connected with the processor 2013 and stores various information related to the operation of the processor 2013. The RF unit 2016 is connected with the processor 2013 and sends and / or receives radio signals. The terminal 2020 includes a processor 2023, a memory 2024, and an RF unit 2021, 1422. The processor 2023 may be configured to implement the procedures and / or methods proposed in the present invention. The memory 2024 is connected to the processor 2023 and stores various information related to the operation of the processor 2023. The RF unit 2021, 2022 is connected to the processor 2023 and transmits and / or receives a radio signal. The base station 2010 and / or the terminal 2020 may have a single antenna or multiple antennas.

The embodiments described above are the components and features of the present invention are combined in a predetermined form. Each component or feature is to be considered optional unless stated otherwise. Each component or feature may be embodied in a form that is not combined with other components or features. In addition, it is also possible to construct an embodiment of the present invention by combining some components and / or features. The order of the operations described in the embodiments of the present invention may be changed. Some components or features of one embodiment may be included in another embodiment, or may be replaced with other components or features of another embodiment. It is obvious that the claims may be combined with claims that do not have an explicit citation in the claims, or may be incorporated into new claims by amendment after filing. Depending on the particular case described in this document as being performed by the base station, it may be performed by its upper node. That is It is apparent that various operations performed for communication with a terminal in a network composed of a plurality of network nodes including a station may be performed by a base station or other network nodes other than the base station. The base station may be replaced by terms such as fixed station, Node B, eNodeB (eNB), access point, and the like.

An embodiment according to the present invention may be implemented by various means, for example, hardware, firmware, software, or a combination thereof. In the case of a hardware implementation, an embodiment of the present invention may include one or more ASICs (application integrated speci fic integrated circuits), DSPs (digi tal signal processors), DSPDs (digi tal signal processing devices), and PLDs (programmable logic). devices), FPGAs (ield programmable gate arrays), processors, controllers, microcontrollers, microprocessors, and the like.

In the case of implementation by firmware or software, an embodiment of the present invention may be implemented in the form of modules, procedures, functions, etc. that perform the functions or operation stones described above. The software code may be stored in a memory unit and be rounded up by the processor.

The memory unit may be located inside or outside the processor to exchange data with the processor by various known means.

Detailed descriptions of the preferred embodiments of the present invention as described above are provided to enable those skilled in the art to implement and practice the present invention. Although the above has been described with reference to preferred embodiments of the present invention, those skilled in the art will understand that the present invention can be variously modified and changed without departing from the scope of the present invention. For example, those skilled in the art can use each of the configurations described in the above-described embodiments in combination with each other. Thus, the present invention is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

The present invention can be embodied in other specific forms without departing from the spirit and essential features of the invention. Accordingly, the above detailed description should not be construed as limiting in all respects and should be considered as illustrative. The scope of the invention should be determined by reasonable interpretation of the appended claims, and all changes within the equivalent scope of the invention are included in the scope of the invention. The invention is presented here It is not intended to be limited to the embodiments, but is to be accorded the widest scope consistent with the principles and novel features disclosed herein. In addition, the claims may be combined to form an embodiment by combining claims that are not expressly cited in the claims or may be incorporated as new claims by amendment after filing.

[190] [Industrial Applicability]

The present invention can be used in a wireless communication device such as a terminal, a relay, and a base station.

Claims

【Scope of Claim】

【Claim 1】

In a signal reception method in which a terminal receives a signal in a wireless communication system, a first signal ( Calculating αΑ);

calculating a second signal (βΒ') consisting of a second partial signal (Β') corresponding to a parity signal of the target signal among the encoded received signals and a second noise (Ν2);

Calculating a third signal (α'A) by decoding the first signal (αΑ) and the second signal (βΒ') based on the first signal (αΑ) and the second signal (βΒ');

encoding the third signal (α'Α) to calculate a fourth signal (α'Α'); Calculating a fifth signal (β'Β) by performing an XOR operation on the fourth signal (α'Α') and the second signal (βΒ'); and

Calculating the target signal using the third signal (α'Α) and the fifth signal (β'Β)

Including,

The second partial signal (Β') is generated by performing an XOR operation on a signal (Α') encoding the target signal and a parity signal (Β) of the target signal.

【Claim 2】

According to clause 1,

The encoded received signal (Q) is composed of the first signal (αΑ), the second signal (βΒ'), a third partial signal (C), and a third noise (Ν3).

【Claim 3】

According to clause 2,

The third partial signal (C) includes a parity signal including information about the first partial signal (Α).

【Claim 4】

According to clause 2,

The third partial signal (C) includes a parity signal including information about the second partial signal (Β).

【Claim 5】 According to clause 1,

A method of receiving a signal wherein the bit length of the first signal (αΑ) is the same as the bit length of the target signal.

【Claim 6】

According to clause 1,

A signal reception method in which the bit length of the first signal (αΑ) is determined by the length from the most significant bit (MSB) to the starting point of the parity signal.

【Claim 7】

According to clause 1,

The bit length of the second signal (βΒ') is the same as the bit length of the parity signal.

【Claim 8】

In a terminal that receives a signal in a wireless communication system,

RF (Radio Frequency) unit; and

Includes a processor,

The processor,

Calculating a first signal (αΑ) consisting of a first partial signal (A) and first noise (N1) corresponding to the target signal among the encoded received signals (Q),

Among the encoded received signals, a second signal (Β') consisting of a second partial signal (Β') and a second noise (Ν2) corresponding to the parity signal of the target signal is calculated, and the first signal (αΑ) is calculated. ) and decoding based on the second signal (βΒ') to calculate the third signal (α'Α),

The third signal (α'Α) is encoded to calculate a fourth signal (α'Α'), and the fourth signal (α'Α') is XOR-operated with the second signal (βΒ') to produce a fifth signal. yields the signal (β'Β),

It is configured to calculate the target signal using the third signal (α'Α) and the fifth signal (β'Β),

【Claim 9】

According to clause 8, The encoded received signal (Q) consists of the first signal (αΑ), the second signal (βΒ'), a third partial signal (C), and a third noise (Ν3).

[Claim 10]

In clause 9,

【Claim 11】

In clause 9,

【Claim 12】

In clause 8,

The bit length of the first signal (αΑ) is the same as the bit length of the target signal.

【Claim 13】

According to clause 8,

The bit length of the first signal (αΑ) is determined by the length from the most significant bit (MSB) to the starting point of the parity signal.

[Claim 14]

According to clause 8,