WO2010061652A1

WO2010061652A1 - Pfc converter

Info

Publication number: WO2010061652A1
Application number: PCT/JP2009/059749
Authority: WO
Inventors: 鵜野良之
Original assignee: 株式会社村田製作所
Priority date: 2008-11-25
Filing date: 2009-05-28
Publication date: 2010-06-03
Also published as: US8228696B2; CN102187560B; CN102187560A; US20110211377A1; JP5141774B2; JPWO2010061652A1

Abstract

Provided is a PFC converter wherein a current flowing through an inductor can be detected at high speed and with high accuracy to perform a proper harmonic and power factor improvement, and the accurate detection of an operation state. A first current value (ILav1) is obtained by taking a sample at a central timing (ts1) of ON period of time (Ton) of a switching element and a second current value (ILav2) is obtained by taking a sample at a central timing (ts2) of OFF period of time (Toff) of the switching element. For example, if ILav1 = ILav2, it is determined to be a current continuous mode, and if ILav1 ≠ ILav2, it is determined to be a current discontinuous mode.

Description

PFC converter

The present invention relates to an AC-DC converter that inputs an AC power supply and outputs a DC voltage, and more particularly to a PFC converter that improves the power factor.

In Japan, Europe, etc., harmonic current regulations are classified according to application and input power. In order to deal with these problems, a power supply for general household electrical appliances that meet the regulations has been devised to suppress harmonic currents by adding a circuit called a PFC (power factor correction circuit) converter.

A general switching power supply device that uses a commercial AC power supply as an input power supply rectifies and smoothes the commercial AC power supply and converts it to a DC voltage, which is then switched by a DC-DC converter. Is greatly distorted. This is the cause of the harmonic current.

Therefore, for the purpose of suppressing this harmonic current, a PFC converter is provided after the full-wave rectifier circuit and before the smoothing circuit by the smoothing capacitor.

This PFC converter is composed of a chopper circuit, and operates so that the input current waveform is similar to the input voltage waveform, that is, in the form of a sine wave having the same phase. Therefore, the harmonic current is suppressed to a certain level or less.

Here, a configuration example of the PFC converter disclosed in Patent Document 1 will be described with reference to FIG.
In the power factor correction circuit shown in FIG. 1, a series circuit of an inductor L1, a switching element Q1 that is a MOSFET, and a current detection resistor R is provided at both ends of the diode bridge B1 that rectifies the AC power supply voltage of the AC input power supply Vac. It is connected. A series circuit of a diode D1 and a smoothing capacitor C1 is connected to both ends of the switching element Q1, and a load RL is connected to both ends of the smoothing capacitor C1. The switching element Q1 is turned on / off by PWM control of the control circuit 10. The current detection resistor R detects an input current flowing through the diode bridge B1.

The control circuit 10 includes an error amplifier 111, a multiplier 112, an error amplifier 113, a voltage controlled oscillator (VCO) 115, and a PWM comparator 116.

The error amplifier 111 obtains an error between the voltage of the smoothing capacitor C1 and the reference voltage E1. The multiplier 112 multiplies the error voltage signal and the rectified voltage by the diode bridge B1. The error amplifier 113 generates an error between the multiplication result of the multiplier 112 and the current signal flowing through the diode bridge B1 and outputs the error to the PWM comparator 116.

The VCO 115 generates a triangular wave signal having a frequency corresponding to the voltage value after rectification of the AC power supply voltage.

In the PWM comparator 116, the triangular wave signal from the VCO 115 is input to the-terminal, and the signal from the error amplifier 113 is input to the + terminal. That is, the PWM comparator 116 applies a duty pulse corresponding to the current flowing through the diode bridge B1 and the output voltage to the switching element Q1. The duty pulse is a pulse width control signal that continuously compensates for fluctuations in the AC power supply voltage and the DC load voltage at a constant period.

With such a configuration, the AC power supply current waveform is controlled to be similar to and in phase with the AC power supply voltage waveform, and the harmonics and the power factor are improved.

On the other hand, Patent Document 2 is disclosed as a digitally controlled PFC converter.
Also in the case of digital control, the current flowing through the inductor is detected, and the switching element is switched by PWM control according to the current value.

JP 2004-282958 A Japanese Patent Laid-Open No. 7-177746

By the way, in order to appropriately suppress the harmonics and improve the power factor, which are the purposes of the PFC converter, it is necessary to detect the current flowing through the inductor at high speed and with high accuracy. Further, it is necessary to detect the current flowing through the inductor at high speed and with high accuracy even when the operation state of the PFC converter is detected and processing corresponding to the operation state is performed.

In a conventional PFC converter that performs switching control using an analog circuit like the PFC converter of Patent Document 1, the current flowing through the inductor cannot always be detected at high speed. Further, in the case of performing digital control like the PFC converter of Patent Document 2, a large amount of calculation processing is originally required, and the response speed and accuracy are in a trade-off relationship. For this reason, there is a limit to improving the responsiveness while maintaining accuracy.

SUMMARY OF THE INVENTION An object of the present invention is to provide a PFC converter capable of detecting current flowing through an inductor at high speed and with high accuracy so that proper harmonics and power factor can be improved and an accurate operation state can be detected. It is in.

In order to solve the above problems, the present invention is configured as follows.
(1) A rectifying circuit for rectifying an AC voltage input from an AC input power supply, a series circuit including an inductor and a switching element connected to the next stage of the rectifying circuit, and a rectifying / smoothing connected in parallel to the switching element A PFC converter comprising: a circuit; and switching control means for controlling on / off of the switching element so that an input current input from the AC input power source is similar to the AC voltage,
A current detection circuit for detecting a current flowing through the switching element or the inductor during an on period of the switching element;
First current detection means for sampling a detection signal of a current flowing through the switching element or the inductor at the center of the ON period of the switching element and detecting it as a first current value;
Second current detection means for sampling a detection signal of a current flowing through the inductor at the center of the off period of the switching element and detecting it as a second current value;
Means for comparing the first current value and the second current value to detect a current increase / decrease state;
Is provided.

The first current value is an average value of currents flowing through the switching element and the inductor during the ON period of the switching element. The second current value is an average value of the current flowing through the inductor during the OFF period of the switching element. Therefore, the increase / decrease state of the current flowing through the inductor can be detected substantially by this two-point sampling, and control corresponding to the increase / decrease state can be performed at high speed.

(2) The current increase / decrease state detection means considers the current continuous mode when the first current value and the second current value are equal, and when the second current value is smaller than the first current value. Considered as a discontinuous current mode.

With this configuration, it is possible to determine the current continuous mode and the current discontinuous mode at high speed with a very small amount of calculation processing, and to perform control according to the mode at high speed.

(3) The current increase / decrease state detection unit determines a steady state and a transient state based on a change between the first current values or a change between the second current values at different periods.

With this configuration, the steady state and the transient state can be determined at a high speed with a very small amount of calculation processing, and the control according to the state can be performed at a high speed.

According to the present invention, an increase / decrease state of the current flowing through the inductor can be detected based on the first current value and the second current value, and control corresponding to the increase / decrease state can be performed at high speed.

Further, by determining the current continuous mode and the current discontinuous mode based on the first current value and the second current value, the current continuous mode and the current discontinuous mode can be performed with a very small amount of calculation processing. Can be determined at high speed, and control according to the mode can be performed at high speed.

In addition, by determining the steady state and the transient state based on the first current value and the second current value, the determination between the steady state and the transient state can be performed at a high speed with a very small amount of calculation processing. It is possible to perform control according to the mode at high speed.

2 is a circuit diagram of a PFC converter disclosed in Patent Document 1. FIG. 1 is a circuit diagram of a PFC converter according to an embodiment of the present invention. FIG. 3 is a diagram showing various control methods of the PFC converter 101 by the digital signal processing circuit 13. FIG. It is a wave form diagram of the voltage and current of the PFC converter 101 in the unit of a switching cycle in the state in which control is performed in the current continuous mode. It is a figure which shows about the method of calculating | requiring the average value of the electric current which flows into the inductor L1, in order to perform average current control in electric current continuous mode. 6A is a waveform diagram of the inductor current in the continuous current mode, and FIG. 6B is a waveform diagram of the inductor current in the current discontinuous mode. FIG. 7A is a waveform diagram of the inductor current in the continuous current mode and in the steady state, and FIG. 7B is a waveform diagram of the inductor current in the current continuous mode and in the transient state. 8A is a waveform diagram of the inductor current in the current discontinuous mode and in the steady state, and FIG. 8B is a waveform diagram of the inductor current in the current continuous mode and in the transient state.

A PFC converter according to an embodiment of the present invention will be described with reference to FIGS.
FIG. 2 is a circuit diagram of the PFC converter 101 according to the embodiment of the present invention. In FIG. 2, reference signs P <b> 11 and P <b> 12 are input ports of the PFC converter 101, and reference signs P <b> 21 and P <b> 22 are output ports of the PFC converter 101. An AC input power supply Vac, which is a commercial AC power supply, is input to the input ports P11 to P12, and a load circuit 20 is connected to the output ports P21 to P22.

The load circuit 20 is, for example, a DC-DC converter and a circuit of an electronic device that is supplied with power by the DC-DC converter.

In the input stage of the PFC converter 101, a diode bridge B1 which is a rectifier circuit for full-wave rectifying the AC voltage of the AC input power supply Vac is provided. A series circuit of an inductor L1, a switching element Q1, and a current detecting resistor R1 is connected to the output side of the diode bridge B1. A rectifying / smoothing circuit including a diode D1 and a smoothing capacitor C1 is connected in parallel to both ends of the switching element Q1. The inductor L1, the switching element Q1, the diode D1, and the smoothing capacitor C1 constitute a so-called boost chopper circuit.

An input voltage detection circuit 11 is provided between both ends on the output side of the diode bridge B1. An output voltage detection circuit 12 is provided between the output ports P21 and P22. The digital signal processing circuit 13 is constituted by a DSP, and controls the PFC converter 101 by digital signal processing. That is, the digital signal processing circuit 13 receives the output signal of the input voltage detection circuit 11 and detects the phase of the voltage of the AC input power supply by a method described later. Further, the output signal of the output voltage detection circuit 12 is inputted to detect the output voltage. Further, the switching element Q1 is turned on / off at a predetermined switching frequency.

The processing unit related to the switching control signal for the switching element Q1 of the digital signal processing circuit 13 corresponds to the “switching control means” according to the present invention. The current detection resistor R1 corresponds to a “current detection circuit” according to the present invention. Further, the processing section related to current detection of the digital signal processing circuit 13 corresponds to the “first current detection means” and the “second current detection means” according to the present invention.

The digital signal processing circuit 13 is provided with a port for communicating with the load circuit 20, and for example, performs data communication or signal input / output, and indicates the state of the converter with respect to the load circuit (electronic device). Always transmit, transmit input voltage, output voltage, output current, etc., or receive the load status from the load circuit side and reflect it in switching control.

FIG. 3 is a diagram showing various control methods of the PFC converter 101 by the digital signal processing circuit 13. 3A, 3B, and 3C are current waveforms in one cycle of the AC input power supply. Here, the waveform IL is a waveform of a current flowing through the inductor L1 in the PFC converter 101 shown in FIG. Ip is an envelope of the peak value (peak current), and Ia is an envelope of the average value (average current). However, for convenience of illustration, the case where the switching frequency of the PFC converter 101 is extremely low, that is, the current waveform flowing through the inductor L1 is represented by a frequency that is visible in a triangular waveform.

3A is a waveform diagram in the current continuous mode, FIG. 3B is a waveform diagram in the current discontinuous mode, and FIG. 3C is a waveform diagram in the current critical mode. Thus, in the current continuous mode shown in FIG. 3A, the current flowing through the inductor L1 of the PFC converter 101 does not become zero except near the zero cross of the AC input power supply. In the current discontinuous mode shown in FIG. 3B, a period in which the current value becomes 0 occurs every time the excitation energy is accumulated / released in the inductor L1 of the PFC converter 101. Further, in the critical mode shown in FIG. 3C, the current value becomes 0 each time the excitation energy is accumulated / released in the inductor L1, and the state of the current value 0 does not continue.

FIG. 4 is a voltage / current waveform diagram of the PFC converter 101 in units of switching periods in a state where control is performed in the continuous current mode.
The digital signal processing circuit 13 performs switching control so that the input current to the PFC converter 101, that is, the average value of the current flowing through the inductor L1, is similar to the full-wave rectified waveform. In this way, when an input current similar to the input voltage flows, harmonics are suppressed and the power factor is improved.

4A shows a current waveform of the average value Ii of the current flowing through the inductor L1 in a half cycle unit of the commercial power supply frequency, and FIG. 4B shows a switching cycle of a part of the time axis. A waveform diagram of the current IL flowing through the inductor L1 in units, (C) is a waveform diagram of the drain-source voltage Vds of the switching element Q1.

In the ON period Ton of the switching element Q1, the current IL flows through the inductor L1, and the current IL increases with a slope determined according to the voltage across the inductor L1 and the inductance of the inductor L1. Thereafter, the current IL decreases with an inclination determined by the voltage across the inductor L1 and its inductance during the OFF period Toff of the switching element Q1. As described above, the current IL flowing through the inductor L1 with the width of the current ripple ΔIL varies in the switching cycle.

FIG. 5 is a diagram illustrating a method for obtaining an average value of the current flowing through the inductor L1 in order to perform the average current control in the current continuous mode.
When the current value (peak value) flowing through the inductor L1 at the turn-off timing of the switching element Q1 is represented by ILp and the current value (minimum value) flowing through the inductor L1 at the turn-on timing of the switching element Q1 is represented by ILb, the on period Ton of the switching element Q1. The average value (average current) of the current flowing through the inductor L1 is expressed by the following relationship.

ILav = (ILp + ILb) / 2 (1)
On the other hand, since the current flowing through the inductor L1 linearly decreases during the off period Toff of the switching element Q1, the current value of the inductor L1 at the central timing of the off period Toff of the switching element Q1 is equal to the average current value ILav.

Therefore, the drop voltage of the resistor R1 at the center timing of the ON period Ton of the switching element Q1 is sampled. This sampling value is a value proportional to the average current value ILav of the current flowing through the inductor L1 during the ON period Ton of the switching element Q1. Further, the voltage drop of the resistor R1 at the center timing of the off period Toff of the switching element Q1 is sampled. This sampling value is a value proportional to the average current value ILav of the current flowing through the inductor L1 during the OFF period Toff of the switching element Q1.

Since the switching control signal given to the gate of the switching element Q1 is generated by the digital signal processing circuit 13, the central timing ts1 of the on period Ton and the central timing ts2 of the off period Toff are also digital signal processed. The circuit 13 knows (under control). Therefore, for example, the voltage drop of the current detection resistor R1 can be sampled at the above timing without inputting a timing signal from the outside.

Next, the first processing content of the “current increase / decrease state detection means” by the digital signal processing circuit 13 shown in FIG. 2 will be described with reference to FIG.
6A is a waveform diagram of the inductor current in the continuous current mode, and FIG. 6B is a waveform diagram of the inductor current in the current discontinuous mode.

In the current continuous mode, as described above, as shown in FIG. 6A, the average current value ILav1 of the current flowing through the inductor L1 during the on period Ton of the switching element Q1 and the inductor during the off period Toff of the switching element Q1. The average current value ILav2 of the current flowing through L1 is equal. Therefore, first, the first current value ILav1 is obtained by sampling at the central timing ts1 of the ON period Ton of the switching element Q1, and the second current value is obtained by sampling at the central timing ts2 of the OFF period Toff of the switching element Q1. ILav2 is obtained, and when ILav1 = ILav2, the current continuous mode is determined.

The current critical mode is a special state of the continuous current mode, and the relationship between the first and second current values is the same as in the continuous current mode. In the following description, “current continuous mode” includes “current critical mode”.

On the other hand, in the current discontinuous mode, as shown in FIG. 6B, the average current value ILav1 of the current flowing in the inductor L1 during the on period Ton of the switching element Q1 and the inductor L1 during the off period Toff of the switching element Q1. Is different from the average current value ILav2 of the current flowing through the. Therefore, first, the first current value ILav1 is obtained by sampling at the central timing ts1 of the ON period Ton of the switching element Q1, and the second current value is obtained by sampling at the central timing ts2 of the OFF period Toff of the switching element Q1. ILav2 is obtained, and when ILav1 ≠ ILav2, the current discontinuous mode is determined.

Next, the second processing content of the “current increase / decrease state detection means” by the digital signal processing circuit 13 shown in FIG. 2 will be described with reference to FIG.
FIG. 7A is a waveform diagram of the inductor current in the continuous current mode and steady state, and FIG. 7B is a waveform diagram of the inductor current in the continuous current mode and transient state.
In the steady state, as shown in FIG. 7A, in any switching cycle, the average current flowing through the inductor L1 during the ON period Ton of the switching element Q1 and the inductor L1 flows during the OFF period Toff of the switching element Q1. It is equal to the average current. Accordingly, by sampling at the central timing (ts11, ts12,...) Of the on period Ton in different periods of the switching element Q1, the first current value ILav1 is obtained a plurality of times, and the switching element Q1 is turned off in different periods. The second current value ILav2 is obtained by sampling at the central timing (ts21, ts22,...) Of the period Toff, and when the first current value and the second current value at a plurality of timings are equal, It is determined to be a continuous mode and a steady state.

On the other hand, in a transient state, for example, when the input power supply voltage is started, as shown in FIG. 7B, the average currents flowing in the inductor L1 during the on period Ton of the switching element Q1 are different between the switching elements Q1 as shown in FIG. In comparison, it is changing. Even if the average currents of the currents flowing through the inductor L1 in the off period Toff of the switching element Q1 are compared with each other, it is changed.

As in the example shown in FIG. 7B, when compared in adjacent switching cycles, the average current flowing through the inductor L1 during the ON period Ton of the switching element Q1 increases by ΔIL1. Further, the average current flowing through the inductor L1 during the OFF period Toff of the switching element Q1 is increased by ΔIL2.

Therefore, the first current value is obtained a plurality of times by sampling at the central timing (ts11, ts12,...) Of the on-period Ton in different periods of the switching element Q1, and the first current values are obtained from each other. If it changes and it has changed, it will determine with it being in a transient state. Alternatively, the second current value is obtained a plurality of times by sampling at the central timing (ts21, ts22,...) Of the off period Toff in different periods of the switching element Q1, and the second current values are obtained from each other. If it changes and it has changed, it will determine with it being in a transient state.

Next, the third processing content of the “current increase / decrease state detection means” by the digital signal processing circuit 13 shown in FIG. 2 will be described with reference to FIG.
FIG. 8A is a waveform diagram of the inductor current in the current discontinuous mode and steady state, and FIG. 8B is a waveform diagram of the inductor current in the current continuous mode and transient state.
In the current discontinuous mode, as shown in FIG. 8A, the average current value ILav1 of the current flowing in the inductor L1 during the ON period Ton of the switching element Q1 and the inductor L1 flows during the OFF period Toff of the switching element Q1. It differs from the average current value ILav2 of the current. In the steady state, the average current value ILav1 of the current flowing through the inductor L1 during the ON period Ton of the switching element Q1 is constant in different switching cycles. Similarly, in different switching cycles, the average current value ILav2 of the current flowing through the inductor L1 during the OFF period Toff of the switching element Q1 is constant.

Therefore, first, the first current value is obtained a plurality of times by sampling at the central timing (ts11, ts12,...) Of the ON period Ton in different periods of the switching element Q1, or the switching element Q1 is different. The second current value is obtained a plurality of times by sampling at the center timing (ts21, ts22,...) Of the off period Toff in the cycle, and the first current values or the second current values are compared, If it has not changed, it is determined that it is in a steady state. Then, the first current value ILav1 obtained by sampling at the central timing (ts11, ts12,...) Of the ON period Ton of the switching element Q1 and the central timing (ts21, ts22) of the OFF period Toff of the switching element Q1. ,...) Is determined to be in the current discontinuous mode when the second current value ILav2 obtained by sampling is a different value.

On the other hand, in the current continuous mode and in the transient state in the current decreasing direction, as shown in FIG. 8B, the switching element Q1 is turned off based on the average current flowing through the inductor L1 during the on period Ton of the switching element Q1. The average current flowing through the inductor L1 during the period Toff decreases. The change in the average current in one cycle appears in the same manner as in the case shown in FIG. However, when the average currents of the currents flowing through the inductor L1 in the ON period Ton of the switching element Q1 are compared with each other in different switching periods, they change as indicated by ΔIL1. Even if the average currents of the currents flowing through the inductor L1 during the OFF period Toff of the switching element Q1 are compared, they are similarly changed as indicated by ΔIL2.

Therefore, by determining the current continuous mode and the current discontinuous mode as described above and determining whether or not there is an excessive state, whether the current continuous mode is a steady state or a transient state in the current continuous mode. Is determined.

DESCRIPTION OF SYMBOLS 101 ... PFC converter 11 ... Input voltage detection circuit 12 ... Output voltage detection circuit 13 ... Digital signal processing circuit 20 ... Load circuit B1 ... Diode bridge C1 ... Smoothing capacitor D1 ... Diode Q1 ... Switching element R1 ... Current detection resistance Toff ... Off Period Ton: On period ts1, ts2: Central timing Vac: AC input power

Claims

A rectifying circuit for rectifying an AC voltage input from an AC input power supply; a series circuit including an inductor and a switching element connected to the next stage of the rectifying circuit; and a rectifying / smoothing circuit connected in parallel to the switching element; Switching control means for controlling on / off of the switching element so that an input current input from the AC input power source is similar to the AC voltage, and a PFC converter comprising:
A current detection circuit for detecting a current flowing through the switching element or the inductor during an on period of the switching element;
First current detection means for sampling a detection signal of a current flowing through the switching element or the inductor at the center of the ON period of the switching element and detecting it as a first current value;
Second current detection means for sampling a detection signal of a current flowing through the inductor at the center of the off period of the switching element and detecting it as a second current value;
Current increase / decrease state detection means for comparing the first current value and the second current value to detect a current increase / decrease state;
PFC converter with
The current increase / decrease state detection means regards the current continuous mode when the first current value and the second current value are equal, and current discontinuity when the second current value is smaller than the first current value. The PFC converter according to claim 1, which is regarded as a mode.
The current increase / decrease state detection means determines a steady state and a transient state based on a change between the first current values or a change between the second current values at different periods. The PFC converter according to 1 or 2.