US20070258412A1

US20070258412A1 - Method for recovering data transmitted over a plurality of channels employing wireless code division multiple access communication

Info

Publication number: US20070258412A1
Application number: US11/824,856
Authority: US
Inventors: Donald Schilling; John Kowalski
Original assignee: InterDigital Technology Corp
Current assignee: InterDigital Technology Corp
Priority date: 1993-04-22
Filing date: 2007-07-03
Publication date: 2007-11-08
Also published as: SE532856C2; SE532857C2; SE9700184D0; CA2195534A1; ATE460785T1; DE19581709T1; CN1501611A; EP0772928A1; US7230938B2; HK1065190A1; CN1229935C; CN1154770A; EP1860811B1; US7164668B2; US7167462B2; CA2369499C; US7167464B2; ES2151461T1; EP1860811A1; EP0772928B1

Abstract

A method for recovering data transmitted over a plurality of channels employing wireless code division multiple access communication, comprises receiving the plurality of channels as a received signal, each channel associated with a code. Others from the plurality of channels from the received signal is subtracted for each for each of the plurality of channels and a result a result of that subtracting as data for that channel is despread. That channel despread signal is respread with a respective channel code, wherein the respreading channel code is aligned to a timing of the despread received signal.

Description

CROSS REFERENCE TO RELATED APPLICATIONS

This application is a continuation of application Ser. No. 10/201,797, filed on Jul. 24, 2002, which is a continuation of application Ser. No. 09/851,740, filed May 9, 2001, now U.S. Pat. No. 6,868,076, which is a continuation of application Ser. No. 09/276,019, filed Mar. 25, 1999, now U.S. Pat. No. 6,259,688, which is a continuation of U.S. application Ser. No. 08/939,146, filed Sep. 29, 1997, now U.S. Pat. No. 6,014,373, which is a continuation of U.S. application Ser. No. 08/654,994, filed May 29, 1996, now U.S. Pat. No. 5,719,852, which is a continuation of U.S. application Ser. No. 08/279,477, filed Jul. 26, 1994, now U.S. Pat. No. 5,553,062, which is a continuation-in-part of U.S. application Ser. No. 08/051,017, filed Apr. 22, 1993, now U.S. Pat. No. 5,363,403, all of which are incorporated herein by reference as if fully set forth.

BACKGROUND

This invention relates to spread-spectrum communications, and more particularly to an interference canceller employed by a remote terminal for reducing interference in a direct sequence, code division multiple access receiver.
Direct sequence, code division multiple access, spread-spectrum communications systems are capacity limited by interference caused by other simultaneous users. This is compounded if adaptive power control is not used, or is used but is not perfect.
Code division multiple access is interference limited. The more users transmitting simultaneously, the higher the bit error rate (BER). Increased capacity requires forward error correction (FEC) coding, which in turn, increases the data rate and limits capacity.

SUMMARY

A general object of the invention is to reduce noise resulting from N−1 interfering signals in a direct sequence, spread-spectrum code division multiple access receiver.
The present invention, as embodied and broadly described herein, provides a method for recovering data transmitted over a plurality of channels employing wireless code division multiple access communication. The method comprises receiving the plurality of channels as a received signal, each channel associated with a code. Others from the plurality of channels from the received signal is subtracted for each for each of the plurality of channels and a result a result of that subtracting as data for that channel is despread. That channel despread signal is respread with a respective channel code, wherein the respreading channel code is aligned to a timing of the despread received signal.
Additional objects and advantages of the invention are set forth in part in the description which follows, and in part are obvious from the description, or may be learned by practice of the invention. The objects and advantages of the invention also may be realized and attained by means of the instrumentalities and combinations particularly pointed out in the appended claims.

BRIEF DESCRIPTION OF THE DRAWING(S)

The accompanying drawings, which are incorporated in and constitute a part of the specification, illustrate preferred embodiments of the invention, and together with the description serve to explain the principles of the invention.
FIG. 1 is a block diagram of the spread-spectrum CDMA interference canceller using correlators;
FIG. 2 is a block diagram of the spread-spectrum CDMA interference canceller for processing multiple channels using correlators;
FIG. 3 is a block diagram of the spread-spectrum CDMA interference canceller using matched filters;
FIG. 4 is a block diagram of the spread-spectrum CDMA interference canceller for processing multiple channels using matched filters;
FIG. 5 is a block diagram of the spread-spectrum CDMA interference canceller having multiple iterations for processing multiple channels;
FIG. 6 illustrates theoretical performance characteristic for E_b/η=6 dB;
FIG. 7 illustrates theoretical performance characteristic for E_b/η=10 dB;
FIG. 8 illustrates theoretical performance characteristic for E_b/η=15 dB;
FIG. 9 illustrates theoretical performance characteristic for E_b/η=20 dB;
FIG. 10 illustrates theoretical performance characteristic for E_b/η=25 dB;
FIG. 11 illustrates theoretical performance characteristic for E_b/η=30 dB;
FIG. 12 is a block diagram of interference cancellers connected together;
FIG. 13 is a block diagram combining the outputs of the interference cancellers of FIG. 12;
FIG. 14 illustrates simulation performance characteristics for asynchronous, PG=100, Equal Powers, E_bN=30 dB;
FIG. 15 illustrates simulation performance characteristics for asynchronous, PG=100, Equal Powers, E_bN=30 dB;
FIG. 16 illustrates simulation performance characteristics for asynchronous, PG=100, Equal Powers, E_bN=30 dB; and
FIG. 17 illustrates simulation performance characteristics for asynchronous, PG=100, Equal Powers, E_bN=30 db.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT(S)

Reference now is made in detail to the present preferred embodiments of the invention, examples of which are illustrated in the accompanying drawings, wherein like reference numerals indicate like elements throughout the several views.
In the exemplary arrangement shown in FIG. 1, a spread-spectrum code division multiple access (CDMA) interference canceller is provided for reducing interference in a spread-spectrum CDMA receiver having N channels. The present invention also works on a spread-spectrum code division multiplexed (CDMA) system. Accordingly, without loss of generality, the term spread-spectrum CDMA signal, as used herein, includes spread-spectrum CDMA signals and spread-spectrum CDM signals. In a personal communications service, the interference canceller may be used at a base station or in a remote unit such as a handset.
FIG. 1 illustrates the interference canceller for the first channel, defined by the first chip-code signal. The interference canceller includes a plurality of despreading means, a plurality of timing means, a plurality of spread-spectrum-processing means, subtracting means, and first channel-despreading means.
Using a plurality of chip-code signals, the plurality of despreading means despreads the received spread-spectrum CDMA signals as a plurality of despread signals, respectively. In FIG. 1 the plurality of despreading means is shown as first despreading means, second despreading means, through N^thdespreading means. The first despreading means includes a first correlator, which is embodied, by way of example, as a first mixer 51, first chip-code-signal generator 52, and a first integrator 54. The first integrator 54 alternatively may be a first lowpass filter or a first bandpass filter. The first mixer 51 is coupled between the input 41 and the first chip-code-signal generator 52 and the first integrator 54.
The second despreading means includes a second correlator, which is embodied, by way of example, as second mixer 61, second chip-code-signal generator 62 and second integrator 64. The second integrator 64 alternatively may be a second lowpass filter or a second bandpass filter. The second mixer 61, is coupled between the input 41, the second chip-code-signal generator 62, and the second integrator 64.
The N^thdespreading means is depicted as an N^thcorrelator shown, by way of example, as N^thmixer 71, and N^thchip-code-signal generator 72, and N^thintegrator 74. The N^thintegrator 74 alternatively may be an N^thlowpass filter or an N^thbandpass filter. The N^thmixer 71 is coupled between the input 41, the N^thchip-code-signal generator 72 and the N^thintegrator 74.
As is well known in the art, the first through N^thdespreading means may be embodied as any device which can despread a channel in a spread-spectrum signal.
The plurality of timing means may be embodied as a plurality of delay devices 53, 63, 73. A first delay device 53 has a delay time T, which is approximately the same as the integration time T_bof first integrator 54, or time constant of the first lowpass filter or first bandpass filter. A second delay device 63 has a time delay T, which is approximately the same as the integration time T_bof second integrator 64, or time constant of the second lowpass filter or second bandpass filter. Similarly, the N^thdelay device 73 has a time delay T, which is approximately the same as the integration time T_bof N^thintegrator 74, or time constant of the N^thlowpass filter or N^thbandpass filter. Typically, the integration times of the first integrator 54, second integrator 64 through N^thintegrator 74 are the same. If lowpass filters are used, then typically the time constants of the first lowpass filter, second lowpass filter through N^thlowpass filter are the same. If bandpass filters are used, then the time constants of the first bandpass filter, second bandpass filter through N^thbandpass filter are the same.
The plurality of spread-spectrum-processing means regenerators each of the plurality of despread signals as a plurality of spread-spectrum signals. The plurality of spread-spectrum-processing means uses a timed version, i.e. delayed version, of the plurality of chip-code signals, for spread-spectrum processing the plurality of despread signals, respectively, with a chip-code signal corresponding to a respective despread signal. The plurality of spread-spectrum-processing means is shown, by way of example, as a first processing mixer 55, a second processing mixer 65, through an N^thprocessing mixer 75. The first processing mixer 55 is coupled to the first integrator 54, and through a first delay device 53 to the first chip-code-signal generator 52. The second processing mixer 65 is coupled to the second integrator 64, and through the second delay device 63 to the second chip-code-signal generator 62. The N^thprocessing mixer 75 is coupled to the N^thintegrator 74 through the delay device 73 to the N^thchip-code-signal generator 72.
For reducing interference to a channel using an i^thchip-code signal of the spread-spectrum CDMA signal, the subtracting means subtracts, from the spread-spectrum CDMA signal, each of the N−1 spread-spectrum-processed-despread signals not corresponding to the i^thchannel. The subtracting means thereby generates a subtracted signal. The subtracting means is shown as a first subtractor 150. The first subtractor 150 is shown coupled to the output of the second processing mixer 65, through the N^thprocessing mixer 75. Additionally, the first subtractor 150 is coupled through a main delay device 48 to the input 41.
The i^thchannel-despreading means despreads the subtracted signal with the i^thchip-code signal as the i^thchannel. The first channel-despreading means is shown as a first channel mixer 147. The first channel mixer 147 is coupled to the first delay device 53, and to the first subtractor 150. The first channel integrator 146 is coupled to the first channel mixer 147.
The first chip-code-signal generator 52, the second chip-code-signal generator 62, through the N^thchip-code signal generator 72 generate a first chip-code signal, a second chip-code signal, through an N^thchip-code signal, respectively. The term “chip-code signal” is used herein to mean the spreading signal of a spread-spectrum signal, as is well known in the art. Typically the chip-code signal is generated from a pseudorandom (PN) sequence. The first chip-code signal, the second chip code signal, through the N^thchip-code signal might be generated from a first PN sequence, a second PN sequence, through an N^thPN sequence, respectively. The first PN sequence is defined by or generated from a first chip codeword, the second PN sequence is defined by or generated from a second chip codeword, through the N^thPN sequence is defined by or generated from an N^thchip-codeword. Each of the first chip codeword, second chip codeword through N^thchip codeword is distinct, i.e. different from one another. In general, a chip codeword can be the actual sequence of a PN sequence, or used to define settings for generating the PN sequence. The settings might be the delay taps of shift registers, for example.
A first channel of a received spread-spectrum CDMA signal at input 41 is despread by first mixer 51 as a first despread signal, using the first chip-code signal generated by first chip-code-signal generator 52. The first despread signal from the first mixer 51 is filtered through first integrator 54. First integrator 54 integrates for a time T_b, the time duration of a symbol such as a bit. At the same time, the first chip-code signal is delayed by time T by delay device 53. The delay time T is approximately equal to the integration time T_bplus system or component delays. Systems or component delays are usually small, compared to integration time T_b.
The delayed version of the first chip-code signal is processed with the first despread signal from the output of the first integrator 54 using the first spreading mixer 55. The output of the first spreading mixer 55 is fed to subtractors other than first subtractor 150 for processing the second through N^thchannels of the spread-spectrum CDMA signal.
For reducing interference to the first channel of the spread-spectrum CDMA signal, the received spread-spectrum CDMA signal is processed by the second through N^thdespreaders as follows. The second channel of the spread-spectrum CDMA signal is despread by the second despreading means. At the second mixer 61, a second chip-code signal, generated by the second chip-code-signal generator 62, despreads the second channel of the spread-spectrum CDMA signal. The despread second channel is filtered through second integrator 64. The output of the second integrator 64 is the second despread signal. The second despread signal is spread-spectrum processed by second processing mixer 65 by a delayed version of the second chip-code signal. The second chip-code signal is delayed through delay device 63. The delay device 63 delays the second chip-code signal by time T. The second channel mixer 65 spread-spectrum processes a timed version, i.e. delayed version, of the second chip-code signal with the filtered version of the second spread-spectrum channel from second integrator 64. The term “spread-spectrum process” as used herein includes any method for generating a spread-spectrum signal by mixing or modulating a signal with a chip-code signal. Spread-spectrum processing may be done by product devices, EXCLUSIVE-OR gates, matched filters, or any other device or circuit as is well known in the art.
Similarly, the N^thchannel of the spread-spectrum CDMA signal is despread by the N^thdespreading means. Accordingly, the received spread-spectrum CDMA signal has the N^thchannel despread by N^thmixer 61, by mixing the spread-spectrum CDMA signal with the N^thchip-code signal from N^thchip-code-signal generator 72. The output of the N^thmixer 71 is filtered by N^thintegrator 74. The output of the N^thintegrator 74, which is the N^thdespread signal, is a despread and filtered version of the N^thchannel of the spread-spectrum CDMA signal. The N^thdespread signal is spread-spectrum processed by a delayed version of the N^thchip-code signal. The N^thchip-code signal is delayed through N^thdelay device 73. The N^thprocessing mixer 75 spread-spectrum processes the timed version, i.e. a delayed version, of the N^thchip-code signal with the N^thdespread signal.
At the first subtractor 150, each of the outputs of the second processing mixer 65 through the N^thprocessing mixer 75 is subtracted from a timed version, i.e. a delayed version, of the spread-spectrum CDMA signal from input 41. The delay of the spread-spectrum CDMA signal is timed through the first main delay device 48. Typically, the delay of the first main delay device 48 is time T, which is approximately equal to the integration time of the first integrator 54 through N^thintegrator 74.
At the output of the first subtractor 150, is generated a first subtracted signal. The first subtracted signal, for the first channel of the spread-spectrum CDMA signal, is defined herein to be the outputs from the second processing mixer 65 through N^thprocessing mixer 75, subtracted from the delayed version of the spread-spectrum CDMA signal. The second subtracted signal through N^thsubtracted signal are similarly defined.
The delayed version of the first chip-code signal from the output of first delay device 53 is used to despread the output of the first subtractor 150. Accordingly, the first subtracted signal is despread by the first chip-code signal by first channel mixer 147. The output of the first channel mixer 147 is filtered by first channel integrator 147. This produces an output estimate d₁of the first channel of the spread-spectrum CDMA signal.
As illustratively shown in FIG. 2, a plurality of subtractors 150, 250, 350, 450 can be coupled appropriately to the input 41 and to a first spreading mixer 55, second spreading mixer 65, third spreading mixer, through an N^thspreading mixer 75 of FIG. 1. The plurality of subtractors 150, 250, 350, 450 also are coupled to the main delay device 48 from the input 41. This arrangement can generate a first subtracted signal from the first subtractor 150, a second subtracted signal from the second subtractor 250, a third subtracted signal from the third subtractor 350, through an N^thsubtracted signal from an N^thsubtractor 450.
The outputs of the first subtractor 150, second subtractor 250, third subtractor 350, through the N^thsubtractor 450 are each coupled to a respective first channel mixer 147, second channel mixer 247, third channel mixer 347, through N^thchannel mixer 447. Each of the channel mixers is coupled to a delayed version of the first chip-code signal, g₁(t-T), second chip-code signal, g₂(t-T), third chip-code signal, g₃(t-T), through N^thchip-code signal, g_N(t-T). The outputs of each of the respective first channel mixer 147, second channel mixer 247, third channel mixer 347, through N^thchannel mixer 447 are coupled to a first channel integrator 146, second channel integrator 246, third channel integrator 346 through N^thchannel integrator 446, respectively. At the output of each of the channel integrators is produced an estimate of the respective first channel d₁, second channel d₂, third channel d₃, through N^thchannel d_N.
Referring to FIG. 1, use of the present invention is illustrated for the first channel of the spread-spectrum CDMA signal, with the understanding that the second through N^thCDMA channels work similarly. A received spread-spectrum CDMA signal at input 41 is delayed by delay device 48 and fed to the first subtractor 150. The spread-spectrum CDMA signal has the second channel through N^thchannel despread by second mixer 61 using the second chip-code signal, through the N^thmixer 71 using the N^thchip-code signal. The respective second chip-code signal through the N^thchip-code signal are generated by the second chip-code-signal generator 62 through the N^thchip-code-signal generator 72. The second channel through N^thchannel are despread and filtered through the second integrator 64 through the N^thintegrator 74, respectively. The despreading removes, partially or totally, the non-despread channels at the outputs of each of the second integrator 64 through N^thintegrator 74.
In a preferred embodiment, each of the chip-code signal used for the first chip-code-signal generator 52, second chip-code-signal generator 62 through the N^thchip-code-signal generator 72, are orthogonal to each other. Use of chip-code signals having orthogonality however, is not required for operation of the present invention. When using orthogonal chip-code signals, the despread signals have the respective channel plus noise at the output of each of the integrators. With orthogonal chip-code signals, theoretically the mixers remove channels orthogonal to the despread channel. The respective channel is spread-spectrum processed by the respective processing mixer.
At the output of the second processing mixer 65 through the N^thprocessing mixer 75 is a respread version of the second channel through the N^thchannel, plus noise components contained therein. Each of the second channel through N^thchannel is then subtracted from the received spread-spectrum CDMA signal by the first subtractor 150. The first subtractor 150 produces the first subtracted signal. The first subtracted signal is despread by a delayed version of the first chip-code signal by first channel mixer 147, and filtered by first channel filter 146. Accordingly, prior to despreading the first channel of the spread-spectrum CDMA signal, the second through N^thchannels plus noise components aligned with these channels are subtracted from the received spread-spectrum CDMA signal. As illustratively shown in FIG. 3, an alternative embodiment of the spread-spectrum CDMA interference canceller includes a plurality of first despreading means, a plurality of spread-spectrum-processing means, subtracting means, and second despreading means. In FIG. 3, the plurality of despreading means is shown as first despreading means, second despreading means through N^thdespreading means. The first despreading means is embodied as a first matched filter 154. The first matched filter 154 has an impulse response matched to the first chip-code signal, which is used to spread-spectrum process and define the first channel of the spread-spectrum CDMA signal. The first matched filter 154 is coupled to the input 41.
The second despreading means is shown as second matched filter 164. The second matched filter 164 has an impulse response matched to the second chip-code signal, which is used to spread-spectrum process and define the second channel of the spread-spectrum CDMA signal. The second matched filter 164 is coupled to the input 41.
The N^thdespreading means is shown as an N^thmatched filter 174. The N^thmatched filter has an impulse response matched to the N^thchip-code signal, which is used to spread-spectrum process and define the N^thchannel of the spread-spectrum CDMA signal. The N^thmatched filter is coupled to the input 41.
The term matched filter, as used herein, includes any type of matched filter that can be matched to a chip-code signal. The matched filter may be a digital matched filter or analog matched filter. A surface acoustic wave (SAW) device may be used at a radio frequency (RF) or intermediate frequency (IF). Digital signal processors and application specific integrated circuits (ASIC) having matched filters may be used at RF, IF or baseband frequency.
In FIG. 3, the plurality of spread-spectrum-processing means is shown as the first processing mixer 55, the second processing mixer 65, through the N^thprocessing mixer 75. The first processing mixer 55 may be coupled through a first adjustment device 97 to the first chip-code-signal generator 52. The second processing mixer 65 may be coupled through the second adjustment device 98 to the second chip-code-signal generator 62. The N^thprocessing mixer 75 may be coupled through the N^thadjustment device 99 to the N^thchip-code-signal generator 72. The first adjusting device 97, second adjustment device 98 through N^thadjustment device 99 are optional, and are used as an adjustment for aligning the first chip-code signal, second chip-code signal through N^thchip-code signal with the first despread signal, second despread signal through N^thdespread signal, outputted from the first matched filter 154, second matched filter 164 through N^thmatched filter 174, respectively.
The subtracting means is shown as the first subtractor 150. The first subtractor 150 is coupled to the output of the second processing mixer 65, through the N^thprocessing mixer 75. Additionally, the first subtractor 150 is coupled through the main delay device 48 to the input 41.
The first channel-despreading means is shown as a first channel-matched filter 126. The first channel-matched filter 126 is coupled to the first subtractor 150. The first channel-matched filter 126 has an impulse response matched to the first chip-code signal.
A first channel of a received spread-spectrum CDMA signal, at input 41, is despread by first matched filter 154. The first matched filter 154 has an impulse response matched to the first chip-code signal. The first chip-code signal defines the first channel of the spread-spectrum CDMA signal, and is used by the first chip-code-signal generator 52. The first chip-code signal may be delayed by adjustment time τ by adjustment device 97. The output of the first matched filter 154 is spread-spectrum processed by the first processing mixer 55 with the first chip-code signal. The output of the first processing mixer 55 is fed to subtractors other than the first subtractor 150 for processing the second channel through the N^thchannel of the spread-spectrum CDMA signals.
For reducing interference to the first spread-spectrum channel, the received spread-spectrum CDMA signal is processed by the second despreading means through N^thdespreading means as follows. The second matched filter 164 has an impulse response matched to the second chip-code signal. The second chip-code signal defines the second channel of the spread-spectrum CDMA signal, and is used by the second chip-code-signal generator 62. The second matched filter 164 despreads the second channel of the spread-spectrum CDMA signal. The output of the second matched filter 164 is the second despread signal. The second despread signal triggers second chip-code-signal generator 62. The second despread signal also is spread-spectrum processed by second processing mixer 65 by a timed version of the second chip-code signal. The timing of the second chip-code signal triggers the second despread signal from the second matched filter 164.
Similarly, the N^thchannel of the spread-spectrum CDMA signal is despread by the N^thdespreading means. Accordingly, the received spread-spectrum CDMA signal has the N^thchannel despread by N^thmatched filter 174. The output of the N^thmatched filter 174 is the N^thdespread signal, i.e. a despread and filtered version of the N^thchannel of the spread-spectrum CDMA signal. The N^thdespread signal is spread-spectrum processed by a timed version of the N^thchip-code signal. The timing of the N^thchip-code signal is triggered by the N^thdespread signal from the N^thmatched filter 174. The N^thprocessing mixer 75 spread-spectrum processes the timed version of the N^thchip-code signal with the N^thdespread signal.
At the first subtractor 150, each of the outputs of the second processing mixer 65 through the N^thprocessing mixer 75 are subtracted from a delayed version of the spread-spectrum CDMA signal from input 41. The delay of the spread-spectrum CDMA signal is timed through delay device 48. The time of delay device 48 is set to align the second through N^thspread-spectrum-processed-despread signals for subtraction from the spread-spectrum CDMA signal. This generates at the output of the first subtractor 150, a first subtracted signal. The subtracted signal is despread by the first channel-matched filter 126. This produces an output estimate d₁of the first channel of the spread-spectrum CDMA signal.
As illustrated in FIG. 4, a plurality of subtractors 150, 250, 350, 450 can be coupled appropriately to the output from a first processing mixer, second processing mixer, third processing mixer, through an N^thprocessing mixer, and to a main delay device form the input. A first subtracted signal is outputted from the first subtractor 150, a second subtracted signal is outputted from the second subtractor 250, a third subtracted signal is outputted from the third subtractor 350, through an N^thsubtractor signal is outputted from the N^thsubtractor 450.
The output of the first subtractor 150, second subtractor 250, third subtractor 350, through the N^thsubtractor 450 are each coupled to a respective first channel-matched filter 126, second channel-matched filter 226, third channel-matched filter 326, through N^thchannel-matched filter 426. The first channel-matched filter 126, second channel-matched filter 226, third channel-matched filter 326 through N^thchannel-matched filter 426 have an impulse response matched to the first chip-code signal, second chip-code signal, third chip-code signal, through N^thchip-code signal, defining the first channel, second channel, third channel through N^thchannel, respectively, of the spread-spectrum CDMA signal. At each of the outputs of the respective first channel-matched filter 126, second channel-matched filter 226, third channel-matched filter 326, through N^thchannel-matched filter 426, is produced an estimate of the respective first channel d₁, second channel d₂, third channel d₃, through N^thchannel d_N.
In use, the present invention is illustrated for the first channel of the spread-spectrum CDMA signal, with the understanding that the second channel through N^thchannel work similarly. A received spread-spectrum CDMA signal at input 41 is delayed by delay device 48 and fed to subtractor 150. The same spread-spectrum CDMA signal has the second through N^thchannel despread by the second matched filter 164 through the N^thmatched filter 174. This despreading removes the other CDMA channels from the respective despread channel. In a preferred embodiment, each of the chip-code signals used for the first channel, second channel, through the N^thchannel, is orthogonal to the other chip-code signals. At the output of the first matched filter 154, second matched filter 164 through N^thmatched filter 174, are the first despread signal, second despread signal through N^thdespread signal, plus noise.
The respective channel is spread-spectrum processed by the processing mixers. Accordingly, at the output of the second processing mixer 65 through the N^thprocessing mixer 75 is a spread version of the second despread signal through the N^thdespread signal, plus noise components contained therein. Each of the spread-spectrum-processed-despread signals, is then subtracted from the received spread-spectrum CDMA signal by the first subtractor 150. This produces the first subtracted signal.
The first subtracted signal is despread by first channel-matched filter 126. Accordingly, prior to despreading the first channel of the spread-spectrum CDMA signal, the second channel through N^thchannel plus noise components aligned with these channels, are subtracted from the received spread-spectrum CDMA signal.
As is well known in the art, correlators and matched filters may be interchanged to accomplish the same function. FIGS. 1 and 3 show alternate embodiments using correlators or matched filters. The arrangements may be varied. For example, the plurality of despreading means may be embodied as a plurality of matched filters, while the channel despreading means may be embodied as a correlator. Alternatively, the plurality of despreading means may be a combination of matched filters and correlators. Also, the spread-spectrum-processing means may be embodied as a matched filter or SAW, or as EXCLUSIVE-OR gates or other devices for mixing a despread signal with a chip-code signal. As is well known in the art, any spread-spectrum despreader or demodulator may despread the spread-spectrum CDMA signal. The particular circuits shown in FIGS. 1-4 illustrate the invention by way of example.
The concepts taught in FIGS. 1-4 may be repeated, as shown in FIG. 5. FIG. 5 illustrates a first plurality of interference cancellers 511, 512, 513, a second plurality of interference cancellers 521, 522, 523, through an N^thplurality of interference cancellers 531, 532, 533. Each plurality of interference cancellers includes appropriate elements as already disclosed, and referring to FIGS. 1-4, the input is delayed through a delay device in each interference canceller.
The received spread-spectrum CDMA signals has interference canceled initially by the first plurality of interference cancellers 511, 512, 513, thereby producing a first set of estimates, i.e. a first estimate d₁₁, a second estimate d₁₂, through an N^thestimate d_1N, of the first channel, second channel through the N^thchannel, of the spread-spectrum CDMA signal. The first set of estimates can have interference canceled by the second plurality of interference cancellers 521, 522, 523. The first set of estimates d₁₁, d₁₂, . . . , d_1N, of the first channel, second channel through N^thchannel, are input to the second plurality of interference cancellers, interference canceller 521, interference canceller 522 through N^thinterference canceller 523 of the second plurality of interference cancellers. The second plurality of interference cancellers thereby produce a second set of estimates, i.e. d₂₁, d₂₂, . . . , d_2N, of the first channel, second channel, through N^thchannel. Similarly, the second set estimates can pass through a third plurality of interference cancellers, and ultimately through an M^thset of interference cancellers 531, 532, 533, respectively.
The present invention also includes a method for reducing interference in a spread-spectrum CDMA receiver having N chip-code channels. Each of the N channels is identified by a distinct chip-code signal. The method comprises the steps of despreading, using a plurality of chip-code signals, the spread-spectrum CDMA signal as a plurality of despread signals, respectively. Using a timed version of the plurality of chip-code signals, the plurality of despread signals are spread-spectrum processed with a chip-code signal corresponding to a respective despread signal. Each of the N−1 spread spectrum-processed-despread signals, is subtracted from the spread-spectrum CDMA signal, with the N−1 spread-spectrum-processed-despread signals not including a spread-spectrum-processed signal of the i^thdespread signal, thereby generating a subtracted signal. The subtracted signal is despread to generate the i^thchannel.
The probability of error P_efor direct sequence, spread-spectrum CDMA system is: $P_{e} = \frac{1}{2} {erfc (α SNR)}^{\frac{1}{2}}$
where erfc is complementary error function, SNR is signal-to-noise ratio, and 1≦α≦2. The value of cL depends on how a particular interference canceller system is designed.
The SNR after interference cancellation and method is given by: $SNR = \frac{{(PG / N)}^{R + 1}}{1 + {(PG / N)}^{R + 1} \frac{1}{E_{b} / η} \frac{1 - {(N / PG)}^{R + 1}}{1 - N / PG}}$
where N is the number of channels, PG is the processing gain, R is the number of repetitions of the interference canceller, E_bis energy per information bit and η is noise power spectral density.
FIG. 6 illustrates theoretical performance characteristic, of the interference canceller and method for when E_b/η=6 dB. The performance characteristic is illustrated for SNR out of the interference canceller, versus PG/N. The lowest curve, for R=0, is the performance without the interference canceller. The curves, for R=1 and R=2, illustrates improved performance for using one and two iterations of the interference canceller as shown in FIG. 5. As PG/N→1, there is insufficient SNR to operate. If PG>N, then the output SNR from the interference canceller approaches E_b/η. Further, if (N/PG)^R+1<<1, then
SNR→(E_b/η)(1−N/PG).
FIG. 7 illustrates the performance characteristic for when E_b/η=10 dB.
FIG. 7 illustrates that three iterations of the interference canceller can yield a 4 dB improvement with PG/N=2.
FIG. 8 illustrates the performance characteristic for when E_b/η=15 dB. With this bit energy to noise ratio, two iterations of the interference canceller can yield 6 dB improvement for PG/N=2.
FIG. 9 illustrates the performance characteristic for when E_b/η=20 dB. With this bit energy to noise ratio, two iterations of the interference canceller can yield 6 dB improvement for PG/N=2. Similarly, FIGS. 10 and 11 show that one iteration of the interference canceller can yield more than 10 dB improvement for PG/N=2.
The present invention may be extended to a plurality of interference cancellers. As shown in FIG. 12, a received spread-spectrum signal, R(t), is despread and detected by CDMA/DS detector 611. Each of the channels is represented as outputs O₀₁, O₀₂, O₀₃, . . . , O_0m. Thus, each output is a despread, spread-spectrum channel from a received spread-spectrum signal, R(t).
Each of the outputs of the CDMA/DS detector 611 is passed through a plurality of interference cancellers 612, 613, . . . , 614, which are serially connected. Each of the spread-spectrum channels passes through the interference canceling processes as discussed previously. The input to each interference canceller is attained by sampling and holding the output of the previous stage once per bit time. For channel i, the first interference canceller samples the output of the CDMA/DS detector at time t=T+τ_i. This value is held constant as the input until t=2T+τ_iat which point the next bit value is sample. Thus, the input waveforms to the interference canceller are estimates, dˆ_i(t−τ_i), of the original data waveform (d_i(t−τ_i), and the outputs are second estimates, dˆˆ_i(t−τ_i). The M spread-spectrum channel outputs O_0i, i=1, 2, . . . , M, are passed through interference canceller 612 to produce a new corresponding set of channel outputs O_1i, i=1, 2, . . . , M.
As shown in FIG. 13, the outputs of a particular spread-spectrum channel, which are at the output of each of the interference cancellers, may be combined. Accordingly, combiner 615 can combine the output of the first channel which is from CDMA/DS detector 611, and the output O₁₁from the first interference canceller 612, and the output O₂₁from the second interference canceller 613, through the output O_N1from the N^thinterference canceller 614. Each output to be combined is of the corresponding bit. Therefore “s” bit time delays is inserted for each O_s1. The combined outputs are then passed through the decision device 616. This can be done for each spread spectrum channel, and therefore designate the outputs of each of the combiners 615, 617, 619 as averaged outputs O₁for channel one, averaged output O₂for channel two, and averaged output O_Mfor channel M. Each of the averaged outputs are sequentially passed through decision device 616, decision device 618, and decision device 620. Preferably, the averaged outputs have multiplying factor c_jwhich may vary according to a particular design. In a preferred embodiment, c_j=½^j. This allows the outputs of the various interference cancellers to be combined in a particular manner.
FIGS. 14-17 illustrate simulation performance characteristics for the arrangement of FIGS. 12 and 13. FIGS. 14-17 are for asynchronous channel (relative time delays are uniformly distributed between 0 and bit time, T), processing gain of 100, all users have equal powers, and thermal signal to noise ratio (E_bN of 30 dB). Length 8191 Gold codes are used for the PN sequences.
In FIG. 14, performance characteristic of each of the output stages of FIG. 12 is shown. Thus, S0 represents the BER performance at the output of CDMA/DS detector 611, S1 represents the BER performance at the output of interference canceller 612, S2 represents the BER performance at the output of interference canceller 613, etc. No combining of the outputs of the interference cancellers are used in determining the performance characteristic shown in FIG. 14. Instead, the performance characteristic is for repetitively using interference cancellers. As a guideline, in each of the subsequent figures the output for each characteristic of CDMA/DS detector 611 is shown in each figure.
FIG. 15 shows the performance characteristic when the output of subsequent interference cancellers are combined. This is shown for a particular channel. Thus, curve S0 is the output of the CDMA/DS detector 611. Curve S1 represents the BER performance of the average of the outputs of CDMA/DS detector 611 and interference canceller 612. Here C₀=C₁=½C_j=0,j not equal to zero, one. Curve S2 represents the BER performance of the average output of interference canceller 613 and interference canceller 612. Curve S2 is determined using the combiner shown in FIG. 13. Here, C₁and C₂are set equal to ½ and all other C_jset to zero. Similarly, curve S3 is the performance of the output of a second and third interference canceller averaged together. Thus, curve S3 is the performance characteristic of the average between outputs of a second and third interference canceller. Curve S4 is the performance characteristic of the average output of a third and fourth interference canceller. Only two interference cancellers are taken at a time for determining a performance characteristic of an average output of those to particular interference cancellers.
FIG. 16 shows the regular outputs for the CDMA/DS detector 611, and a first and second interference canceller 612, 613. Additionally, the average output of the CDMA/DS detector 611 and the first interference canceller 612 is shown as S1 AVG. The BER performance of the average of the outputs of the first interference canceller 612 and the second interference canceller 613 is shown as the average output S2 AVG.
FIG. 17 shows performance characteristic correspondence for those of FIG. 16, but in terms of signal to-noise ratio in decibels (dB).
It will be apparent to those skilled in the art that various modifications can be made to the spread-spectrum CDMA interference canceller and method of the instant invention without departing from the scope or spirit of the invention, and it is intended that the present invention cover modifications and variations of the spread-spectrum CDMA interference canceller and method provided they come within the scope of the appended claims and their equivalents.

Claims

1. A method for recovering data transmitted over a plurality of channels employing wireless code division multiple access communication, comprising:

a) receiving the plurality of channels as a received signal, each channel associated with a code;

b) subtracting for each of the plurality of channels others of the plurality of channels from the received signal and despreading a result of that subtracting as data for that channel; and

c) respreading that channel despread signal with a respective channel code;

wherein the respreading channel code is aligned to a timing of the despread received signal.

2. The method of claim 1 wherein step (b) includes, for each channel:

despreading the received signal with the others channel codes;

respreading the despread others channel codes using the other channels codes; and

subtracting from the received signal the respread other channels.

3. The method of claim 2 wherein the despreading is performed by a mixer.

4. The method of claim 2 wherein the despreading is performed by a matched filter.