KR102673405B1 - ESS charger with ripple cancellation - Google Patents

Abstract

The present invention is a technology that supplies high-quality direct current through low power and inverse ripple function in a charging device that charges ESS using alternating current. The present invention enhances the safety of the ESS by eliminating the surge pulse factor generated from the PWM when the ESS (energy storage device) is fully charged, and thereby expands the charging capacity of the ESS.
The present invention for the above purpose,
A main power unit that outputs a voltage lower than the voltage required by the charging control system;
A charging system connected to receive charging power from the main power unit and an ESS unit that stores charging energy;
a supplementary power unit that boosts and regulates the low voltage of the main power unit to the voltage required for the charging system;
A ripple detection unit that detects ripple when the output voltage of the main power unit is a pulsating voltage including ripple;
A configuration comprising a reverse ripple function generator that generates an inverse ripple that is opposite to the ripple detected by the ripple detection unit,
The supplementary power unit is linked with the main power unit so that the voltage output from the main power unit is maintained at the set load voltage, and when the ripple is detected from the ripple detection unit, the supplementary power unit detects the reverse ripple from the reverse ripple function generator. A non-ripple charging device configured to generate a pulsating current output by a function and generate a direct current voltage with the ripple canceled at the output terminal of the main power unit is disclosed.
According to the present invention, there are effects of minimizing losses consumed in power control, ultra-fast maximum power point tracking, strengthening battery safety from limb pulses, and expanding battery charging capacity.

Description

ESS charging device with ripple suppression function {ESS charger with ripple cancellation}

The present invention is a technology that supplies high-quality direct current through inverse ripple function control using low power in a charging device that charges ESS using alternating current. The present invention enhances the safety of the ESS by eliminating the surge pulse factor generated from the PWM when the ESS (energy storage device) is fully charged, and maintains the pure direct current component required by the communication power supply even during charging, and further improves the ESS's Expand charging capacity.

ESS is an energy storage device that is useful for factories or homes in regions or countries where power conditions are poor. Energy is mainly stored during times when power is supplied or late at night when power rates are low, and then discharged and used during times when power rates are high or during power outages.

Figure 1 is a block diagram showing a general charging control system. The main power obtained from the AC rectifier (1) is supplied to the battery (ESS, 2) through a charger (charge controller; 3) while changing the setting to the required voltage for each charging stage. The load end (4) is directly connected to the ESS in parallel or connected through the load end terminal of the charger.

Figure 1 depicts the input voltage supplied to the charger 3 as VP2 and the charger output voltage as VP1. Figure 1 depicts the AC power supply (1-3) in the form of a general sine wave (1000-1) and when it is full-wave rectified. It includes the output waveform (1000-2) of the rectifier (1-1) and the pulsating waveform (1000-3) when supplying current to an appropriate load after filtering it into direct current by the smoothing capacitor (1-2).

In Figure 1, the charging controller 3 receives the output of the main power unit 1 in the form of a pulsating current (1000-3) and outputs a stable direct current voltage (1000-4). At this time, in order to obtain a high-quality direct current voltage, the voltage set as the lower limit (1000-4) in (C) of FIG. 1 should not be exceeded. If this level is exceeded, ripple (1000-3), which is the alternating current component of pulsating voltage, is supplied to the ESS, so this ripple may cause surge pulse problems. Additionally, this ripple causes noise problems in the power supply of communication power supplies or audio devices.

In Figure 1, (1-3) is a transformer, (1-2) is a semiconductor type rectifier element made of a diode or FET, and 1-1 is a filtering device that compensates for the breaking point in (B) with the charging time constant. It is a capacitor.

In Figure 1, the charging controller can be configured as an analog regulator or a digital charging controller using PWM control. In the case of an analog regulator, the voltage difference between (VP2 - VP1) acts as input/output loss and causes heat generation, so the analog method is not particularly preferred for large-capacity charging other than for communication or audio devices that require precision.

In comparison, the PWM control method has relatively small losses between input and output, but due to its inherent characteristic (not shown) of interrupting power at short time intervals when charging is completed, pulse-shaped PWM noise is generated, especially as shown in (Rn) in Figure 2. Surge pulses in the indicated full charge area may cause adverse effects. Even if the voltage supplied to the ESS is constant, as it approaches full charge and the charging current gradually decreases, the input voltage (VP2) is controlled with a pulse width of a narrow duty ratio to prevent it from flowing to the load end (VP1), which ultimately narrows the pulse. It becomes a vicious cycle in which a larger surge voltage is created.

As fires in ESS occur frequently, relevant organizations have restricted ESS charging to 80% of maximum capacity, which proves that PWM noise increases from the point it reaches 80%. If PWM noise can be fundamentally eliminated, ESS charging can be expected to expand to a high level of over 80%, and more preferably up to 95%.

The reason why PWM noise causes problems or heat generation in analog chargers is because PWM control or regulation is performed on the entire input voltage (VP2).

The present invention was conceived as an alternative to this, and in particular, fundamentally solves the problem of heat generation through a configuration that does not control the input voltage (VP2), and further provides offset control and surge pulse for the corresponding ripple portion when ripple occurs. A technology to expand the safety and performance of ESS is disclosed by blocking ESS.

The present inventor has invented a power pump, which is the principle of leverage in the solar energy field. The present invention is an idea to obtain new configurations and effects by applying this power pump to AC power, which is a heterogeneous technology. This makes it possible to expand the charging capacity of the ESS by strengthening safety against PWM pulses that cause surges.

(1) KR 1020200089557 (2020.07.20.) (2) KR 1020190019077 (2019.02.19.) (3) KR 1020190094849 (2019.08.05.) (4) KR 1020200039764 (2020.04.01.) (5) KR 1020190094844 (2019.08.05.) (6) KR 1020150008277 (2015.01.16.) (7) KR 1020180001666 (2018.01.05.) (8) KR 1020170153635 (2017.11.17.) (9) KR 1020180154303 (2018.12.04.) (10) KR 1020190170458 (2019.12.19. (11) KR 1020200038300 (2020.03.30.) (12) KR 1020210003544 (2021.01.11.) (13) KR 10-2021-0172644(2021.12.06.) (14) KR 10-2021-0176358(2021.12.10.) (15) KR 10-2022-0013866(2022.02.02.) (16) KR 10-2022-0017217(2022.02.09.) (17) KR 10-2022-0041425(2022.04.03.)

The first purpose of the present invention is to disclose a technology that minimizes the operation loss of the charge controller by minimizing the difference between the voltage input to the charge controller and the voltage output from the charge controller.

The second purpose of the present invention is to obtain a complete DC output by smoothing the ripple output from the main power supply, and to disclose a technology that minimizes the power control range, that is, loss factors, even in the smoothing configuration.

The third purpose of the present invention is to initiate a technical configuration that enhances safety from ESS explosion by immediately responding to the occurrence of pulse voltage in the ESS charging system.

The present invention for the above purpose,

A main power unit that outputs a voltage lower than the voltage required by the charging control system;

A charging system connected to receive charging power from the main power unit and an ESS unit that stores charging energy;

a supplemental power unit that boosts and regulates the low voltage of the main power unit to the voltage required for the charging system;

A ripple detection unit that detects ripple when the output voltage of the main power unit is a pulsating voltage including ripple;

A configuration that includes a reverse ripple function generator that generates a reverse-phase ripple opposite to the ripple detected by the ripple detection unit,

The supplementary power unit is linked with the main power unit so that the voltage output from the main power unit is maintained at the set load voltage, and when the ripple is detected from the ripple detection unit, the supplementary power unit detects the reverse ripple from the reverse ripple function generator. Disclosed is an ESS charging device characterized in that it is configured to generate a pulsating current output by a function and generate a direct current voltage in which the ripple is canceled at the anode of the main power unit.

Here, the supplemental power unit may further include an interlocking configuration of a pulse detection control unit that controls the boost supply to be limited when a surge pulse voltage is detected in the charging system (charge control unit and EES unit).

In addition, the supplementary power supply is supplied from an external power source other than the main power supply, and an active current detection unit is linked to the supply path, so as to track the maximum value of the active current supplied to the load with the remainder consumed in the operation of the supplemental power supply, a maximum power tracking configuration, Alternatively, some of the power of the main power supply is fed back to supplement the voltage of the main power supply, and an active current detection unit is linked to the feedback path to determine the maximum value of the active current supplied to the load with the remainder consumed in the operation of the supplemental power supply. It may include a maximum power tracking configuration.

The present invention discloses a technical configuration in which the supplemental power unit optimally matches the main power unit and the load end and further maintains operation at the power point of maximum efficiency, which is near the resonance point of the transformer. The supplementary power supply unit of the present invention includes technology for tracking the maximum power point at ultra-high speed through a current congestion control function.

According to the present invention, the main power unit, which shares most of the load power, supplies rectified power to the load as is, and the supplementary power unit is responsible for regulating voltage and ripple cancellation in a small range, thereby minimizing losses due to control. There is.

According to the present invention, the difference between the input voltage and output voltage of the charge controller is eliminated to a negligible level by inverse ripple function control that cancels out the ripple, and further, it is possible to obtain high quality pure direct current components through such technology.

According to the present invention, ultra-fast maximum power point tracking technology can be obtained, and furthermore, it is possible to significantly expand charging capacity while strengthening safety from ESS explosion by blocking the pulse voltage generated when ESS charging is completed.

According to the present invention, it is possible to secure high-quality power for communication or audio devices through power control with a small control range.

Figure 1 is a block diagram showing a conventional ESS charging system.
Figure 2 is a battery current flow graph showing how the charging current flow of the ESS varies by stage and when a surge pulse is generated in the process.
Figure 3 is a block diagram schematically expressing the position of each waveform in a conventional charging system. It indicates that a surge pulse is generated when ripple and PWM control are mixed.
Figure 4 is a block diagram of one embodiment of the present invention. It shows the principle and circuit of obtaining a pure direct current component by combining the pulsating current voltage with ripple in the main power supply and the pulsating current voltage with reverse ripple in the supplemental power supply.
FIG. 5 is a block diagram showing an example of how the concept of FIG. 4 is achieved by specific combination of components. FIG. 5 shows an example in which the supplementary power unit in FIG. 4 operates by receiving feedback from a portion of the output power of the main power unit.
Figure 6 is a block diagram of one embodiment to explain the maximum power tracking function of the present invention.
FIG. 7 is a graph explaining the maximum power tracking function of the supplementary power unit, which is an example of FIG. 6, using the duty ratio control principle.
FIG. 8 is a flowchart explaining the principle of controlling the maximum power of the supplementary power unit, which is an example of FIG. 6, by current runaway, using an algorithm.
Figures 9 and 10 are block diagrams and algorithm flowcharts showing an example of a charging system that maintains a set output voltage while suppressing the output voltage when a surge pulse is detected in the supplemental power supply unit of the present invention.
Figure 11 is a voltage-current-power curve diagram illustrating the resonance point of the transformer output to explain the maximum power tracking operation of the present invention.

The present invention may have various embodiments in addition to those described below, and specific embodiments will be illustrated in the drawings and described in detail in the detailed description. However, since this is not intended to limit the present invention to specific embodiments, the configuration disclosed below should be understood to include all changes, equivalents, and substitutes included in the spirit and technical scope of the present invention. While describing each drawing, similar reference numerals are used for similar components, but for example, terms such as first, second, first, second, etc. are used only for the purpose of distinguishing one component from other components. However, these components should not be understood as being limited by labeling them as first, second, first, second, etc. The above terms may be used to refer to a first component as a second component without departing from the scope of the present invention, and in the same principle, the second component may also be referred to as a first component. The same goes for the first and second, and the terms ‘first’ and ‘next’ are also the same.

Under this principle, embodiments according to the present invention will be described in detail below with reference to the attached drawings. The objects and features of the present invention will become more clear through the following detailed description.

Figure 3 is a block diagram schematically illustrating the conventional charging controller 3 and its surrounding components.

Referring to Figure 3, the (A) waveform is output from the secondary coil output of the transformer (1-3), the (B) waveform, for example, full-wave rectified, is output from the rectifier (1-1), and the smoothing unit ( You will understand that when power is supplied to the load in 1-2), a ripple-shaped waveform (1000-3; C) in which the voltage decreases over time from the maximum voltage is output.

Here, (1000-4) is the DC voltage level standard that limits the ripple (1000-3) from being supplied to the output. As a result, from the (1000-4) level to the peak of (1000-3), for example, 1.414 A 2x voltage difference occurs, and when this 0.4x difference is regulated in the charge controller, it becomes the subject of heat generation. (0.414 times is an example of the difference between P-P voltage and rms voltage. Also, Figure 3 shows a rotary transformer as an example, but if insulation is not important, an autotransformer may be applied.)

Figures 3 (D) and (E) mainly show an example of the waveform that appears when the charge controller is operated by PWM control, and (1000-5) in Figures 3 (D) and (E) indicates battery charging. It shows the surge pulse waveform by PWM that appears when completed.

If the smoothing circuit capacitor (1-2) cannot sufficiently handle the load current, the ripple voltage (△r) in Figure 3 (D) increases in size, and the capacity of the coil (1-3) of the transformer or the diode of the rectifier ( 1-1) If capacity is insufficient, the range of △V fluctuation becomes larger, as shown in (E) of Figure 3. Anyway, in any case, it acts as a ripple on the load, and in order to prevent this ripple from flowing to the load, ripples with a level higher than (1000-4) must be cut off in the regulator (3).

Surge pulse is a pulse noise that is particularly problematic when the current supplied to the battery is intermittently limited by PWM in the (Rn) section of FIG. 2, that is, in a fully charged state. Since these surge pulses can cause fire or explosion, especially in the case of lithium-ion batteries, it is generally recommended to charge the ESS at a charge rate of about 80%, which is a level at which such pulses do not occur.

Figure 4 is a block diagram conceptually explaining the principle of the present invention, and Figure 5 is a block diagram showing one example of various configurations in which the present invention can be implemented. Its main composition is

A main power unit (1) that outputs a voltage lower than the voltage required by the charging control system;

A charging system connected to receive charging power from the main power unit and an ESS unit (2) that stores charging energy;

A supplementary power supply unit (30) that boosts and regulates the low voltage of the main power supply to the voltage required for the charging system;

A ripple detection unit 31 that detects ripple when the output voltage of the main power unit is a pulsating voltage including ripple;

A configuration comprising a reverse ripple function generator (32) that generates a reverse-phase ripple opposite to the ripple detected by the ripple detection unit,

The supplementary power unit is linked with the main power unit so that the voltage output from the main power unit is maintained at the set load voltage, and when the ripple is detected from the ripple detection unit, the supplementary power unit detects the reverse ripple from the reverse ripple function generator. An interlocking configuration is disclosed in which a pulsating current voltage output is generated by a function, and a direct current voltage in which the ripple is canceled is generated at the output terminal where the output of the main power unit and the supplementary power unit are combined.

The supplemental power unit 30 may further include a pulse detection control unit (60 in FIG. 9) that controls the boost supply to be limited when a surge pulse voltage is detected in the charging system (charge control unit and EES unit). You can.

The supplementary power supply unit 30 of FIG. 4 can be supplied from an external power source (Buck (+)in), not shown, in addition to the main power supply unit 1.

Referring to FIG. 5, the supplementary power supply unit 30 may feed back a portion of the power of the main power supply unit 1 to perform feedback control to supplement the voltage of the main power supply unit. The feedback path may further include a connection configuration of a maximum power tracking unit 40 linked to the active current detection unit IP3. The maximum power tracking unit 40 performs a function of tracking the remaining active current (IP3) supplied to the load to the maximum value after being consumed in the operation of the supplemental power unit 30.

According to the same principle, the supplementary power supply is supplied from an external power source other than the main power supply, and the active current detection unit (IP3) is linked to the supply path, so that the maximum active current (IP3) supplied to the load with the remainder consumed in the operation of the supplementary power supply is supplied. It may further include configuration for tracking values.

First, the operation of Figure 4 will be explained.

Rectifying sine wave (1000-1) commercial power can generate ripple (△r) equivalent to the difference between the maximum value (p-p; 1000-3) and the effective value (rms; 1000-4). This ripple disappears when the load current is 0 and its output voltage becomes the same as the maximum voltage of the sine wave. However, if the current flowing to the load terminal is consumed or the time constant of the smoothing circuit including the smoothing capacitor (1-1) changes, it may occur periodically or irregularly. A ripple occurs in the form of The ripple at this time is (G).

If the supplementary power unit 30 connected in series with the main power unit 1 generates a ripple with a function opposite to this ripple (this is defined as an inverse ripple function) and is connected to the main power unit so that the ripples cancel each other out (Figure 4) (Refer to H)) If so, the signal of the original ripple (E-2) and the corresponding reverse ripple (E-1) of the opposite phase is transmitted to the output terminal (VP1) where the main power unit (1) and the supplementary power unit (30) are combined. They are offset and combined to output a pure direct current component voltage such as (E-3) (1000-4).

In other words, for example, in a configuration in which the main power unit shares 80% of the total power output and the supplementary power unit shares 20% in series, if a pure direct current component is obtained through the inverse ripple function output of the supplementary power unit, it is the loss necessary for conversion (control). is reduced to 20/100. Figure 5 of the present invention is an embodiment that specifically realizes this.

Each component and its interlocking actions will be described with reference to FIG. 5 .

The main power unit (1) basically outputs a voltage lower than the voltage required by the charging control system. The reason for setting it to a low voltage is to establish a voltage drop that can supply power to the charging system when the supplemental power unit intervenes and boosts the voltage, but also to block the current or power flowing to the charging system by detecting surge pulses or overcharge. When doing this, the output of the supplementary power supply is battery-powered to prevent the voltage drop from occurring. However, it does not necessarily have to be low to operate, so it is not necessarily limited to low voltage. For example, a configuration that clamps ripples may also be considered.

The ESS unit 2 includes a charging system connected to receive charging power from the main power unit and a battery that stores charging energy. In the case of lithium-ion batteries, it is desirable to include a battery management system (BMS) in the charging system. This BMS may include a configuration that balances the voltage of each battery terminal when a plurality of batteries are assembled in series or parallel and further remotely monitors them.

The supplemental power unit 30 is a component that boosts and regulates the low voltage of the main power unit 1 to the voltage required for the charging system.

The supplementary power unit may be supplied with operating power through feedback power from the main power unit or may be operated with power supplied from a separate, independent auxiliary power source. Here, independent auxiliary power means that a lottery-type leakage transformer has an additional winding and may be direct current power rectified from that winding. In addition, there can be a variety of independent auxiliary power sources, such as batteries and renewable energy sources.

The ripple detection unit 31 functions to detect ripple voltage when it is generated in the charging system. Simply put, it includes a configuration that detects and extracts only the alternating current component from the pulsating voltage that includes the alternating current component in the direct current component. For example, it may be a configuration that extracts and detects signals of alternating current components by connecting capacitors in series.

The inverse ripple function generator 32 uses the AC signal extracted from the ripple detection unit 31 to generate a ripple signal of the corresponding inverse function. The inverse ripple function includes a configuration that generates a signal of inverse phase by detecting the temporal change and height of the alternating current component included in the pulsation as a function.

As an example, by using the inverting (-) input of an operational amplifier, an inverse ripple function can be easily created by interpreting the ripple signal in reverse. Additionally, it can be encoded with an inverse ripple function using the microcomputer's sampling function. This can also be utilized by modeling the ripple pattern that appears in the periodic characteristics of commercial power 60Hz. The pattern modeling at this time may be a forward or ground control that matches the phase of the ripple signal coming in the next cycle.

The set voltage detection unit 33 is a component that sets the required voltage at the load end. For example, if the ESS is lithium-ion series 24V, it is set to 29.2V. These settings may include configurations that are automatically set by detecting the battery voltage and type by the microcomputer.

The supplementary power supply unit 30 is a buck converter in one embodiment of the present invention (in addition, various converter series such as buck-boost, boost, sepic, zeta, flyback, etc. can be applied) and supplies some current of the power of the main power supply. It can be implemented in a configuration that receives the voltage and feeds it back to the main power supply at a lower voltage.

At this time, since control by the inverse ripple function generator 32 and the set voltage detection unit 33 is applied to the feedback voltage output, the supplementary power supply operates in the range where the total output voltage (VP1) is maintained at the required voltage of the load end. The output voltage (VP3) controlled by the control signal (△-V) generated by the inverse ripple function generator 32 is generated. Therefore, even if ripple (△V) is included in (VP2), a pure direct current component with the ripple canceled by the control signal (△-V) can be obtained in (VP1).

By this principle, (VP1) can obtain a pure direct current component voltage of the optimal potential that is neither higher nor lower than the voltage required at the load end.

If we go back to Figure 4 and summarize conceptually,

There is a pulsating component, ΔV, in VP2 in Figure 4, and its height can be up to 1.4 times depending on the consumption of load power (difference between the maximum value of the sine wave and the effective value (rms)). In the present invention, this is defined as △V, and the inverse ripple function corresponding to the reverse direction is defined as △-V. In Figure 4, △V is (G), and △-V by the inverse function is (F). Since they are out-of-phase signals, if (F) and (G) are canceled in series on the same time axis, the ripple generated in the main power supply is offset by the inverse ripple function of the supplementary power supply, and the power supplied to the battery becomes pure direct current (E-3). This principle is depicted in overlapping graphs in (H) of Figure 4.

In Figure 4, (H) is an inverted ripple signal (E-1) generated by the inverse ripple function generator in response to (E-2), whose height of the ripple varies depending on the current consumption of the load end, and pure direct current voltage (E-3) that cancel each other out as they are combined.

In short, even without the conventional charge controller (3), it is possible to adjust and send only the necessary voltage to the load ends (2, 4) through control of the supplemental power unit (30), and as a result, the voltage that originally acted as a loss in the charge controller (3) can be adjusted and sent. △V disappears.

However, even in the case of the present invention, there will be a conversion loss in which the supplementary power unit 30 handles the output, but the supplementary power unit has a significantly lower contribution to offset the ripple compared to the load power, for example, a 20/10 contribution, so the conversion loss The loss is reduced by that ratio.

The present invention supplies the entire output voltage of the main power supply up to its peak voltage to the load stage, thereby significantly increasing power efficiency. Therefore, according to the present invention, the difference between peak power and real power is eliminated, and accordingly, the important effect of eliminating PWM-controlled surge pulses generated due to peak voltage can be obtained. According to the present invention, even if the charging capacity is increased to 100%, there is no reason to generate a surge pulse.

In addition to this, the present invention can be further connected to a pulse detection control unit 60 that controls the boost supply to be limited when a surge pulse is detected in the charging control unit and the EES unit, which are the charging system, and in this case, the pulse detection control unit can be connected to the pulse detection control unit in the safety situation as above. This is to prepare for PWM noise that may occur when charging is completed. This will be described later in Figure 9.

Furthermore, by adding the function of the maximum power tracking unit that acts as a current runaway control to the inverse ripple function generator of the present invention, it becomes possible to automatically track the maximum power point without damaging the resonance point of the transformer. This has a unique function of eliminating ripple while operating the transformer at maximum efficiency in a configuration using a commercial power transformer.

Hereinafter, the maximum power tracking unit of the present invention that achieves this will be described in detail with reference to FIGS. 5 and 6.

As an example, the supplementary power unit 30 of FIG. 5 is a configuration that receives operating power feedback from the main power source,

A main power supply unit (1) powered by a transformer;

Battery or/and load end (2, 4);

A supplementary power supply unit (30) connected between the main power supply and the load terminal to adjust the output voltage;

An active current detection unit (IP3) that detects the active current supplied to the battery system or the active current supplied to the load terminal connected to the battery system;

A current runaway control unit (40) that causes the current of the main power supply to runaway in a range where the active current detected by the active current detection unit increases,

The supplementary power supply unit 30 is configured to link the first input terminal (X), the second input/output terminal (Y), and the third output terminal (Z) between the main power supply (1) and the load terminal (4), It includes a configuration in which the output voltage (VP3) of the supplementary power unit is adjusted within the maximum power (Vmp) maintenance range of the main power unit (1) by feeding back the output voltage to one electrode (-) of

The current congestion control unit 40 controls the current of the main power supply so that the active current IP3 maintains an active current value corresponding to the maximum power even if the voltage at the load end 4 is higher than the maximum power voltage Vmp. It also functions as a maximum power tracking unit that controls the main power supply to maintain the maximum power range.

In the configuration of Figure 5,

The main power unit (1) supplies operating power from the transformer (1-3). Since the transformer can achieve maximum efficiency when supplying power according to its resonance characteristics, the present invention includes a maximum power tracking configuration that operates at the resonance point where the current flowing to the load is maximized while the load voltage is within a certain range. However, the overall configuration of the present invention is not limited to necessarily including this configuration.

The supplementary power unit 30 feeds back the output voltage VP3 to one electrode of the main power unit 1 to generate a voltage VP1 that is the sum of the output voltages of the main power unit and the supplemental power unit. As an example of the circuit configuration, the supplementary power unit shown in FIG. 5 connects the first input terminal (X) and the second input/output terminal (Y) through a power supply path that receives power from the main power supply unit, and the second It will be implemented in a configuration in which the output of the supplementary power supply is fed back to one electrode of the main power supply through the input/output terminal (Y), and the combined voltage of the output of the main power supply and the supplemental power supply is output to the load terminal, which is the connection point of the third output terminal (Z). You can. This configuration corresponds to a configuration in which a supplemental power supply is connected between the cathode of the main power supply and the cathode of the load end, but is not limited to this. For example, the supplementary power supply unit 30 may be connected to the positive electrode of the main power supply unit 1 by changing the polarity.

In this configuration of each input and output terminal of the supplementary power unit 30, the path flowing to the (Z) terminal, which is the third output terminal, includes the total current (IP2) produced in the main power unit 1 to the first input terminal (X) of the supplementary power unit. After subtracting the idling current (IP1) supplied, only the active current (IP3) supplied to the load ends flows. The active current detection unit (IP3) of the present invention detects this current and connects it with the current runaway control unit 40, which will be described later, to maintain the transformer in a resonance state and achieve a balance in supplying appropriate power to the load.

Here, the transformer produces maximum efficiency when in a resonance state, and if the load voltage is constant, the effective current value also becomes maximum when the supplemental power supply is operated at maximum power output. Therefore, maximum power tracking is, for example, the effective current value above. It can be implemented in a configuration that tracks the maximum detection value of the current detection unit (IP3).

The active current detection unit (IP3) can be linked to detect the current flowing in the resistor using the voltage drop method, amplify it with an operational amplifier, and then supply it to the current runaway control unit as an active current control signal. Here, the voltage detection method using resistance can be replaced by the magnetic induction method using a Hall sensor. The magnetic induction method has the advantage of being able to provide insulation. Of course, in the case of voltage detection, using a photocoupler, etc., it is possible to detect voltage or current that changes in an insulated state.

In FIG. 5, reference numeral 30-6 is a switch that operates and stops the supplemental power unit as needed.

The current runaway control unit 40 controls the supplementary power unit 30 to quickly increase or decrease the output exponentially when it generates output.

Here, runaway control means that the supplementary power unit squeezes the voltage (VP2) of the main power unit (1) connected between the load end (4) and both ends of the supplementary power unit (30) so that the maximum current flows from the transformer (1-3). However, it means increasing the output of the supplemental power supply at an exponential rate until the desired current value is reached.

Through this current runaway control, as soon as the control signal from the inverse ripple function generator is supplied, the supplementary power unit can generate the output voltage as is the control signal by the inverse ripple function, and furthermore, the maximum power that does not disturb the resonance point of the transformer. It is possible to detect a decrease in active current at that point and maintain the output voltage at that point. Therefore, in the present invention, the current congestion control unit can also serve as a maximum power tracking function.

Figure 6 is a block diagram showing an example of the current congestion control unit 40.

Referring to FIG. 6, the first input terminal (a) of the current runaway control unit is connected to detect the voltage change value, and the second input terminal (b) is connected to detect the effective current change value (IP3). The voltage change value means that the supplementary power output voltage (VP3), main power voltage (VP2), or summation voltage (VP1) is detected as a relative change value.

These first input terminals (a) and second input terminals (b) are connected to the rising current congestion command unit 40-3 and the falling current congestion command unit 40-4 via the instantaneous edge detection units 40-1 and 40-2. ) is supplied. The edge detection result determines whether to command a rise or a fall command in the logic circuit, and the command proceeds as a command signal in the form of a current runaway that linearly increases or decreases until the desired result is reached. . Here, the logic circuit may be a combination of gates or a programmed gate combination using an FPGA. It may be a program using a microcomputer.

The command signal may be output as a pulse or encoded signal through the mixing circuit 40-7.

The command signal that has passed through the mixing circuit (40-7) and the waveform shaping circuit (40-8) is supplied as a control signal to the supplementary power supply unit (30), so the rising current congestion command unit (40-3) and the falling current congestion command unit The maximum power point is tracked as the balance corresponding to the point where (40-4) is balanced.

Here, the instantaneous edge detection unit (40-1, 402) is a component that determines just before and immediately after as relative values. This instantaneous edge detection makes it possible to generate an inverse ripple function that immediately responds to the ripple waveform in the present invention.

The rising current runaway command unit 40-3 detects the presence or absence of the ripple voltage through the first input terminal (a), and if it detects the ripple voltage, it immediately moves the supplementary power unit 30 in the opposite direction to increase the sum voltage ( It cancels out the ripple voltage in VP1). The falling current runaway command unit 40-4 is configured to lower the rising current runaway command unit 40-3 so as not to excessively increase the output of the supplemental power unit 30, and in particular, the effective maximum detected from the active current detection unit IP3. It is a component that operates immediately at the point when the current falls, causing a reaction to stop or offset the action of the rising current runaway command unit 40-3. Here, if the rising runaway is excessive, the main power supply unit (1) is excessively compressed, overloading the transformer, and this destroys the resonance point of the transformer, ultimately reducing the effective current (IP3). The falling runaway command stays at the neutral point and the summed voltage ( VP1) works in the opposite direction paired with the rising current runaway command to maintain a balance that maintains the appropriate range and resonance point.

Figure 7 is a graph showing the signal characteristics of the rising current runaway command unit 40-3 and the falling current runaway command unit 40-4 in the concept of duty ratio control.

Referring to Figures 7 (A) and (B), the output of the rising current congestion command unit 40-3 and the output of the falling current congestion command unit 40-4 are respectively the rising duty ratio signal 40-5. As the falling duty ratio signal 40-6, the rising signal outputs a wide duty ratio (40a) as a command to increase the voltage, and the falling signal outputs a narrow duty ratio (40c) signal as a command to lower the voltage. The average value (40b) is supplied as a control signal input to the supplemental power supply unit to compress or relieve the voltage of the main power supply unit.

When the voltage of the main power supply is squeezed, the load on the main power supply becomes heavier and the voltage decreases while the current increases. Conversely, when it is relaxed, the voltage increases while the current decreases. This action causes a decrease in the effective current centered on the resonance point. Since it has a , the supplementary power unit uses this to control the instantaneous current surge.

The duty ratio signal in FIG. 7 may remain in the on state until it reaches the maximum power point current when a rising current runaway command is given, and on the contrary, when a falling current runaway command is commanded, it may remain in the off state until it returns to the maximum power point current. Therefore, it is not necessarily composed of a repetitive duty ratio as shown in FIG. 7, but may be composed of an asynchronous duty ratio control signal that is generated depending on the case or freely determines the duty ratio width. Since this duty ratio is ultimately supplied as a control signal that operates the supplementary power unit 30, the current congestion control unit can be controlled by observing that the neutral point average signal of the rising or falling current congestion signal is supplied to the input of the supplementary power unit 30. You can infer whether it's working or not.

In short, according to the present invention, by making the duty ratio width 40a of FIG. 7 very large or repeatedly generating a relatively wide duty ratio, this becomes a rising current surge, and on the contrary, like the duty ratio of 40c, by continuing or repeating a narrow duty ratio. This can be used as a command to stop the falling current or rising current.

Figure 7(B) illustrates a case where the duty ratio is controlled by synchronizing with the same phase time. The operating principle is the same as (A).

The current runaway control unit 40 substantially integrates and performs the functions of the maximum power tracking unit. In particular, this function can include a fine adjustment role of comparing and canceling errors when an error occurs in the combination of ripple (△V) and reverse ripple (△-V) described above.

The photos attached to Figure 7 show current runaway command signals observed with an oscilloscope. In Photo 1, the uppermost trace waveform represents the duty ratio signal of the rising current runaway command, and the middle trace waveform represents the duty ratio signal of the falling current runaway command section. The pulsating waveform of the lowermost trace represents the control signal supplied to the supplemental power supply unit 30. Photo 1 was taken when the control signal was in balance while repeating rising and falling current surges, but even in this case, it appears that the load end becomes heavy and balance is maintained with a runaway signal when it sometimes deviates from balance.

Photo 2 of FIG. 7 shows the control of the supplemental power supply unit at the time of the initial current surge, and Photo 3 shows the brief rise or fall current surge occurring during the period when the supplementary power unit is operated.

The photos shown in FIG. 7 are when observed with an oscilloscope, but in addition, a duty ratio signal or a pulse-type signal can be observed using an LED lamp or various other means. The present invention may also include means for controlling or monitoring the supplemental power unit as a data signal according to a protocol.

Figure 8 is an algorithm flowchart logically explaining the overall operation of the current runaway command unit.

Referring to Figure 8, the operation of the current runaway control unit 40 of the present invention is,

[Step 1] Detect voltage changes and effective current changes (401, 402).

Here, it is desirable to detect VP1, VP2, and VP3 for voltage changes. Depending on the number of logical cases, they can be detected interchangeably.

[Step 2] Compare the instantaneous change values and control the output of the supplementary power unit in an upward direction when the actions that increase in the same direction are included (403, 404).

Here, it is desirable to apply detection of relative value changes just before and after the instantaneous change value.

[Step 3] Compare the instantaneous change values and control the output of the supplementary power unit in the downward direction if they increase or decrease in opposite directions (405, 406).

In step 3 above, step 405, which detects the instantaneous change value, refers to the difference between moving in opposite directions or not.

[Step 4] The above output control signal is smoothed with a filtering function and generated as a control output of the supplementary power supply (408, 107, 409, 50). According to one embodiment, this supplemental power supply control signal may be in analog form.

In summary, the current runaway command unit of the present invention can be configured to include the flow steps of Step 1, Step 2, Step 3, and Step 4 above. When each of the above steps operates in hardware, it is processed in real time without step distinction, and when implemented as software using a microcomputer, it can be processed in the above order or in the reversed order.

Figure 9 is a pulse detection control unit 60 that controls the supplementary power unit 30 of the present invention to suppress or block the output of the supplementary power unit when a surge pulse voltage is detected in the charging system (2; charging control unit and EES unit). A configuration is being disclosed.

Referring to FIG. 9, if ripple is supplied to the load end or noise resulting from PWM control is generated at the load end, the pulse detection unit 60-1 can detect this first and reduce the output of the supplemental power unit. there is. This reduction weakens the surge pulse, which can be a risk factor, while allowing the maximum power tracking unit 40 to achieve temporal synchronization. Staggered control may include leading or lagging control that matches the combined phase of the ripple and reverse ripple.

Surge pulses include the previously mentioned pulse noise generated in the charging path. Specifically, examples include arc noise generated due to poor contact in the circuit, PWM (pulse) noise generated from the charger, and spark arc noise generated from connectors such as the main power supply.

When a surge pulse is detected by the pulse detection unit, controlling the pulse detection control unit to weaken the output voltage of the supplementary power supply unit may include lowering the output of the supplementary power unit to the point where the surge pulse disappears.

When explaining the operation of the pulse detection control unit 60 with reference to FIG. 9,

In FIG. 9, since the pulse noise includes components of an alternating current signal, it is supplied to the operational amplifier 60-6 through the capacitor 60-1. Accordingly, the output of the operational amplifier 60-6 generates a negative polarity signal, and the output is suppressed through the diode 6-7 in a direction to weaken the output of the current runaway control unit 40. For example, by detecting a noise pulse caused by a PWM control signal generated when charging is completed, the function of the current runaway control unit 40 is urgently weakened when surge pulse noise is generated. When the surge pulse disappears during attenuation, the operational amplifier 60-6 returns the output to normal, and the current runaway control unit 40 operates normally as if the pulse detection control unit 60 is not present. A variable resistor for gain adjustment can be added to the input terminal of the operational amplifier 60-6.

Meanwhile, the set voltage detection control unit 61 functions to limit the maximum value of the direct current component or maintain the set voltage, for example, by setting the sum voltage VP1 higher than the voltage required at the load end 4. This may include lowering the output of the supplemental power unit 30 when the output is supplied. This function functions as a protection circuit to prevent excessive main power voltage rise. It can also be implemented as a control function to maintain VP1 in a set voltage range.

As a circuit simplification measure, the pulse detection control unit 60 and the set voltage detection unit 61 can be integrated. In this case, the value of the resistance (61-1) is sufficiently larger than the value of the resistance (60-2) so that the pulse detection control unit ( 60) can be configured to detect and control both direct current and alternating current.

FIG. 10 is an algorithm flowchart explaining in more detail the operation of each component shown in FIG. 9.

Referring to Figure 10,

[Step 540] Detection of active current (IP3) supplied to the load end (501-1), load end voltage detection (501-2), main power supply output voltage detection (501-3), or supplemental power supply output voltage detection (501) Detect at least one of -4). However, if only some of the steps below are selected, only one can be detected.

[Step 550] The pulse detection control unit 60 detects whether there is a surge pulse (503). If there is a surge pulse, the output of the supplementary power unit is suppressed or the supplementary power unit operation switch (30-6) is blocked (504).

[Step 560] Check whether the sum voltage (VP1) supplied to the load is higher than the set voltage required by the load (505). This is a safety function that limits the maximum voltage required at the load end. If the setting range is exceeded, the output of the supplementary power unit is lowered (506).

[Step 570] The summed voltage (VP1) is detected to determine whether it is higher than the previous voltage (506, 512). If it is judged to be higher than the previous time, it is considered to be the high point of the ripple and the supplementary voltage (VP3) is lowered (507) to offset it. If it is judged to be lower, it is considered to be the low point of the ripple and the supplementary voltage (VP3) is increased (513) to offset it.

[Step 580] In step 570 above, the supplementary voltage is lowered (507). If it is determined that the effective current (IP3) is higher than before, the supplementary voltage continues to be lowered (508, 509). On the contrary, if it is determined that the effective current (IP3) is lower than before due to the falling action (507), the supplementary voltage is reversed to rise (510, 511). Meanwhile, in step 570 above, the supplementary voltage is increased (513), and if it is determined that the effective current (IP3) is higher than before, the supplementary voltage continues to be increased (514, 515). On the contrary, if it is determined that the effective current IP3 is lower than before due to the rising action (513), the supplementary voltage is reversed to fall (516, 517).

[Comprehensive action] Step 570 is an action to cancel the ripple, and stem 580 is an action to track the maximum power point.

In other words, when the active current increases from the previous point (n-1), it is a phenomenon when the resonance point of the transformer is approached, and when the active current decreases from the previous point (n-1), it is inferred that it is a phenomenon when the resonance point is passed. Using the principle of Figure 10 of the present invention, ripple and maximum power tracking are achieved simultaneously.

Through this algorithm, the supplementary power unit intervenes to compensate for the insufficient voltage of the main power unit, matches the optimal load voltage, and further maintains operation at the power point of maximum efficiency, which is near the resonance point of the transformer. Since the supplemental power unit is controlled as a current runaway control unit, tracking the maximum power centered on this resonance point is directly in contact with the principle of ultra-high-speed control through the current runaway control unit.

Figure 11 (I) is an I-V curve and P-V curve graph for explaining resonance characteristics.

Referring to Figure 11 (I), the output voltage (VP2) of the main power unit (1) becomes 0V on the I-V curve, that is, the current becomes the maximum value (Isc) at the load end short voltage point (Vsc), and at this time, The power becomes 0. On the contrary, at the open-circuit voltage point (Voc) of the load side where the VP2 voltage is maximum, the current (Ioc) becomes 0 and the power becomes 0.

Maximum efficiency is achieved when the summed voltage (VP1) at the Pmax point that obtains the maximum output in Figure 11 matches the voltage required at the load end (4). In the present invention, this match is achieved by the supplementary voltage unit providing the optimal output voltage. This occurs at the point where VP2+VP3=VP1, that is, the effective resonance point. At voltages below Pmax, the transformer is in a tightly coupled state that overloads the transformer, making it impossible to obtain maximum power. At voltages above Pmax, the transformer is in a loosely coupled state where it cannot properly supply current to the load, making it impossible to obtain maximum power. .

Therefore, the ability to track the Pmax point at high speed becomes key, and this maximum power point can be achieved by tracking the maximum detection value of the active current detection unit (IP3). This sensing result can also be achieved with power sensing applying the concept of ‘VP1 x IP3’.

If we summarize the operations of Figures 10 and 11,

[Step 560] in FIG. 10 is a pulsating voltage including the reverse ripple signal (△-V) in the supplementary power supply unit to offset the ripple signal (△V) included in the main power supply voltage (VP2) in (H) of FIG. 11. This corresponds to the algorithm that outputs (VP3). In addition, [Step 570] of FIG. 10 corresponds to maximum power point tracking (△P), which detects the active current (IP3) in (I) of FIG. 11 and tracks the power of the Pmax point.

In the terms of the present invention,

Maximum power tracking means detecting the current flowing from the main power supply, but tracking the remaining active current, which offsets the current consumed by the supplemental power supply, to maintain the maximum value. This detection is in charge of the active current detection unit, but its execution is in charge of the current runaway control unit, which has an ultra-fast (e.g., real-time, approximately 3 seconds) response to simultaneously achieve ripple cancellation and maximum power tracking. In the present invention, these individual or simultaneous functional blocks are defined as an inverse ripple function control device.

At this time, maximum power tracking is, for example, when the change value of the main power supply voltage and the effective current change value increase together, the supplementary power supply increases the output voltage to operate the main power supply current in a runaway manner, and the change in the main power supply voltage When the value and the effective current change value increase or decrease inversely, the supplementary power unit reduces the output voltage and repeats feedback control to control the main power unit current to be released from runaway, finds the maximum power point, and then centers around the maximum power point. The output voltage of the supplemental power unit may be maintained or tracked.

The circuit configuration of the current runaway control unit of the present invention may include a logic circuit including a combination of at least one of AND, NAND, NOR, EXOR, and NOT, or may be achieved as a programming language using an FPGA chip. It can also be achieved through the configuration of the microcomputer and its program.

The output voltage of the supplemental power unit can be inferred whether the supplementary power unit is adjusted through observation of changes in voltage or ripple of at least one of analog direct current or pulsating current at the output terminal, and such observation may be configured with an LED or a probe of an oscilloscope. there is. Additionally, it can be configured as a check mechanism during mass production using tools such as jigs.

The supplemental power unit may include a configuration to set an upper limit output voltage to limit the maximum value of the voltage output from the main power unit. In this case, it is desirable to add it in package form to a specific main power supply.

The supplementary power supply system may be combined with a data communication node or server to monitor and remotely control at least one of the voltage, current, and power of the relevant and adjacent main power supplies, and thereby block and control the main power supply path. You can.

The supplementary power supply unit 30 can be operated in the same configuration as above or similar to that inferred from the claims of the present invention by connecting an external power source other than the main power supply unit and linking IP3 to the active current detection unit configuration on the same principle.

Instantaneous edge detection can be configured with a sample hold and comparison circuit using hardware. In the case of software using a microcomputer, sampling data can be made to correspond to this.

The mixing circuit can calculate the average of duty ratio signals of opposite polarity or calculate the value by averaging wide or narrow duty ratio signals based on 50%, and the charge pump connected to the rear of the mixing circuit provides smooth output of DC to supplement. It can be used as a control signal from the power supply or encoded with an encoder and used directly in the supplemental power supply, or converted back to the decoder in the supplemental power supply.

In the present invention, the generation of the asynchronous duty ratio signal applies the AND logic series to the rising command within the initial edge timing range that occurs when there is a change value in which the effective current flows, and the NOT logic is applied to the falling command at the time of the effective current decrease. By applying the OR logic series, it can include at least one asynchronous signal among PWM (Pulse Width Modulation), PPM (Pulse Position Modulation), PTM (Pulse Timing Modulation), and PFM (Pulse Forming Modulation) generated therefrom. there is.

Here, the asynchronous signal includes the current runaway command signal observed as an output voltage that momentarily changes at irregular intervals or at an irregular level depending on the load end or main power source environment.

In the present invention, effective current detection (IP3) can use a resistance sensor or a Hall sensor, and an insulation method using a photo coupler can also be additionally applied.

In terms of industrial usability, the configuration of the present invention can be implemented as a configuration in which the main power unit and the supplementary power unit are integrated, and is integrated and accommodated in at least one of a charging control device for charging the ESS, a distribution board, a junction box, or an inverter. It can be implemented as a structure.

Meanwhile, the components of the above-described embodiment can be easily understood from a process perspective. In other words, each component can be understood as a separate process. Additionally, the processes of the above-described embodiments can be easily understood from the perspective of the components of the device.

Additionally, the technical contents described above may be implemented in the form of program instructions that can be executed through various computer means and recorded on a computer-readable medium.

The computer-readable medium may include program instructions, data files, data structures, etc., singly or in combination. Program instructions recorded on the medium may be specially designed and configured for the embodiments or may be known and available to those skilled in the art of computer software. Examples of computer-readable recording media include magnetic media such as hard disks, floppy disks, and magnetic tapes, optical media such as CD-ROMs and DVDs, and magnetic media such as floptical disks. -Includes optical media (magneto-optical media) and hardware devices specifically configured to store and execute program instructions, such as ROM, RAM, flash memory, etc. Examples of program instructions include machine language code, such as that produced by a compiler, as well as high-level language code that can be executed by a computer using an interpreter, etc. A hardware device may be configured by combining one or more software modules or hardware chips to perform the operations of the embodiments.

The above-described embodiments of the present invention have been disclosed for illustrative purposes, and those skilled in the art will be able to make various modifications, changes, and additions within the spirit and scope of the present invention, and such modifications, changes, and additions will be possible. should be regarded as falling within the scope of the patent claims below.

Main power unit (1);
Rectification donation (1-1);
Smoothing capacitor (1-2);
Transformer section (1-3);
ESS, battery (2);
Charging control unit (3);
lower end (4);
Main power output voltage detection unit (VP2);
Charge controller output voltage detection unit (VP1);
Supplementary power supply output voltage detection unit (VP3);
Supplementary power unit (30);
Ripple detection unit (31);
Inverse ripple function generator (32);
Set voltage detection unit (33);
Maximum power tracking unit (40);
Supplementary power supply operating current (IP1);
The remaining active current detection unit (IP3) after deducting the power consumption of the supplementary power unit;
Buck converter (30-1, 30-2, 30-3, 30-4, 30-5);
Buck converter operation switch (30-6);
Total output current of the main power supply (IP2);
Active current detection unit (IP3);
Voltage deviation (△V, △-V);
Current deviation (△I);
Power deviation (△W);
Current runaway control unit 40;
Instantaneous edge detection unit (40-1, 40-2);
Rising current runaway command unit (40-3);
Rising current runaway stop command unit (40-4);
Mixing balance unit (40-7);
Filtering unit (40-7, 40-8);
Pulse detection unit (60-3);
Pulse detection control unit 60;
AC voltage limit unit (60-1);
DC voltage limit unit (60-4);
bypass section (30-3);
Coil (30-4);
capacitor (30-5);
MOSFET(30-1);

Claims (7)

A main power unit that outputs a voltage lower than the voltage required by the charging control system;
A charging system connected to receive charging power from the main power unit and an ESS unit that stores charging energy;
a supplemental power unit that boosts and regulates the low voltage of the main power unit to the voltage required for the charging system;
A ripple detection unit that detects ripple when the output voltage of the main power unit is a pulsating voltage including ripple;
A configuration that includes a reverse ripple function generator that generates a reverse-phase ripple opposite to the ripple detected by the ripple detection unit,
The supplementary power unit is linked with the main power unit so that the voltage output from the main power unit is maintained at the set load voltage, and when the ripple is detected from the ripple detection unit, the supplementary power unit detects the reverse ripple from the reverse ripple function generator. By generating an output by a function, the output terminal of the main power unit and the supplementary power unit are combined to generate a direct current voltage with the ripple canceled out,
The ESS charging device further includes a pulse detection control unit in the supplementary power unit that controls the boost supply of the supplementary power unit to limit when a surge pulse voltage is detected in the charging system. delete According to paragraph 1,
The supplemental power supply unit is an ESS charging device characterized in that it includes a feedback control configuration to supplement the voltage of the main power unit by feeding back a portion of the power of the main power unit. A main power unit that outputs a voltage lower than the voltage required by the charging control system;
A charging system connected to receive charging power from the main power unit and an ESS unit that stores charging energy;
a supplemental power unit that boosts and regulates the low voltage of the main power unit to the voltage required for the charging system;
A ripple detection unit that detects ripple when the output voltage of the main power unit is a pulsating voltage including ripple;
A configuration that includes a reverse ripple function generator that generates a reverse-phase ripple opposite to the ripple detected by the ripple detection unit,
The supplementary power unit is linked with the main power unit so that the voltage output from the main power unit is maintained at the set load voltage, and when the ripple is detected from the ripple detection unit, the supplementary power unit detects the reverse ripple from the reverse ripple function generator. By generating an output by a function, the output terminal of the main power unit and the supplementary power unit are combined to generate a direct current voltage with the ripple canceled out,
The supplementary power supply is supplied from an external power source other than the main power supply, and an active current detection unit is linked to the supply path to form a maximum power tracking unit that tracks the maximum value of the active current supplied to the load with the remainder consumed in the operation of the supplementary power supply. ESS charging device including more. A main power unit that outputs a voltage lower than the voltage required by the charging control system;
A charging system connected to receive charging power from the main power unit and an ESS unit that stores charging energy;
a supplementary power unit that boosts and regulates the low voltage of the main power unit to the voltage required for the charging system;
A ripple detection unit that detects ripple when the output voltage of the main power unit is a pulsating voltage including ripple;
A configuration that includes a reverse ripple function generator that generates a reverse-phase ripple opposite to the ripple detected by the ripple detection unit,
The supplementary power unit is linked with the main power unit so that the voltage output from the main power unit is maintained at the set load voltage, and when the ripple is detected from the ripple detection unit, the supplementary power unit detects the reverse ripple from the reverse ripple function generator. By generating an output by a function, the output terminal of the main power unit and the supplementary power unit are combined to generate a direct current voltage with the ripple canceled out,
The supplementary power unit detects the active current supplied to the load end and further includes a configuration that links the active current detection unit and the current congestion control unit to maintain the combination of the main power unit and the load end at maximum power tracking. Device. In the ESS charging system configuration, which charges the ESS with the summed voltage of the main power unit and supplementary power unit linked in series,
When the output voltage of the main power unit is a pulsating voltage including ripple, the ripple is extracted and detected, and a reverse-phase ripple opposite to the extracted and detected ripple is generated, and at least one of the main power unit or the supplementary power unit is used to generate the reverse-phase ripple. Controlling the total voltage to generate a direct current voltage with the ripple canceled out,
In the ESS charging system configuration, the remaining active current that offsets the current consumed by the supplemental power supply among the current from the main power supply is tracked to flow to the ESS charging system while maintaining the maximum value, and the maximum value tracking is performed by detecting the active current. An inverse ripple function control device for an ESS charging device, further comprising a configuration that achieves the ripple cancellation and maximum active current tracking by linking the results of to current runaway control.
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