JPH0715900A - Synchronous machine and control method for synchronous machine - Google Patents

Abstract

PURPOSE:To simplify and strengthen the structure of a rotor, and to prevent deformation and damage at the time of operation at high speed by installing field windings generating the field magnetic flux of a synchronous machine on the armature side as three pairs of three-phase windings, in which electrical angles are displaced at every 120 deg., and also mounting armature windings on the armature side as three pairs of three-phase windings, in which electrical angles are displaced at every 120 deg.. CONSTITUTION:Field windings 17 for generating field magnetic flux and armature windings 19 are wound in each slot 15 of an armature core 13 in two layers. A rotor 21 is mounted rotatably on the inside in the radial direction of the core 13. The rotor 21 is constituted so as to be easily magnetized in the fixed direction of a cross section. The field windings (u), (v), (w), u', v', w' are wound while phase angles are displaced at every 120 deg., and the armature windings U-W. U'-W' are also wound while phase angles are displaced at every 120 deg.. Phase angles are displaced at every 90 deg. in the armature windings 19 corresponding to the field windings 17. Accordingly, the rotor 21 is magnetized in the fixed direction by the field currents of the field windings 17, and revolving torque by the Fleming's rule is generated between the field currents and armature currents flowing through the armature windings 19.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a synchronous machine, and more particularly to rotary and linear synchronous motors and synchronous generators.

[0002]

2. Description of the Related Art Conventionally, a synchronous motor used in a machine tool or the like has a rotor and an armature (or a stator), which is composed of a permanent magnet or is wound with a coil to generate a direct current. What is excited is used. Further, as the armature, one having a coil wound in a single layer and having the number of poles of 2, 4, or 6 is used. A two-phase or three-phase (normally three-phase) alternating current is used as a current for generating the rotating magnetic field.

As a conventional generator, a coil is wound around an armature (or a stator) and a permanent magnet is provided on the rotor, or a coil is wound into an electromagnet.

[0004]

However, if a rotor is provided with a permanent magnet or a coil is wound, the structure becomes complicated and weakened, and various problems occur due to deformation or damage when rotated at high speed. There's a problem.
In addition, the method of controlling the current by the single layer winding has a problem that the control method becomes complicated when a plurality of characteristics are required.

The present invention has been made to solve the above problems.

[0006]

A synchronous machine according to the present invention comprises:
The field winding that generates the field flux of the synchronous machine is set to an electrical angle of 120.
Provided on the armature side as three sets of three-phase windings staggered,
The armature windings are also provided on the armature side as three sets of three-phase windings shifted by an electrical angle of 120 degrees, and the electrical angle between the windings is preferably 90 degrees.

[0007]

The rotor is magnetized in a predetermined direction by the field current of the field winding wound around the armature, and the armature current flowing in the armature winding has a phase angle of a predetermined angle with the magnetization direction of the rotor. Since they are controlled so as to deviate from each other, a rotational torque or an induced voltage according to Fleming's law is generated.

[0008]

The present invention can be applied not only to rotary type synchronous motors and linear type synchronous motors, but also to synchronous generators. This will be described sequentially below.

First, an embodiment in which the present invention is applied to a rotary synchronous motor will be described with reference to the drawings. Figure 1
Shows an example of the armature 11 of the three-phase synchronous motor. In the figure, the armature core 13 is provided with 24 slots 15, and each slot has a field winding 17 for generating a field magnetic flux and an armature winding 19 wound in two layers. There is.

A rotor 21 is provided on the inner side in the radial direction of the core.
Is rotatably provided, and the rotor 21 is configured to be easily magnetized in a predetermined direction of the cross section.

In the figure, w, v, u, w ', v', u'indicate field windings, and W, V, U, W ', V', U'indicate armature windings. Field windings w, v, u and w ', v', u '
Are wound by shifting the phase angle by 120 degrees. Similarly, the armature windings W, V, U and W ′, V ′, U ′ also have the phase angle of 120 °.
It is wound with a shift. Further, the phase angle of the armature winding corresponding to the field winding is shifted by 90 degrees.

When the three-phase field winding currents Iw, Iv, Iu shown in FIG. 2 are passed through the field winding 17, a combined magnetic field N · S is generated by the field winding, and its magnetic flux distribution is sinusoidal. Become. If the maximum magnetic flux is Φm and the magnetic pole center is θ = 0, the magnetic flux is (1)
It is expressed as an equation.

Φ = Φm · cos θ (1) Further, the field winding current is controlled so that the center of the magnetic pole of the magnetic field generated by the field winding current matches the easy axis of easy magnetization of the rotor. Then, the rotor is magnetized in the specified direction,
The magnetic flux density is approximately expressed by equation (2).

B = Bm · cos θ (2) On the other hand, as shown in FIG. 2, field currents Iw and I are applied to the armature winding.
Three-phase currents Iw, Iv, and Iu whose electrical phase angles are delayed by a predetermined angle α, preferably 90 degrees from v and Iu are supplied.

Then, according to Fleming's law, the torque T is generated and the rotor rotates. This torque T is as follows.

Magnetic flux density B at the positions of the windings w, v, u
w, Bv, and Bu are expressed by the equation (3), and the armature winding currents Iw, Iv, and Iu can be expressed by the equation (4).

Bw = Bm · cos β Bv = Bm · cos (β−120 °) Bu = Bm · cos (β−240 °) (3) Iw = Im · cos β Iv = Im · cos (β−120 ° ) Iu = Im · cos (β−240 °) (4) Therefore, the torque T is expressed by the equation (5).

T = K (BwIw + BvIv + BuIu) = K ₁ BmIm; K ₁ = 3/2 · K (5) In these equations, Bw is the maximum magnetic flux density, Iw is the maximum value of the armature current, and β is the magnetic property. Is the electrical phase angle formed by the center of the coil and the coil w. It should be noted that the magnetic flux Φ ′ also depends on the armature current.
However, since the magnetic resistance of the rotor in the direction of the magnetic flux is large and it is difficult to magnetize, the effect is small.

FIG. 3 shows an outline of the above-mentioned relationship.

FIG. 4 to FIG. 7 show specific examples of the structure of the rotor. These are examples of two poles, but the same can be applied to the case of four poles or more.

FIG. 4 shows an example of a rotor 31 having a circular cross section and a magnetic body 32 having magnetic anisotropy. Examples of the metal of the magnetic anisotropic magnetic material include directional silicon copper plate, directional nickel, iron, steel plate and the like. In FIG. 4, the magnetic anisotropic magnetic body is made of a material that is easily magnetized in the X-axis direction but is hard to be magnetized in the Y-axis direction.

FIG. 5 shows a rotor 33 using an isotropic magnetic material.
In the case of a convex pole shape, it is easily magnetized in the X-axis direction, but is hard to be magnetized because a void is provided in the Y-axis direction.

FIG. 6 shows a case in which the rotor 35 has a segment shape, and the inside of the cross section is made of a non-magnetic body 37, the outside is made of a magnetic body 39, and the outer magnetic body portion 39 is slit in the X-axis direction. A void 41 or a non-magnetic material is provided. Therefore, since the magnetic resistance is small in the X-axis direction, it is easily magnetized, but it is difficult to magnetize in the Y-axis direction.

FIG. 7 shows a case where the rotor 43 is of a hybrid type, and a gap or a non-magnetic body 47 is provided in the magnetic body 45 in the X-axis direction. Therefore, it is easy to magnetize in the X-axis direction, but difficult to magnetize in the Y-axis direction.

FIG. 8 shows an example in which the rotor 49 has four poles. Although it is easy to magnetize in the X and Y directions, it is difficult to magnetize in the Y and Y'axis directions. In the case of the quadrupole type, there are two directions in which the magnetization is easy.

As described above, the magnetic resistance of the rotor is reduced in a predetermined direction of the cross section perpendicular to the axial direction, and two sets of three rotors are provided for the rotor.
When the phase winding is wound and the current phase angle is shifted preferably 90 degrees, a field magnetic flux is generated by the field winding current, and a torque according to Fleming's law is generated between the field winding current and the armature winding current. it can. As a result, perfect vector control capable of generating the optimum and maximum torque by the magnetic flux Φ and the current I becomes possible.

If the field magnetic flux due to the field current is in a proportional relationship, the torque T is given by equation (6).

T = K ₂ · field current / armature current (6) In the above, armature reaction flux Φ ′ that is orthogonal to magnetic flux Φ is also generated by the armature current, and torque is generated with the field current. To do. If the rotor has a circular cross section and is made of a magnetic isotropic material, and the air gap is uniform, the total torque generated is balanced and the rotor does not rotate.

If the rotor material is a magnetic anisotropic rotor having an easy axis of magnetization in the direction of the magnetic flux Φ, torque according to equation (5) is generated even if the cross section is circular and the air gap is uniform. .

Therefore, a synchronous motor based on the present theory can be realized by using a material or structure in which the rotor has a magnetization characteristic that is easily magnetized in the Φ direction and is hard to be magnetized in the Φ ′ direction. Therefore, in the rotor according to the present invention, it is not necessary to wind a field coil around the rotor or attach a permanent magnet unlike the conventional synchronous motor. Further, unlike an induction motor, since it is not necessary to use a silicon steel plate for the rotor and to provide a slot therein and to form the shaped winding with a cage made of aluminum, copper or the like, there is no heat generation due to an induction current.

The synchronous motor according to the present invention can be used as follows.

From the equation (5), the motor output P [w] can be expressed as the equation (7).

P = 2πnT = √3 EI (7) In the equation (7), n is the number of revolutions per second of the motor [rp
s], T is torque [Nm], E is a back electromotive force [v] between the three-phase lines, and I is a phase current [A]. In addition, the back electromotive force E
[V] is represented by the equation (8). However, k is a proportional constant.

E = kΦn [v] (8) From equations (7) and (8), the following can be used. That is, with Φ being constant, a synchronous motor having a constant torque characteristic between 0 and n revolutions, and with Φ being variable, a synchronous motor having a constant output characteristic between about 0 and n revolutions, the product Φ · It is possible to use a high-efficiency synchronous motor or the like that optimally controls I and minimizes motor loss for any load between 0 and n revolutions. Therefore, the motor according to the present invention can be used in all fields of industry. Specific application examples will be described below.

FIG. 9 shows a block diagram of an AC servo motor whose speed is controlled by using the synchronous motor 101 of the present invention.

In the motor 101, the armature current I _a and the field current I _f are the armature winding 19 and the field winding 17 shown in FIG.
And the rotational speed of the magnetic pole of the motor 101 is detected by the first detector 103.

The first detector 103 is a detector capable of detecting the rotational speed and the magnetic pole position, and for example, a rotary encoder or a rotor resolver is used.

The armature current I _a and the field current I _f are controlled by an inverter I 105 and an inverter II 107, respectively, as described below. That is, the rotation speed of the synchronous motor 101 is controlled as follows.

First, the desired rotational speed is given to the rotational speed amplifier 111 by the rotational speed command S ₁ . Further, the rotation speed amplifier 111 includes the first detector 103.
The rotation speed S ₂ of the synchronous motor 101 detected by is fed back, and the armature current control command value S ₃ is output.

The armature current command value S ₃ is the armature current command S ₅ and the armature current S detected by the armature current detector 115 provided on the output side of the inverter I 105.
_It is fed back to the armature current amplifier 113 together with ₇ , and the inverter control signal S ₉ is output from the armature current amplifier 113.

On the other hand, the field current command S ₁₁ is input to the field current amplifier 121 and the field current S ₁₃ detected by the field current detector 117 provided on the output side of the inverter II is the field current S _13. It is fed back to the amplifier 121. From this field current amplifier 121 to the inverter II 10
An inverter control signal S ₁₅ for controlling 7 is output.

Further, the rotation speed S ₂ and the armature current S
₇ and the field current S ₁₃ are input to the armature current and magnetic current phase control amplifier 123, and the control signals S ₁₇ and S ₁₉ for controlling the phase and frequency of each current are input to the inverter I 105 and the inverter II 109. Input to the side.

FIG. 10 shows another embodiment of the present invention, which is a block diagram of a control circuit of an AC servomotor in which the synchronous motor 101 is used to control the rotation angle of the motor or the amount of movement of the load. In FIG. 10, the same circuits as those in FIG. 9 are denoted by the same reference numerals and the description thereof will be omitted. Only new circuits of this application will be described below.

According to the position command S ₂₁ , the desired rotation angle or load movement amount of the motor is input to the position deviation amplifier 201, while the load rotation angle load movement amount detection sensor 2
Rotation angle of the load or movement amount S ₂₃ detected by 03
And the signal S _{25 of} the rotation angle or the rotation position detected by the first detector 103 is simultaneously sent to the position deviation amplifier 2
01, and the rotational speed command S ₂₇ is input from the position deviation amplifier 201 to the input side of the rotational speed amplifier 111 described above.

FIG. 11 is a block diagram of another embodiment of the present invention, which is a high-efficiency operation control system using a synchronous motor to minimize the loss of the motor. The numbers and reference numerals in the figure are the same as those in FIG.

As described above, the motor output of the present invention is p = 2πnT as shown in the equation (7),
The torque is T = k ₂ × armature current × field current as shown in the equation (6). Therefore, armature winding resistance R _a , field winding resistance R _f ,
The armature current I _a and the field current I _f can be minimized depending on the field magnetic flux characteristics with respect to the field current I _f , the armature, and the motor characteristics such as iron loss with respect to the frequency of the field current. Highly efficient operation can be realized if the ratio is set and controlled.

As an example of high-efficiency operation, an example of controlling the copper loss of the motor to the minimum will be described with reference to FIG.

Armature current I _a [A], field current I
_f [A], armature resistance R _a [Ω], field resistance R _f [Ω]
Then, the copper loss P _c [w] of the motor is expressed by the equation (9). Further, the torque T [Nm] is expressed by the equation (10).

P _C = I _a ² · R _a + I _f ² · R _f [w] (9) T = K · T _a · I _f [Nm] (10) Armature current detector 115 and field current detection vessel current I _a detected by 117, since the load torque from the I _f is found, the current to not lower than a load torque I _a, I
I _a ^* , I _f ^* such that _f is variable and P _c is minimized ^.
Is determined, and control is performed based on this. That is, in FIG. 11, the current value I _a detected by the armature current detector 115 and the current value I _f detected by the field current detector 117 are input to the motor loss minimum control circuit 211. Further, the armature winding resistance R of the motor loss minimum control circuit 211 is
Set _a and field winding resistance R _f . This control circuit 211
The I _a control command I _a ^* and the I _f control command I _f ^* determined by the armature current S ₇ and the field current S ₁₃ described with reference to FIG.
Instead of the input, the signal is input to the armature current amplifier 113 and the field current amplifier 121.

FIG. 12 shows another embodiment in which the present invention is applied to a synchronous motor. As shown in FIG. 12, the armature current winding 17 is directly connected to the three-phase AC power supply, and the field current winding 19 is connected to the three-phase AC power supply via the capacitor 221 and the electromagnetic switch 223. Has been done. The electromagnetic switch 223 is controlled to be turned on and off by the synchronization circuit 225.

First, when a three-phase AC current is passed through the armature winding 17 with the electromagnetic switch 223 turned off, an induced current flows through the rotor 227, which induces a rotating magnetic field and induction by the armature winding. A torque according to Fleming's law is generated between the electric current and the electric current, and the motor rotates as an induction motor. When the rotational speed of the motor approaches the synchronous speed due to this induced torque, the synchronizing circuit 225 is activated to turn on the electromagnetic switch 223. The field winding 19 has a capacitor 221
Currents with a phase difference of 0 degrees flow and field poles are generated in the rotor. An attractive force acts between this field pole and the rotating magnetic field created by the armature current, and the rotor is synchronized and rotates as a synchronous motor. A coil or both may be used instead of the capacitor.

FIG. 13 shows another embodiment of the present invention in which the rotor 241 is further provided with permanent magnets 243a and 243b. The magnetic flux generated by the permanent magnets 243a and 243b is Φ _1, and the magnetic flux generated by the field winding 17 (u, v, w) is Φ.

A magnetic pole position detector (not shown) is provided on the rotor 241 to control the current flowing through the field winding 17 so that the directions of Φ ₁ and Φ are always matched. In this case, the combined field magnetic flux ΣΦ becomes ΦΦ = Φ ₁ + Φ, and the field magnetic flux increases.

FIG. 14 shows the armature of the synchronous motor of the present invention in two
This is an embodiment in which the motor is divided to facilitate the assembly of the motor. The division is not limited to two, but may be divided into an appropriate number of plural pieces.
In FIG. 14, the divided armatures 261a and 261b are divided.
The windings 263a and 263b are wound separately.

Therefore, there are fewer assembly restrictions that occur when assembling the motor to the machine. That is, the divided armatures 261a and 261b can be abutted in the direction of the arrow in the figure to integrate the armatures, and the bearing 265 can be attached to the rotating shaft 267 regardless of the assembly of the motor.

FIG. 15 shows an embodiment in which the main shaft of the machine tool and the rotor shaft of the motor are integrally formed. That is, when the main shaft 281 of the machine tool is made of a magnetic material, the end portion 283 is appropriately processed to form the rotor according to the present invention, and the armature winding and the field winding are provided outside the rotor. By providing the wound armature 285, the machine tool and the motor can be integrally manufactured. In the figure, the cutting tool 287 is attached to a tool 289, and the tool 289 is the spindle 28.
1, the main shaft 281 is attached to the bearing 2
It is rotatably supported by 91.

16 and 17, the field winding 301 and the armature winding 303 are wound around separate armature cores 305 and 307, and the reference axis 30 is adjusted so that the phase angles are preferably different by 90 degrees.
An embodiment is shown in which 9 and 311 are combined so that they can be assembled in the axial direction. In FIG. 16, a rotor 319 is composed of a non-magnetic body 315 and a magnetic body portion 317 on a rotating shaft 313. The armature cores 305 and 307 wound with the respective windings are provided outside the rotor 319.
Connecting magnetic body 32 for forming a magnetic circuit outside 07
1 is set. As a result, a closed magnetic circuit indicated by the one-dot chain line 322 is formed, and the same performance as the compound winding synchronous machine described above can be exhibited. When the present embodiment is used, the armature is divided into two, so that the dimension of the armature in the diameter direction can be reduced, which is effective for a machine that requires an elongated motor.

FIG. 18 shows an embodiment in which the present invention is applied to a linear motor. A linear motor 401 shown in FIG. 18 is a structure in which the two-pole, 24-slot three-phase armature shown in FIG.
5 shows a magnetic pole having a segment structure shown in FIG.

In FIG. 18, an armature 403 has a comb-shaped armature core 407 having a field winding 409 composed of windings u, v, w and an armature winding 411 composed of windings U, V, W. Two
It is made up of layers. In addition, the mover 405 includes magnetic poles 413 made of a magnetic material such as iron at intervals of a predetermined distance.
15 is placed on the mounting plate 417 made of a non-magnetic material such as aluminum. These windings 409, 41
When the three-phase alternating current shown in FIG. 2 is flown in FIG. 1, a horizontal force is generated between the armature and the mover by the same principle as that of the rotary motor. Therefore, if the armature is fixed, the mover moves, and if the mover is fixed, the armature moves and a linear motor is configured.

In this embodiment, two poles and 24 slots are used, but the present invention is not limited to this, and the combination of the armature and the mover is not limited to this, and all the above-mentioned configurations can be applied. .

FIG. 19 is a diagram for explaining the principle of an application example of the present invention to a synchronous generator. In the figure, a field winding 503 and an armature winding 505 are wound in two layers on an armature core 501. The rotor 507 is formed in a salient pole shape, and is easily magnetized in the vertical direction in the drawing, but is hard to be magnetized in the horizontal direction. Also, the winding 50
Reference numerals 3 and 505 denote windings for two poles and three phases, which are preferably arranged so that their phases are shifted by 90 degrees. Now, a three-phase current is passed through the field winding 503 composed of the windings u, v, and w, and the magnetic pole center axis 511 of the magnetic field magnetic flux 509 generated thereby and the easy axis of magnetization 513 of the rotor are always maintained. The field winding current is controlled so that they match. Since the rotor is always magnetized in a fixed direction, when it is rotated, a three-phase voltage is induced in the armature winding 505 composed of the windings u, v, and w according to Fleming's law, and it becomes a generator.

The output voltage V and output frequency f of the generator are given by equations (11) and (12), respectively.

V = K ₁ · Φ · n [v] (11) f = K ₂ · n · p [HZ] (12) In the above equation, K ₁ and K ₂ are proportional constants, and Φ is the field magnetic flux [ MAX
WELL], n is the number of revolutions per second [rps]. Also,
If the field current _If is proportional to the field flux Φ (13)
The formula holds.

Φ = K ₃ · I _f [MAXWELL] (13) As described above, the synchronous generator according to the present invention differs from the conventional synchronous generator in that a coil is connected to the rotor and a permanent magnet is attached. No need. Therefore, it is possible to construct a synchronous generator whose rotor is extremely simple and robust.

FIG. 20 is a block diagram of a control circuit for using the synchronous generator according to the present invention to keep the output voltage constant against load changes.

In FIG. 20, a prime mover 525 including a turbine, an engine, a water turbine, etc. is connected to a rotor 523 of the synchronous generator 521 and is rotated at a constant speed. A load 527 is connected to the armature winding 505. Further, the rotor 523 is provided with a magnetic pole position detector 531 including a rotary encoder and the like, and a magnetic pole position signal S ₅₁ is output. The armature winding 505 is provided with an instrument transformer 535, and the output voltage S ₅₂ is detected.

A desired predetermined voltage is input to the armature voltage amplifier 537 as a voltage command S ₅₃ , and at the same time, the output voltage S ₅₂ detected by the instrument transformer 535 is input to the armature voltage amplifier 537. The armature voltage amplifier 53
7 inputs the field current command S ₅₅ to the field current amplifier 539. The field current amplifier 539 also includes a field current detector 54.
The field current S ₅₇ detected by 1 is fed back.

The field current value command S ₅₉ output from the field current amplifier 539 is input to the field current phase control amplifier 541. The magnetic pole position signal S ₅₁ detected by the magnetic pole position detector is input to the field current phase control amplifier 541. The field current phase control amplifier 541 supplies the inverter control signal S to the inverter 543 which controls the field current.
Output ₆₁ .

Since the present embodiment is configured as described above, in the no-load operation in which the load is not connected to the generator, the induced voltage becomes the output voltage as it is and the load is not connected to the generator. For example, a current flows through the armature windings u, v, w, a voltage drop occurs due to the impedance of the armature winding, and the output voltage becomes small. Therefore, in order to compensate for this voltage drop and keep the output voltage constant, the instrument transformer 53
5, the output voltage S ₅₂ is fed back to the armature voltage amplifier 537. This armature voltage amplifier 537
Outputs a field current amplifier 539 field current command S ₅₅ by amplifying the deviation between the voltage command S ₅₃ and the generator output voltage S ₅₂ . The field current amplifier 539 amplifies the deviation between the field current command S ₅₅ and the field current S ₅₇ from the field current detector 541, and outputs the field current command S ₅₉ to the field current phase control amplifier 541.
Output to. The field current phase control amplifier 541 determines the rotor 523 based on the magnetic position signal S ₅₁ and the field current command S _59.
, The inverter control signal S ₆₁ is generated so that the field current flows through the field winding correctly. With this signal, the inverter 543 creates a field current and controls its value, so that the output voltage becomes constant even if the load changes.

[0070]

As described above, according to the present invention,
Two sets of coils are wound on the armature side, but since it is not necessary to attach permanent magnets or wind the coils on the rotor side, the structure of the rotor can be simple and robust. Since it can be done, it is not easily damaged even at high speed operation.

[Brief description of drawings]

FIG. 1 is a diagram showing a structure of an armature according to a first embodiment of the present invention.

FIG. 2 is a diagram showing a phase relationship between currents flowing in a field winding and an armature winding.

FIG. 3 is a diagram showing a state of magnetic density due to a field current in the first embodiment.

FIG. 4 is a diagram showing an example of a rotor made of a magnetic material having magnetic anisotropy.

FIG. 5 is a view showing an example of a salient pole rotor.

FIG. 6 is a diagram showing an example of a rotor having a segment shape.

FIG. 7 is a diagram showing an example of a rotor configured as a hybrid type.

FIG. 8 is a diagram showing an example of a salient pole rotor having four poles.

FIG. 9 is a block diagram of a control device that controls the speed of a synchronous motor using the present invention.

FIG. 10 is a block diagram of a control device that controls the position of a synchronous motor using the present invention.

FIG. 11 shows a block diagram of a control device for controlling a synchronous motor using the present invention to minimize motor loss.

FIG. 12 is a diagram showing an example in which a phase delay of a synchronous motor using the present invention is configured by a reactor.

FIG. 13 is a diagram showing an example in which a permanent magnet is further provided on the rotor.

FIG. 14 is a diagram showing an embodiment in which an armature can be divided into two parts and assembled.

FIG. 15 is a diagram showing an example in which a main shaft of a rotor and a main shaft of a motor of a machine tool are integrally formed.

FIG. 16 is a diagram showing an example in which field windings and armature windings are separately configured and arranged in parallel.

FIG. 17 is a diagram showing a positional relationship between the field winding and the armature winding in the embodiment of FIG.

FIG. 18 is a diagram showing the configuration of an embodiment in which the present invention is applied to a linear motor.

FIG. 19 is a diagram illustrating the principle of an embodiment in which the present invention is applied to a synchronous generator.

20 shows a block diagram of an embodiment of a control device for making the output voltage constant in the generator of FIG.

[Explanation of symbols]

 11 Armature 13 Armature Core 15 Slot 17 Field Winding 19 Armature Winding 21 Rotor 31 Circular Rotor 33 Convex Pole Rotor 35 Segment Rotor 43 Hybrid Rotor 49 4-Pole Rotor 101 Synchronous Motor 103 1st detector 301 Field winding 303 Armature winding 305,307 Armature core 313 Rotating shaft 315 Non-magnetic body 317 Magnetic body part 401 Linear motor 403 Armature 405 Mover 407 Armature core 409 Field winding 411 Armature winding 413 Magnetic pole 501 Armature core 503 Field winding 505 Armature winding 507 Rotor 521 Synchronous generator 531 Magnetic pole position detector

[Procedure amendment]

[Submission date] March 2, 1993

[Procedure Amendment 1]

[Document name to be amended] Statement

[Correction target item name] Full text

[Correction method] Change

[Correction content]

[Document name] Statement

Title: Synchronous machine and method for controlling synchronous machine

[Claims]

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a synchronous machine, and more particularly to rotary and linear synchronous motors and synchronous generators.

[0002]

2. Description of the Related Art Conventionally, a synchronous motor used in a machine tool or the like has an armature (stator) and a rotor, and a permanent magnet is provided on the rotor or a coil is wound to form a field pole. And excite with a direct current to make a field pole. 2 to 8 poles
Many things such as poles are used.

Further, the conventional generator has an armature (stator) and a rotor as in the case of the synchronous motor, and a permanent magnet is provided on the rotor, or a coil is wound to form a field pole as an electromagnet. Has been done.

[0004]

However, if a rotor is provided with a permanent magnet or a coil is wound, the structure becomes complicated and weakened, and various problems occur due to deformation or damage when rotated at high speed. There's a problem.
Also, with such a structure, required for the spindle of machine tools,
There is a problem when a plurality of characteristics such as constant output characteristics in a wide rotation range, rotation with less torque pulsation, and no thermal deformation due to heat generation of the rotor are required.

The present invention has been made to solve the above problems.

[0006]

A synchronous machine according to the present invention comprises:
The field winding that generates the field flux of the synchronous machine is set to an electrical angle of 120.
Provided on the armature side as three sets of three-phase windings staggered,
The armature windings are also provided on the armature side as three sets of three-phase windings shifted by an electrical angle of 120 degrees, and the electrical angle between the windings is preferably 90 degrees.

[0007]

The rotor current is magnetized in a predetermined direction by the field current of the field winding wound around the armature, and the phase of the rotor, the armature current and the field current is irrespective of the position of the rotor. Since the angle is controlled to a predetermined angle, a rotating torque according to Fleming's law is generated between the angle and the armature current flowing through the armature winding. Further, the rotating magnetic field magnetic pole type synchronous machine produces an induced voltage when the rotor is rotated by an external force.

[0008]

The present invention can be applied not only to rotary type synchronous motors and linear type synchronous motors, but also to synchronous generators. This will be described sequentially below.

First, an embodiment in which the present invention is applied to a rotary synchronous motor will be described with reference to the drawings. Figure 1
Shows an example of the armature 11 of the three-phase synchronous motor. In the figure, the armature core 13 is provided with 24 slots 15, and each slot has a field winding 17 for generating a field magnetic flux and an armature winding 19 wound in two layers. There is.
Further, a rotor 21 is rotatably provided inside the core in the radial direction, and the rotor 21 is configured to be easily magnetized in a predetermined direction of a cross section.

In the figure, u, v, w, u ', v', w'represent field windings, and U, V, W, U ', V', W'represent armature windings. The field windings u, v, w, u ', v', w'are wound with a phase angle shift of 120 degrees, and similarly, armature windings U, V, W, U ', V', W '. Are also wound by shifting the phase angle by 120 degrees. Further, the phase angle of the armature winding corresponding to the field winding is shifted by 90 degrees.

When the three-phase field winding currents Iu, Iv, and Iw shown in FIG. 2 are applied to the field winding 17, a composite magnetic field N · S is generated by the field winding, and the magnetic flux distribution is sinusoidal. Become. If the maximum magnetic flux is Φm and the magnetic pole center is θ = 0, the magnetic flux is (1)
It is expressed as an equation.

Φ = Φm · cos θ (1) Further, the field winding current is controlled so that the center of the magnetic pole of the magnetic field generated by the field winding current matches the easy axis of easy magnetization of the rotor. Then, the rotor is magnetized in the specified direction,
The magnetic flux density is approximately expressed by equation (2).

B = Bm · cos θ (2) On the other hand, field currents Iu and I are applied to the armature winding as shown in FIG.
Three-phase currents IU, IV, and IW whose electrical phase angles are advanced by a predetermined angle α, preferably 90 degrees from v and Iw are passed.

Then, according to Fleming's law, the torque T is generated and the rotor rotates. This torque T is as follows.

Here, in order to facilitate explanation of the torque T, the armature current I is adjusted in accordance with the magnetic poles of the magnetized rotor.
The formulas for the torque T when the phases of U, IV and IW are controlled are shown below. Assuming that the magnetic flux densities BU, BV, and BW at U, V, and W coil positions of the armature winding are, BU = Bm · cos θ BV = Bm · cos (θ−120 °) BW = Bm · cos (θ -240 °) (3) and the armature currents IU, IV, IW are controlled according to the magnetic pole position, so IU = Im · cos θ IV = Im · cos (θ−120 °) IW = Im · cos (θ -240 °) (4). Therefore, the torque T is expressed by the equation (5).

T = K (BU · IU + BV · IV + BW · IW) = 3/2 KBm · Im (5) In these equations, Bm is the maximum magnetic flux density, Im is the maximum value of the armature current, and θ is the magnetic pole. It is an electrical phase angle formed by the center and the coil U. It should be noted that the magnetic flux Φ ′ also depends on the armature current.
However, since the magnetic resistance of the rotor in the direction of the magnetic flux is large and the magnetically anisotropic rotor is hard to be magnetized, its influence is small.

FIG. 3 shows an outline of the above-mentioned relationship.

FIG. 4 to FIG. 7 show concrete examples of the structure of the magnetic anisotropic rotor. These are examples of 2 poles, but 4
It can be configured even when the number of poles is more than the maximum.

FIG. 4 shows an example of a rotor 31 having a circular cross section and a magnetic body 32 having magnetic anisotropy. Examples of the metal of the magnetic anisotropic magnetic material include grain-oriented silicon steel sheet and grain-oriented nickel-iron steel sheet. In FIG. 4, the magnetic anisotropic magnetic body is made of a material that is easily magnetized in the X-axis direction but is hard to be magnetized in the Y-axis direction.

FIG. 5 shows a rotor 33 using an isotropic magnetic material.
In the case of a convex pole shape, it is easily magnetized in the X-axis direction, but is hard to be magnetized because a void is provided in the Y-axis direction.

FIG. 6 shows a case in which the rotor 35 has a segment shape. The inside of the cross section is made of a non-magnetic body 37, the outside is made of a magnetic body 39, and the outside magnetic body portion 39 is slit in the X-axis direction. A void 41 or a non-magnetic material is provided. Therefore, since the magnetic resistance is small in the X-axis direction, it is easily magnetized, but it is difficult to magnetize in the Y-axis direction.

FIG. 7 shows a case where the rotor 43 is a hybrid type, in which a gap or a non-magnetic body 47 is provided in the magnetic body 45 in the X-axis direction. Therefore, it is easy to magnetize in the X-axis direction, but difficult to magnetize in the Y-axis direction.

FIG. 8 shows an example in which the rotor 49 has four poles. Although it is easy to magnetize in the X and X'directions, it is difficult to magnetize in the Y and Y'axis directions. In the case of the quadrupole type, there are two directions in which the magnetization is easy.

As described above, the rotor is provided with the magnetic anisotropy in the predetermined direction of the cross section perpendicular to the axial direction, and the armature has two sets of three.
If the phase winding is wound and the current phase angle is shifted preferably 90 degrees, a field magnetic flux is created by the field winding current, and a torque according to Fleming's law can be generated between the phase winding and the armature winding current. it can. As a result, perfect vector control capable of generating the optimum and maximum torque by the magnetic flux Φ and the current I becomes possible.

If the field magnetic flux due to the field current is in a proportional relationship, the torque T is given by equation (6).

T = K ₂ · field current / armature current (6) In the above, armature reaction flux Φ ′ orthogonal to magnetic flux Φ is also generated by the armature current, and torque is generated with the field current. To do. If the rotor has a circular cross section and is made of a magnetic isotropic material and the air gap is uniform, the rotor does not rotate.

If the rotor material is a magnetic anisotropic rotor having an easy axis of magnetization in the direction of the magnetic flux Φ, torque according to equation (5) is generated even if the cross section is circular and the air gap is uniform. .

Therefore, the synchronous motor based on the present theory can be realized by using a material or structure in which the rotor has a magnetization characteristic that is easily magnetized in the Φ direction and is hard to be magnetized in the Φ ′ direction.

Therefore, in the rotor according to the present invention, it is not necessary to wind a field coil or attach a permanent magnet to the rotor as in the conventional synchronous motor. Also, like an induction motor, a synchronous steel machine that does not require heat generation due to induced current without the need to use a silicon steel plate for the rotor, provide slots in it, and squirrel cage windings made of aluminum, copper, etc. It is a rotating field magnetic pole type synchronous machine of the invention.

The synchronous motor according to the present invention can be used as follows.

From the equation (5), the motor output P [w] can be expressed as the equation (7).

P = 2πnT = √3 EI (7) In the equation (7), n is the number of revolutions per second of the motor [rp
s], T is torque [Nm], E is a back electromotive force [v] between the three-phase lines, and I is a phase current [A]. In addition, the back electromotive force E
[V] is represented by the equation (8). However, k is a proportional constant.

E = kΦn [v] (8) From the expressions (7) and (8), the following can be used. That is, with Φ being constant, a synchronous motor having a constant torque characteristic between 0 and n revolutions, and with Φ being variable, a synchronous motor having a constant output characteristic between about 0 and n revolutions, the product Φ · It is possible to use a high-efficiency synchronous motor or the like that optimally controls I and minimizes motor loss for any load between 0 and n revolutions. Therefore, the motor according to the present invention can be used in all fields of industry. Specific application examples will be described below.

FIG. 9 shows a block diagram of an AC servo motor whose speed is controlled by using the synchronous motor 101 of the present invention.

In the motor 101, the armature current I _a and the field current I _f are the armature winding 19 and the field winding 17 shown in FIG.
Of the magnetic pole with respect to the armature winding and the field winding of the motor 101, and the rotation speed of the magnetic pole.
3 is detected.

The first detector 103 is a detector capable of detecting the rotation speed and the magnetic pole position, and for example, a rotary encoder or a rotary resolver is used.

The armature current I _a and the field current I _f are controlled by an inverter I 105 and an inverter II 107, respectively, as described below. That is, the rotation speed of the synchronous motor 101 is controlled as follows.

First, the desired rotational speed is given to the rotational speed amplifier 111 by the rotational speed command S ₁ . Further, the rotation speed amplifier 111 includes the first detector 103.
The rotation speed S ₂ of the synchronous motor 101 detected by is fed back, and the armature current control command value S ₃ is output.

The armature current command value S ₃ is given to the armature current amplifier 113 together with the armature current command S ₅ , and the armature current detector 1 provided on the output side of the inverter I 105.
The armature current S ₇ detected by 15 is fed back to the armature current amplifier 113. The inverter control signal S ₉ is output from the armature current amplifier 113.

On the other hand, the field current command S ₁₁ is input to the field current amplifier 121 and the field current S ₁₃ detected by the field current detector 117 provided on the output side of the inverter II is the field current S _13. It is fed back to the amplifier 121. From this field current amplifier 121 to the inverter II 10
An inverter control signal S ₁₅ for controlling 7 is output.

Further, the magnetic pole position value S ₄ , the armature current S ₇ and the field current S ₁₃ are input to the armature current and field current phase control amplifier 123, and control signals for controlling the phase and frequency of each current. S ₁₇ and S ₁₉ are input to the input sides of the inverter I 105 and the inverter II 109. Therefore, the currents Ia and If are controlled, and the synchronous motor of the present invention operates as an AC servo motor, and a desired predetermined rotation speed is obtained.

FIG. 10 shows another embodiment of the present invention, which is a block diagram of a control circuit of an AC servomotor in which the synchronous motor 101 is used to control the rotation angle of the motor or the amount of movement of the load. In FIG. 10, the same circuits as those in FIG. 9 are denoted by the same reference numerals and the description thereof will be omitted. Only new circuits of this application will be described below.

A desired rotation angle or load movement amount of the motor is input to the position deviation amplifier 201 by the position command S ₂₁ , while the load rotation angle load movement amount detection sensor 2
Rotation angle of the load or movement amount S ₂₃ detected by 03
And the signal S _{25 of} the rotation angle or the rotation position detected by the first detector 103 is simultaneously sent to the position deviation amplifier 2
01, the rotation speed command S ₂₇ is input from the position deviation amplifier 201 to the input side of the rotation speed amplifier 111, and the motor rotates to control the rotation angle and the movement amount.

FIG. 11 is a block diagram of a high efficiency operation control system according to another embodiment of the present invention, which utilizes a synchronous motor to minimize the loss of the motor. The numbers and reference numerals in the figure are the same as those in FIG.

As described above, the motor output of the present invention is p = 2πnT as shown in the equation (7),
The torque is T = k ₂ × armature current × field current as shown in the equation (6). Therefore, armature winding resistance R _a , field winding resistance R _f ,
The armature current I _a and the field current I _f can be minimized depending on the field magnetic flux characteristics with respect to the field current I _f , the armature, and the motor characteristics such as iron loss with respect to the frequency of the field current. Highly efficient operation can be realized if the ratio is set and controlled.

As an example of high efficiency operation, an example of controlling the copper loss of the motor to the minimum will be described with reference to FIG.

Armature current I _a [A], field current I
_f [A], armature resistance R _a [Ω], field resistance R _f [Ω]
Then, the copper loss P _c [w] of the motor is expressed by the equation (9). Further, the torque T [Nm] is expressed by the equation (10).

P _C = I _a ² · R _a + I _f ² · R _f [w] (9) T = K · I _a · I _f [Nm] (10) Armature current detector 115 and field current detection vessel current I _a detected by 117, since the load torque from the I _f is found, the current to not lower than a load torque I _a, I
I _a ^* , I _f ^* such that _f is variable and P _c is minimized ^.
Is determined, and control is performed based on this. That is, in FIG. 11, the current value I _a detected by the armature current detector 115 and the current value I _f detected by the field current detector 117 are input to the motor loss minimum control circuit 211. Further, the armature winding resistance R of the motor loss minimum control circuit 211 is
Set _a and field winding resistance R _f to eigenvalues determined by the motor. I _a determined by this control circuit 211
Control instruction I _a ^*, I _f control command I _f ^* armature current S ₇ described in FIG. 9, instead of the field current S _13, is input to the armature current amplifier 113 and the field current amplifier 121, the motor Minimal control of copper loss and highly efficient movement can be realized.

FIG. 12 shows another embodiment in which the present invention is applied to a synchronous motor. As shown in FIG. 12, the armature current winding 19 is directly connected to the three-phase AC power supply, and the field current winding 17 is connected to the three-phase AC power supply via the capacitor 221 and the electromagnetic switch 223. Has been done. The electromagnetic switch 223 is controlled to be turned on and off by the synchronization circuit 225.

First, when a three-phase AC current is passed through the armature winding 19 with the electromagnetic switch 223 turned off, an induced current flows through the rotor 227, which induces a rotating magnetic field and induction by the armature winding. A torque according to Fleming's law is generated between the electric current and the electric current, and the motor rotates as an induction motor. When the rotational speed of the motor approaches the synchronous speed due to this induced torque, the synchronizing circuit 225 is activated to turn on the electromagnetic switch 223. 9 is connected to the field winding 17 by the capacitor 221.
Currents with a phase difference of 0 degrees flow and field poles are generated in the rotor. An attractive force acts between this field pole and the rotating magnetic field created by the armature current, and the rotor is synchronized and rotates as a synchronous motor. A coil or both may be used instead of the capacitor.

FIG. 13 shows another embodiment of the present invention in which the rotor 241 is further provided with permanent magnets 243a and 243b. The magnetic flux generated by the permanent magnets 243a and 243b is Φ _1, and the magnetic flux generated by the field winding 17 (u, v, w) is Φ.

A magnetic pole position detector (not shown) is provided on the rotor 241 to control the current flowing through the field winding 17 so that the directions of Φ ₁ and Φ are always matched. In this case, if Φ ₁ and Φ are in phase, the combined field magnetic flux ΣΦ is ΣΦ = Φ ₁ + Φ, and the field magnetic flux increases. If Φ ₁ and Φ are in opposite phase, ΣΦ =
It becomes Φ ₁ −Φ and the field magnetic flux decreases.

FIG. 14 shows two armatures of the synchronous motor of the present invention.
This is an embodiment in which the motor is divided to facilitate the assembly of the motor. The division is not limited to two, but may be divided into an appropriate number of plural pieces.
In FIG. 14, the divided armatures 261a and 261b are divided.
The windings 263a and 263b are wound separately.

Therefore, there are fewer assembly restrictions that occur when assembling the motor to the machine. That is, the divided armatures 261a and 261b can be abutted in the direction of the arrow in the figure to integrate the armatures, and the bearing 265 can be attached to the rotating shaft 267 regardless of the assembly of the motor.

FIG. 15 shows an embodiment in which the main shaft of the machine tool and the rotor shaft of the motor are integrally formed. That is, when the main shaft 281 of the machine tool is made of a magnetic material, the end portion 283 is appropriately processed to form the rotor according to the present invention, and the armature winding and the field winding are provided outside the rotor. By providing the wound armature 285, the machine tool and the motor can be integrally manufactured. In the figure, the cutting tool 287 is attached to a tool 289, and the tool 289 is the spindle 28.
1, the main shaft 281 is attached to the bearing 2
It is rotatably supported by 91.

16 and 17, the field winding 301 and the armature winding 303 are wound around separate armature cores 305 and 307, and the reference axis 30 is adjusted so that the phase angles are preferably different by 90 degrees.
An embodiment is shown in which 9 and 311 are combined so that they can be assembled in the axial direction. In FIG. 16, a rotor 319 is composed of a non-magnetic body 315 and a magnetic body portion 317 on a rotating shaft 313. The armature cores 305 and 307 wound with the respective windings are provided outside the rotor 319.
Connecting magnetic body 32 for forming a magnetic circuit outside 07
1 is set. As a result, a closed magnetic circuit indicated by the one-dot chain line 322 is formed, and the same performance as the compound winding synchronous machine described above can be exhibited. When the present embodiment is used, the armature is divided into two, so that the dimension of the armature in the diameter direction can be reduced, which is effective for a machine that requires an elongated motor.

FIG. 18 shows an embodiment in which the present invention is applied to a linear motor. A linear motor 401 shown in FIG. 18 is a structure in which the two-pole, 24-slot three-phase armature shown in FIG.
5 shows a magnetic pole having a segment structure shown in FIG.

In FIG. 18, an armature 403 has a comb-shaped armature core 407 having a field winding 409 including windings u, v and w and an armature winding 411 including windings U, V and W. Two
It is made up of layers. In addition, the mover 405 includes magnetic poles 413 made of a magnetic material such as iron at intervals of a predetermined distance.
15 is placed on the mounting plate 417 made of a non-magnetic material such as aluminum. These windings 409, 41
When the three-phase alternating current shown in FIG. 2 is flown in FIG. 1, a horizontal force is generated between the armature and the mover by the same principle as that of the rotary motor. Therefore, if the armature is fixed, the mover moves, and if the mover is fixed, the armature moves and a linear motor is configured.

In the present embodiment, two poles and 24 slots are used, but the present invention is not limited to this, and the combination of the armature and the mover is not limited to this, and all the above-mentioned configurations can be applied. .

FIG. 19 is a diagram for explaining the principle of an application example of the present invention to a synchronous generator. In the figure, a field winding 503 and an armature winding 505 are wound in two layers on an armature core 501. The rotor 507 is formed in a salient pole shape, and is easily magnetized in the vertical direction in the drawing, but is hard to be magnetized in the horizontal direction. Also, the winding 50
Reference numerals 3 and 505 denote windings for two poles and three phases, which are preferably arranged so that their phases are shifted by 90 degrees. Now, a three-phase current is passed through the field winding 503 composed of the windings u, v, and w, and the magnetic pole center axis 511 of the magnetic field magnetic flux 509 generated thereby and the easy axis of magnetization 513 of the rotor are always maintained. The field winding current is controlled so that they match. Since the rotor is always magnetized in a fixed direction, when it is rotated, a three-phase voltage is induced in the armature winding 505 composed of the windings u, v, and w according to Fleming's law, and it becomes a generator.

The output voltage V and output frequency f of the generator are given by equations (11) and (12), respectively.

V = K ₁ · Φ · n [v] (11) f = K ₂ · n · p [HZ] (12) In the above equation, K ₁ and K ₂ are proportional constants, and Φ is the field magnetic flux [ MAX
WELL], n is the number of revolutions per second [rps]. Also,
If the field current _If is proportional to the field flux Φ (13)
The formula holds.

Φ = K ₃ · I _f [MAXWELL] (13) As described above, the synchronous generator according to the present invention differs from the conventional synchronous generator in that a coil is connected to the rotor and a permanent magnet is attached. No need. Therefore, it is possible to construct a synchronous generator whose rotor is extremely simple and robust.

FIG. 20 is a block diagram of a control circuit for using the synchronous generator according to the present invention to keep the output voltage constant against load changes.

In FIG. 20, a prime mover 525 including a turbine, an engine, a water turbine, etc. is connected to a rotor 523 of the synchronous generator 521 and is rotated at a constant speed. A load 527 is connected to the armature winding 505. Further, the rotor 523 is provided with a magnetic pole position detector 531 including a rotary encoder and the like, and a magnetic pole position signal S ₅₁ is output. The armature winding 505 is provided with an instrument transformer 535, and the output voltage S ₅₂ is detected.

A desired predetermined voltage is input to the armature voltage amplifier 537 as the voltage command S ₅₃ , and at the same time, the output voltage S ₅₂ detected by the instrument transformer 535 is input to the armature voltage amplifier 537. The armature voltage amplifier 53
7 inputs the field current command S ₅₅ to the field current amplifier 539. The field current amplifier 539 also includes a field current detector 54.
The field current S ₅₇ detected by 1 is fed back.

The field current value command S ₅₉ output from the field current amplifier 539 is input to the field current phase control amplifier 541. Further, the field current phase control amplifier 541 has a magnetic pole position signal S detected by the magnetic pole position detector 531.
₅₁ has been entered. The field current phase control amplifier 541 outputs the inverter control signal S ₆₁ to the inverter 543 which controls the field current.

Since the present embodiment is configured as described above, in the no-load operation where the load is not connected to the generator, the induced voltage becomes the output voltage as it is and the load is not connected to the generator. For example, a current flows through the armature windings U, V, W, a voltage drop occurs due to the impedance of the armature winding, and the output voltage becomes small. Therefore, in order to compensate for this voltage drop and keep the output voltage constant, the instrument transformer 53
5, the output voltage S ₅₂ is fed back to the armature voltage amplifier 537. This armature voltage amplifier 537
Amplifies the deviation between the voltage command S ₅₃ and the generator output voltage S ₅₂ and outputs the field current command S ₅₅ to the field current amplifier 539. The field current amplifier 539 amplifies the deviation between the field current command S ₅₅ and the field current S ₅₇ from the field current detector 541, and outputs the field current command S ₅₉ to the field current phase control amplifier 541.
Output to. The field current phase control amplifier 541 determines the rotor 523 based on the magnetic pole position signal S ₅₁ and the field current command S _59.
, The inverter control signal S ₆₁ is generated so that the field current flows through the field winding correctly. With this signal, the inverter 543 creates a field current and controls its value, so that the output voltage becomes constant even if the load changes.

[0069]

As described above, according to the present invention,
Two sets of coils are wound on the armature side, but since it is not necessary to attach permanent magnets or wind the coils on the rotor side, the structure of the rotor can be simple and robust. Since it can be done, it is not easily damaged even at high speed operation.

[Brief description of drawings]

FIG. 1 is a diagram showing a structure of an armature according to a first embodiment of the present invention.

FIG. 2 is a diagram showing a phase relationship between currents flowing in a field winding and an armature winding.

FIG. 3 is a diagram showing a state of magnetic density due to a field current in the first embodiment.

FIG. 4 is a diagram showing an example of a rotor made of a magnetic material having magnetic anisotropy.

FIG. 5 is a view showing an example of a salient pole rotor.

FIG. 6 is a diagram showing an example of a rotor having a segment shape.

FIG. 7 is a diagram showing an example of a rotor configured as a hybrid type.

FIG. 8 is a diagram showing an example of a salient pole rotor having four poles.

FIG. 9 is a block diagram of a control device that controls the speed of a synchronous motor using the present invention.

FIG. 10 is a block diagram of a control device that controls the position of a synchronous motor using the present invention.

FIG. 11 shows a block diagram of a control device for controlling a synchronous motor using the present invention to minimize motor loss.

FIG. 12 is a diagram showing an example in which a phase delay of a synchronous motor using the present invention is configured by a reactor.

FIG. 13 is a diagram showing an example in which a permanent magnet is further provided on the rotor.

FIG. 14 is a diagram showing an embodiment in which an armature can be divided into two parts and assembled.

FIG. 15 is a diagram showing an example in which a main shaft of a rotor and a main shaft of a motor of a machine tool are integrally formed.

FIG. 16 is a diagram showing an example in which field windings and armature windings are separately configured and arranged in parallel.

FIG. 17 is a diagram showing a positional relationship between the field winding and the armature winding in the embodiment of FIG.

FIG. 18 is a diagram showing the configuration of an embodiment in which the present invention is applied to a linear motor.

FIG. 19 is a diagram illustrating the principle of an embodiment in which the present invention is applied to a synchronous generator.

20 shows a block diagram of an embodiment of a control device for making the output voltage constant in the generator of FIG.

[Explanation of Codes] 11 Armature 13 Armature Core 15 Slot 17 Field Winding 19 Armature Winding 21 Rotor 31 Circular Rotor 33 Convex Pole Type Rotor 35 Segment Type Rotor 43 Hybrid Type Rotor 49 4 Pole Rotor 101 Synchronous motor 103 First detector 301 Field winding 303 Armature winding 305, 307 Armature core 313 Rotation axis 315 Non-magnetic material 317 Magnetic material part 401 Linear motor 403 Armature 405 Mover 407 Armature core 409 field winding 411 armature winding 413 magnetic pole 501 armature core 503 field winding 505 armature winding 507 rotor 521 synchronous generator 531 magnetic pole position detector

[Procedure Amendment 2]

[Document name to be corrected] Drawing

[Correction target item name] All drawings

[Correction method] Change

[Correction content]

[Figure 1]

[Fig. 2]

[Figure 3]

[Figure 4]

[Figure 5]

[Figure 6]

[Figure 7]

[Figure 8]

[Figure 9]

[Figure 10]

FIG. 11

[Fig. 12]

[Fig. 13]

FIG. 14

FIG. 15

FIG. 19

FIG. 16

FIG. 17

FIG. 18

FIG. 20

Continuation of the front page (51) Int.Cl. ⁶ Identification number Office reference number FI technical display location H02P 9/14 A 9178-5H

Claims (15)

[Claims] 1. A field winding for generating a field flux of a synchronous machine is provided on the armature side as three sets of three-phase windings, which are shifted by an electrical angle of 120 degrees, and the armature winding is also provided by an electrical angle of 120 degrees. A synchronous machine having an armature structure which is provided on the armature side as three sets of shifted three-phase windings, and an electrical angle between the windings is preferably 90 degrees. 2. The synchronous machine according to claim 1, wherein in the armature structure, the number of phases and the number of poles are arbitrary, and the electrical phase angle between the two windings is 90 degrees. 3. The synchronous machine according to claim 1, wherein in the electric machine structure, the rotor is made of a magnetic material having an arbitrary shape. 4. The synchronous machine according to claim 1, wherein the load shaft itself of the machine or instrument is the rotor of the armature structure. 5. In the synchronous machine, an armature has an electrical angle of 9 degrees.
2. Two sets of three-phase currents of 0 degree phase are made to flow, and the frequency and current are controlled to control the torque of the motor, the number of rotations, the rotation angle of the load, or the amount of movement. Synchronous machine. 6. In the synchronous machine, two sets of three-phase currents having arbitrary electrical angle phases are passed through the armature, and the frequency and current are controlled to control the motor torque, rotation speed, load rotation angle, or the like. 2. The synchronous machine according to claim 1, wherein the amount of movement is controlled. 7. The synchronous machine according to claim 1, wherein two sets of three-phase currents wound around an armature are optimally controlled to perform high-efficiency control with minimum motor loss under arbitrary rotation and arbitrary load. . 8. A three-phase AC power supply is directly connected to the armature winding of the synchronous machine according to claim 1, the induction current torque is used to rotate the motor to a speed close to a synchronous rotation speed, and the field winding is passed through a capacitor or a reactor. A method for synchronizing a synchronous machine, comprising a step of connecting to a phase power source, forming a field pole in a rotor with a 90-degree phase current, and synchronizing. 9. The synchronization method according to claim 8, wherein in the synchronization method, a field pole is formed in the rotor with a current having an arbitrary phase. 10. The synchronous machine according to claim 1, wherein in the synchronous machine, a permanent magnet is attached to a rotor, and a field pole is formed by a sum of a magnetic flux of the permanent magnet and a magnetic flux of a field current. 11. The synchronous machine, wherein two sets of three-phase windings are wound so that the stator can be divided into two or more pieces,
2. The synchronous machine according to claim 1, wherein a split armature is provided so that the stator can be assembled after the rotor is mounted on the machine. 12. The synchronous machine according to claim 11, wherein, in the synchronous machine, a shaft of the machine itself is used as a rotor of a motor and the motor is assembled with the split armature as a stator. 13. In the synchronous machine, the two sets of three-phase windings are wound on separate armature cores, the two sets of armatures are assembled in the axial direction, and the electrical phase angle of the three-phase windings is adjusted. A synchronous machine having an armature structure of 90 degrees. 14. The synchronous machine according to claim 1, wherein the synchronous machine has a linear armature structure. 15. The synchronous machine according to claim 1, wherein the synchronous machine is a generator.