JP3391658B2 - High frequency circuit - Google Patents

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a high frequency circuit, and more particularly to a high frequency circuit such as an amplifier and a frequency converter used in a receiver for microwave and millimeter wave wireless communication.

[0002]

2. Description of the Related Art Bipolar transistor or FET
(Field effect transistor) and passive elements form a unit amplifier or unit mixer, and an input signal is distributed in parallel to the unit amplifier or unit mixer by a distributor, and after performing signal amplification or frequency conversion, unit amplifier or unit There is a high-frequency circuit that combines the outputs of mixers and outputs a combined signal.

In a frequency converter, which is a kind of high-frequency circuit, several unit mixers are balanced in parallel to synthesize desired output signals in phase, and unwanted output signals are synthesized in reverse phase to cancel each other. ing. Various methods have been devised for such a partitioning and combining method. For example, there are an image rejection mixer, a local oscillation signal suppressing single balance mixer and a balance mixer, which are disclosed in JP-A-6-29749, for canceling an image component and a converted signal by the local oscillation signal.

Hereinafter, some examples of conventional high frequency circuits will be described. [Prior Art 1] Referring to FIG. 7, a Wilkinson type amplifier 72 divides an input signal into two in-phase (phase difference is 0 degree) and outputs a divided signal. And unit amplifiers 70a and 70b respectively connected to the outputs of the Wilkinson type distributor / combiners 4 for amplifying the distributed signals and outputting the amplified signals, and the amplified signals in-phase connected to the outputs of the unit amplifiers 70a and 70b. And a Wilkinson type distributor / combiner 5 for combining and outputting.

Wilkinson-type distributor / combiner 4 includes 90-degree phase delay lines 14a and 14b for delaying the input phase by 90 degrees and outputting, and a resistor 13a.

The Wilkinson divider / combiner 5 includes 90-degree phase delay lines 14c and 14d for delaying the input phase by 90 degrees and outputting the same, and a resistor 13b.

The unit amplifier 70a includes a transistor 1a.
A DC bias supply circuits 9a and 10a connected to the base and collector of the transistor 1a for supplying a DC bias (DC bias), matching circuits 2a and 3a, and a DC voltage cutoff for cutting a DC voltage. And a capacitor 8.

Since the main constituent elements of the unit amplifier 70b are the same as the constituent elements of the unit amplifier 70a described above,
The description will not be repeated here.

Next, the operation of the Wilkinson amplifier 72 will be described. Wilkinson type distributor / combiner 4
The input signal is split into two with the same phase and the split signal is output. The unit amplifiers 70a and 70b respectively receive the two divided signals, amplify the signals, and then output the amplified signals. The Wilkinson type distributor / combiner 5 receives the two amplified signals, combines them in the same phase, and outputs them.

The Wilkinson type divider / combiner 4 divides an input signal into two. The two distributed signals are delayed by 90 ° in phase by the 90 ° phase delay line and then output.

The unit amplifiers 70a and 70b receive the distributed signals and output amplified signals.

The Wilkinson type distributor / combiner 5 receives the amplified signals output from the unit amplifiers 70a and 70b, respectively. The respective amplified signals are delayed in phase by 90 degrees by the 90-degree phase delay lines 14c and 14d, and then combined and output.

Incidentally, the Wilkinson type amplifier 72 can be regarded as a unit amplifier and further combined in parallel. Similarly, 2 ⁿ pieces (n = 1, 2, ...) Can be combined in parallel. The Wilkinson amplifier 72 allows the power of the input signal to be doubled. [Prior Art 2] Referring to FIG. 8, a balanced amplifier 8
Reference numeral 4 denotes a 90-degree hybrid 80 for splitting an input signal into two with a phase difference of 90 degrees and outputting a split signal;
Unit amplifier 70a connected to the output of the hybrid 80 to amplify the distributed signal and output the amplified signal.
And 70b, and a 90-degree hybrid 82 that is connected to the outputs of the unit amplifiers 70a and 70b and returns the amplified signals with a phase difference of 90 degrees to the phase difference of 0 degrees to synthesize and output.

The 90-degree hybrid 80 is a 90-degree phase delay line 1 for delaying the input phase by 90 degrees and outputting it.
4e, 14f, 14g and 14y, and a terminating resistor 17.

The 90-degree hybrid 82 is a 90-degree phase delay line 1 for delaying the input phase by 90 degrees and outputting it.
4h, 14i, 14j and 14z, and a terminating resistor 17.

Main components of unit amplifiers 70a and 70b are similar to those described with reference to FIG. 7, and therefore description thereof will not be repeated here.

Next, the operation of the balanced amplifier 84 will be described. The 90-degree hybrid 80 distributes an input signal and outputs two distribution signals having 90-degree phases different from each other.
The unit amplifiers 70a and 70b respectively receive the two distributed signals, amplify the amplified signals, and output the amplified signals.
The 90-degree hybrid 82 receives the two amplified signals, returns them to the same phase, and then synthesizes and outputs them.

The 90-degree hybrid 80 outputs two input signals.
Distribute to one. One of the divided signals is delayed by 90 ° in phase by the 90 ° phase delay line 14e and then output. The other distributed signal is the phase delay circuits 14y and 14y.
The signal is delayed by 90 degrees at f and then output. Therefore, the other distributed signal is 180 degrees out of phase with the input signal. Therefore, the phase difference between the one distributed signal and the other distributed signal is 90 degrees.

The unit amplifiers 70a and 70b respectively receive the distributed signals and output amplified signals. The distribution signal input to the unit amplifier 70b is delayed in phase by 90 degrees from the distribution signal input to the unit amplifier 70a. Therefore, the same relationship is maintained between the amplified signals.

The 90-degree hybrid 82 is a unit amplifier 7
The amplified signals output from 0a and 70b are input.
The amplified signal output from the unit amplifier 70a (the phase of which is delayed by 90 degrees from the input signal) is delayed by 90 degrees by the 90-degree phase delay lines 14h and 14z. The amplified signal output from the unit amplifier 70b (the phase of which is delayed by 180 degrees from the input signal) is delayed in phase by the 90-degree phase delay line 14j. The amplified signals with the two phases delayed are combined and output. Since the amplified signals with the two phases delayed are each 270 degrees out of phase with the input signal, the phase difference between the two amplified signals is 0.
It becomes degree.

The balanced amplifier 84 can be regarded as a unit amplifier and can be further combined in parallel. Similarly,
2 ⁿ pieces (n = 1, 2, ...) Can be combined in parallel.

The balanced amplifier 84 allows the power of the input signal to be doubled. In the balanced amplifier 84, the reflected powers output from the unit amplifiers 70a and 70b are all 90-degree hybrids 80 and 82.
Are respectively absorbed by the respective terminating resistors 17 included in.
Therefore, even when the input / output impedances of the unit amplifiers 70a and 70b deviate from 50Ω, the input / output impedance of the balanced amplifier 84 is almost 50.
It has the advantage of being kept at Ω. The numerical value of 50Ω is an input / output impedance used in commercially available measuring devices, amplifiers, mixers and the like. [Prior Art 3] Referring to FIG. 9, an image rejection mixer 96 includes a Wilkinson distribution combiner 4 for distributing and outputting an LO signal (local oscillation signal) into two in-phase signals, and an RF signal. A 90-degree hybrid 80 for dividing (high-frequency signal) into two with a phase difference of 90 degrees and outputting a distribution signal, and one output of the Wilkinson distribution / combiner 4 and one output of the 90-degree hybrid 80. A unit mixer 90 which is connected and outputs an IF signal (intermediate frequency signal) after frequency-combining the outputs.
And a unit mixer 92 connected to the other output of the Wilkinson divider / combiner 4 and the other output of the 90-degree hybrid 80 to output an IF signal after frequency-combining the respective outputs, and the respective IF signals. 90 for combining 90 degrees and outputting in-phase output and phase difference output
And a degree synthesizer 94.

Wilkinson type partition synthesizers 4 and 90
The main components of the degree hybrid 80 are similar to those described with reference to FIGS. 7 and 8, respectively, and therefore description thereof will not be repeated here.

The unit mixer 90 includes a transistor 1b and
DC bias supply circuits 9b and 10b connected to the base and collector of the transistor 1b for supplying DC bias, and matching circuits 2b and 3b,
It includes a matching circuit IF filter 11b and a DC voltage blocking capacitor 8 for blocking a DC voltage.

Since the main constituent elements of unit mixer 92 are similar to the constituent elements of unit mixer 90 described above, the description of the constituent elements will not be repeated here.

Next, the image rejection mixer 96
The operation of will be described. First, the frequency of the LO signal is R
Consider the case where the frequency is lower than the frequency of the F signal. The LO signal is divided into two in-phase by the Wilkinson divider / combiner 4. RF signal is 90 by 90 degree hybrid 80
It is divided into two with a phase difference of degrees. The unit mixer 92 frequency-synthesizes one output signal output from the Wilkinson divider / combiner 4 and one output signal output from the 90-degree hybrid 80, and outputs an IF signal.
The unit mixer 90 performs frequency synthesis of the other output signal output from the Wilkinson type distributor / combiner 4 and the other output signal output from the 90-degree hybrid 80,
Output IF signal. The two IF signals have a phase difference of 90 degrees. Therefore, the two IF signals are combined by the 90-degree synthesizer 94.
When combined with each other, a combined signal of the LO signal and the RF signal is output to the phase difference output. Further, nothing is output to the in-phase output. It has two IFs with 90 degree phase difference.
Since the signals are converted into two IF signals having a phase difference of 180 degrees by the 90-degree combiner 94 and then combined, 2
This is because the two IF signals cancel each other and no output occurs.

Next, consider the case where the frequency of the LO signal is higher than that of the RF signal. In this case, the unit mixer 90
The relationship of the phase difference between the two IF signals output from the signals and 92 is opposite to the relationship of the phase difference between the two IF signals when the frequency of the LO signal is lower than the frequency of the RF signal. Therefore, the combined signal of the LO signal and the RF signal is output to the in-phase output of the 90-degree combiner 94, and nothing is output to the phase difference output.

With such an image rejection mixer 96, the output terminal can be determined depending on whether the frequency of the LO signal is above or below the frequency of the RF signal. [Prior Art 4] Referring to FIG. 10, single-balance mixer 104 divides an input signal of frequency f1 into two in an opposite phase (phase difference is 180 degrees), outputs a divided signal, and outputs frequency f2. 180 degree hybrid 60 for distributing the LO signal in the same phase and outputting the distribution signal, and frequency combining and amplifying one distribution signal of the input signal of frequency f1 and one distribution signal of the LO signal of frequency f2. Frequency f
Unit amplifier 70a for outputting the amplified signal of 1-f2
And a unit amplifier 70b for frequency-synthesizing and amplifying the other distribution signal of the input signal of the frequency f1 and the other distribution signal of the LO signal of the frequency f2 to output an amplified signal of the frequencies f1-f2, and their amplification. It includes a 180-degree hybrid 62 for receiving a signal, reducing the phase difference between two amplified signals to 0 degree, and then outputting the combined signal, and a terminating resistor 17.

The 180-degree hybrid 60 is a 90-degree phase delay line 14k, 14l, 14m, 14n, 14p and 14q for delaying the input phase by 90 degrees and outputting it.
including.

The 180-degree hybrid 62 is a 90-degree phase delay line 14r, 14s, 14u, 14v, 14w and 14x for delaying the input phase by 90 degrees and outputting it.
including.

The main components of unit amplifiers 70a and 70b are similar to those described with reference to FIG. 7, and therefore description thereof will not be repeated here.

Next, the operation of the single balance mixer 104 will be described. The input signal having the frequency f1 is distributed by the 180-degree hybrid 60, and two distribution signals having phases different by 180 degrees are output. Also, L of frequency f2
The O signal is distributed by the 180-degree hybrid 60, and two in-phase distribution signals are output. Unit amplifier 70a
Is a distribution signal of one of the input signals of the frequency f1 and the frequency f
After frequency-combining the 2 LO signals with one distribution signal and amplifying, the amplified signal of frequencies f1-f2 is output.
The unit amplifier 70b frequency-synthesizes and amplifies the other distribution signal of the input signal of the frequency f1 and the other distribution signal of the LO signal of the frequency f2, and outputs the amplified signal of the frequencies f1-f2. These two signals are 180 degrees out of phase. The two amplified signals are phase-converted by the 180-degree hybrid 62 so that the signal components of the frequencies f1 and f2 have the same phase, and are combined to output a combined signal.

The amplified signals respectively output from the unit amplifiers 70a and 70b include LO signal components. However, this signal component is a 180 degree hybrid 6
Since the two phases are combined in reverse phase, they cancel each other out and are not output. [Prior Art 5] Referring to FIG. 11, a double balance mixer 110 divides an input signal into two in-phase and outputs a distribution signal, and a Wilkinson distribution combiner 4.
1 for distributing the LO signal in opposite phase and outputting the distribution signal
80 degree hybrid 60 and 180 degree hybrid 60
Distribution signal for one side and Wilkinson distribution combiner 4
A single balance mixer 104a for receiving the output of one of the
Receiving the other output of the 80-degree hybrid 60 and the other output of the Wilkinson type distributor / combiner 4, the single balance mixer 104b for outputting a combined signal after frequency conversion and the single balance mixers 104a and 104b respectively output. Received the combined signal
It includes a 180-degree hybrid 62 for returning two combined signals to the same phase and then combining and outputting the combined signals, and a terminating resistor 17.

The main components of 180-degree hybrids 60 and 62 are similar to those of 180-degree hybrids 60 and 62 described with reference to FIG. 10, and therefore description thereof will not be repeated.

Main components of the Wilkinson type distributor / combiner 4 are similar to those of the Wilkinson type distributor / combiner 4 described with reference to FIG. 7, and therefore description thereof will not be repeated. Single balance mixers 104a and 10
The main components of 4b are similar to those of single balance mixer 104 described with reference to FIG. 10, and therefore description thereof will not be repeated.

Next, the operation of the double balance mixer 110 will be described. The input signal of the frequency f1 is divided into two in-phase by the Wilkinson distribution combiner 4 and the divided signal is output. The LO signal of frequency f2 is distributed by the 180 degree hybrid 60 into two distribution signals so that the phase difference is 180 degrees. Single balance mixer 104a
Receives one distribution signal of the input signal of frequency f1 and one distribution signal of the LO signal of frequency f2,
The synthetic signal of f2 is output. Single balance mixer 1
04b receives the other distribution signal of the input signal of frequency f1 and the other distribution signal of the LO signal of frequency f2, and outputs a combined signal of frequencies f1-f2. Phase difference 180 degrees 2
180 degree hybrid 62 of two combined signals with zero phase difference
After synthesizing each time, a synthesized signal is output.

Single-balance mixers 104a and 1
The operation of 04b is the same as that of single balance mixer 104 described with reference to FIG. 10, and therefore description thereof will not be repeated.

Transistors 1a, 1b and 1 which form unit amplifiers 70a, 70b, 70c and 70d, respectively.
For each base and collector of c and 1d,
One DC bias supply circuit is attached to each. Therefore, eight DC bias supply circuits are required as the double balance mixer 110.

[0039]

However, the conventional high frequency circuit has the following problems. In order to operate the bipolar transistors and FETs forming the unit amplifier or unit mixer, it is usually necessary to supply two types of DC bias. For example, GaAs (gallium arsenide)
When the emitter of the system hetro bipolar transistor (HBT) is grounded, it is necessary to apply a DC voltage of about 1.3 to 1.5 V to the base and about 3 V to the collector. Therefore, DC is applied to each contact of the transistor or FET.
Was supplying the bias. When two unit amplifiers or unit mixers are arranged in parallel to form a parallel amplifier or frequency converter, a total of four DC bias supply circuits are required. Similarly, use two unit amplifiers or unit mixers.
^{When n} pieces are arranged in parallel, 2 × 2 ⁿ pieces of DC bias supply circuits are required. On the other hand, the frequency used is 1G
As the frequency increases from about Hz (gigahertz) to about 10 GHz, so-called MMIC (monolithic microwave integrated circuit) in which a high frequency circuit is integrated on one semiconductor chip has been actively developed. When these parallel amplifiers and frequency converters are implemented as MMICs, the layout becomes complicated and the area occupied by the bias supply lines and the DC voltage supply pads becomes large, which causes a cost increase. Further, when the number of unit amplifiers or unit mixers is four or more, the number of intersections of the high frequency signal line and the DC bias supply circuit increases. Usually, at these intersections, one track is bridged over the other,
A so-called air bridge is formed to reduce the influence of mutual lines. However, as the frequency increases, the capacitance between the two lines at the intersection cannot be ignored, and the mutual influence between the two lines increases. This causes deterioration of the characteristics of the high frequency circuit.

The present invention has been made to solve the above problems, and the invention according to any one of claims 1 to 9 provides a high-frequency circuit having a simple circuit configuration and high frequency characteristics. The purpose is to provide.

[0041]

According to a first aspect of the present invention, there is provided a high frequency circuit comprising: a first high frequency component passing means for passing only a high frequency component of an input signal; and a first high frequency component passing means. Distributing means connected to the output, for distributing the output of the first high-frequency component passing means into a plurality of outputs with a certain phase difference, and connected to the output of the distributing means, amplifying the output of the distributing means, respectively. A plurality of amplifying means for outputting, connected to the outputs of the plurality of amplifying means, a combining means for combining and outputting the outputs of the plurality of amplifying means with a certain phase difference, and connected to the output of the combining means, A second high-frequency component passing means for passing only the high-frequency component of the output of the synthesizing means and a plurality of amplifying means connected to the distributing means and / or the synthesizing means, respectively. A and a DC bias supply means for supplying direct current bias, respectively.

In the high frequency circuit according to the first aspect of the present invention, since the DC bias is supplied to the plurality of amplifying means via the distributing means and / or the combining means, the number of the DC bias supplying means is minimized. be able to. Therefore, the circuit configuration can be simplified and the time required for layout design can be shortened. Moreover, since the mutual influence of the high-frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without disturbing the balanced state of the high-frequency signal.

In the high frequency circuit according to the second aspect of the invention, in addition to the configuration of the first aspect of the invention, the distribution means is connected to the output of the first high frequency component passing means,
Includes an in-phase distributor for distributing and outputting the output of the high-frequency component passing means into a plurality of parts with a phase difference of 0 degree, and the combining means is connected to the outputs of the plurality of amplifying means and outputs the outputs of the plurality of amplifying means. An in-phase combiner for combining and outputting with a phase difference of 0 degree is included.

In the high frequency circuit according to a third aspect of the invention, in addition to the configuration of the first aspect of the invention, the distribution means is connected to the output of the first high frequency component passing means,
Includes a 90-degree distributor for dividing and outputting the output of the high-frequency component passing means in two with a phase difference of 90 degrees, the plurality of amplifying means includes two amplifying means, and the combining means includes two amplifying means. And a 90-degree combiner for combining and outputting the outputs of two amplifying means having a phase difference of 90 degrees with a phase difference of 0 degrees.

A high-frequency circuit according to a fourth aspect of the present invention is connected to a plurality of high-frequency component passing means for passing only high-frequency components of a plurality of input signals and outputs of the high-frequency component passing means, respectively. , A plurality of distributing means for distributing and outputting the output of the high-frequency component passing means into a plurality with a certain phase difference, and a certain output of each of the plurality of distributing means, and a certain output of each of the plurality of distributing means. A plurality of mixers for frequency-synthesizing and outputting, and a synthesizing unit connected to outputs of the plurality of mixers, for synthesizing and outputting the outputs of the plurality of mixers with a certain phase difference, and a plurality of distributing units or synthesizing units. And DC bias supply means for respectively supplying DC bias to the plurality of mixers via the plurality of distributing means or the combining means.

In the high frequency circuit according to the fourth aspect of the present invention, since the DC bias is supplied to the plurality of mixers via the plurality of distributing means or the combining means, the number of the DC bias supplying means can be minimized. You can For this reason,
The circuit configuration can be simplified and the time required for layout design can be shortened. Moreover, since the mutual influence of the high-frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without disturbing the balanced state of the high-frequency signal.

In the high frequency circuit according to the invention described in claim 5, in addition to the configuration of the invention described in claim 4, the plurality of input signals include an input signal of frequency f1 and an input signal of frequency f2. , The plurality of high frequency component passing means have a frequency f1
A plurality of distributing means including a first high-frequency component passing means for passing only the high-frequency component of the input signal and a second high-frequency component passing means for passing only the high-frequency component of the input signal of frequency f2. Is connected to the output of the first high-frequency component passing means, divides the output of the first high-frequency component passing means into two with a phase difference of 90 degrees, and outputs the 90-degree distributor; The output of the second high-frequency component passing means is connected to the output of the component passing means and the output of the second high-frequency component passing means is set to 2 degrees with a phase difference of 0 degree.
A plurality of mixers connected to one output of the first distributing means and one output of the second distributing means, A first unit mixer for frequency-synthesizing and outputting one output and one output of the second distributing means, and the other output of the first distributing means and the other output of the second distributing means. A second unit mixer for frequency-combining and outputting the other output of the first distributing unit and the other output of the second distributing unit, and the combining unit outputs the output of the first unit mixer. And the output of the second unit mixer, the signal components of | f1-f2 | of the output of the first unit mixer and the output of the second unit mixer, which have a phase difference of 90 degrees, have a phase difference of 0 degree. It includes a 90-degree combiner for combining and outputting.

In the high frequency circuit according to the invention described in claim 6, in addition to the configuration of the invention described in claim 4, the plurality of input signals include an input signal of frequency f1 and an input signal of frequency f2. , The plurality of high frequency component passing means have a frequency f1
A plurality of distributing means including a first high-frequency component passing means for passing only the high-frequency component of the input signal and a second high-frequency component passing means for passing only the high-frequency component of the input signal of frequency f2. Is connected to the output of the first high-frequency component passing means, divides the output of the first high-frequency component passing means into two with a phase difference of 180 degrees, and outputs the two. The output of the second high-frequency component passing means is connected to the output of the component passing means and the output of the second high-frequency component passing means is set to 2 degrees with a phase difference of 0 degree.
A plurality of mixers connected to one output of the first distributing means and one output of the second distributing means, and one of the first distributing means is provided. Connected to the first unit mixer for frequency-synthesizing and outputting the output of the first distributing means and the output of one of the second distributing means, and the other output of the first distributing means and the other output of the second distributing means. , A second for frequency-synthesizing and outputting the other output of the first distributing means and the other output of the second distributing means
Unit mixer connected to the output of the first unit mixer and the output of the second unit mixer, and the output of the first unit mixer and the output of the second unit mixer with a phase difference of 180 degrees. And an anti-phase combiner for combining and outputting the respective | f1-f2 | signal components with a phase difference of 0 degree.

A high-frequency circuit according to a seventh aspect of the present invention is connected to a plurality of high-frequency component passing means for passing only high-frequency signals of a plurality of input signals and outputs of the plurality of high-frequency component passing means, respectively. The output of the high-frequency component passing means is divided into a plurality of pieces with a certain phase difference and is connected to a plurality of distributing means for outputting the plurality of outputs, and a certain output of each of the plurality of distributing means, and a certain output of each of the plurality of distributing means. Receiving a plurality of frequency conversion means for performing frequency conversion and outputting each, and connected to the outputs of the plurality of frequency conversion means, and for combining and outputting the outputs of the plurality of frequency conversion means with a certain phase difference. The synthesizing means and the plurality of distributing means or the synthesizing means are respectively connected, and the DC bias is supplied to the plurality of frequency converting means via the plurality of distributing means or the synthesizing means. And a DC bias supply means for.

In the high frequency circuit according to the seventh aspect of the present invention, since the DC bias is supplied to the plurality of frequency converting means via the plurality of distributing means or the combining means, the number of the DC bias supplying means is minimized. You can hold it down. Therefore, the circuit configuration can be simplified and the time required for layout design can be shortened. Moreover, since the mutual influence of the high-frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high-frequency circuit are improved, and the chip area can be reduced without disturbing the balanced state of the high-frequency signal.

In the high frequency circuit according to the invention described in claim 8, in addition to the configuration of the invention described in claim 7, the plurality of input signals include an input signal of frequency f1 and an input signal of frequency f2. , The plurality of high frequency component passing means have a frequency f1
A plurality of distributing means including a first high-frequency component passing means for passing only the high-frequency component of the input signal and a second high-frequency component passing means for passing only the high-frequency component of the input signal of frequency f2. Is connected to the output of the first high-frequency component passing means, and divides the output of the first high-frequency component passing means into two with a certain phase difference and outputs the divided first and second high-frequency components. It is connected to the output of the component passing means and outputs the output of the second high frequency component passing means with a certain phase difference of 2
A second distribution means for distributing and outputting the two
The plurality of frequency conversion means are connected to one output of the first distribution means and one output of the second distribution means, and connect one output of the first distribution means and one output of the second distribution means. First frequency conversion means for receiving and performing frequency conversion and outputting, and the other output of the first distribution means and the other output of the second distribution means, and the other of the first distribution means. A second frequency converting means for receiving and outputting the output and the other output of the second distributing means, and performing the frequency conversion, and the combining means includes the output of the first frequency converting means and the second frequency. Connected to the output of the conversion means,
A phase difference synthesizing unit for synthesizing and outputting the output of the first frequency converting unit and the output of the second frequency converting unit with a certain phase difference is included.

In the high frequency circuit according to the invention described in claim 9, in addition to the configuration of the invention described in claim 8, the first distributing means is connected to the output of the first high frequency component passing means,
It includes an in-phase distributor for dividing and outputting the output of the first high-frequency component passing means into two with a phase difference of 0 degrees, and the second distributing means is connected to the output of the second high-frequency component passing means. ,
The output of the second high-frequency component passing means is set to 2 with a phase difference of 180 degrees.
And a phase difference synthesizing means connected to the output of the first frequency converting means and the output of the second frequency converting means and having a phase difference of 180 degrees. And an anti-phase combiner for combining and outputting the output of the frequency converting means and the output of the second frequency converting means with a phase difference of 0 degree.

[0053]

DESCRIPTION OF THE PREFERRED EMBODIMENTS High frequency circuits according to various embodiments of the present invention will be described below with reference to the drawings. In the following description, the same parts are designated by the same reference numerals. Since their names and functions are also the same, repeated description will be omitted as appropriate. [First Embodiment] Referring to FIG. 1, a Wilkinson amplifier 15 of the first embodiment includes a Wilkinson divider / combiner 4 for dividing an input signal into two in-phase and outputting a divided signal. Unit amplifiers 12a and 12b connected to the outputs of the Wilkinson type distributor / combiners 4 for amplifying the distributed signals and outputting the amplified signals, respectively, and connected to the unit amplifiers 12a and 12b to combine and output the amplified signals in phase. Wilkinson type distributor / combiner 5
, A DC bias supply circuit 9 for supplying a DC bias to the bases of transistors 1a and 1b, which will be described later, via the Wilkinson distribution combiner 4, and a transistor 1 via the Wilkinson distribution combiner 5.
It includes a DC bias supply circuit 10 for supplying a DC bias to the collectors of a and 1b, respectively, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The Wilkinson divider / combiner 4 includes 90-degree phase delay lines 14a and 14b for delaying the input phase by 90 degrees and outputting, and a resistor 13a. Wilkinson-type distributor / combiner 5 includes 90-degree phase delay lines 14c and 14d for delaying the input phase by 90 degrees and outputting the same, and a resistor 13b. 90 degree phase delay line 1
4a, 14b, 14c and 14d are composed of a microstrip line, a coplanar line or the like. The unit amplifier 12a includes a transistor 1a and matching circuits 2a and 3a.

The unit amplifier 12b is composed of the transistor 1b.
And matching circuits 2b and 3b.

Next, the operation of the Wilkinson amplifier 15 will be described. The input signal is split into two by the Wilkinson divider / combiner 4 with the same phase. The two distributed signals are respectively input to the unit amplifiers 12a and 12b and amplified respectively. The two amplified signals are input to the Wilkinson divider / combiner 5, combined in the same phase, and output.

The Wilkinson divider / combiner 4 divides the input signal into two. The two distributed signals are separated by 90 ° by the 90 ° phase delay lines 14a and 14b, respectively.
It is output after the phase is delayed.

The unit amplifiers 12a and 12b receive the distributed signals and output amplified signals, respectively.

Wilkinson type distributor / combiner 5 receives the amplified signals output from unit amplifiers 12a and 12b. Each amplified signal is a 90 degree phase delay line 14c.
And 14d, the phases are delayed by 90 degrees, respectively, and then combined and output.

DC biases are supplied to the transistors 1a and 1b forming the unit amplifiers 12a and 12b, respectively, from DC bias supply circuits 9 and 10 connected to the Wilkinson type distributor / combiners 4 and 5, respectively. Further, the DC voltage is blocked by the DC voltage blocking capacitor 8 provided at the input / output port, and only the high frequency signal can be passed.

In the Wilkinson type amplifier 15, by supplying the DC bias before and after distributing the high frequency signal, the number of the DC bias supply circuits which has been required to be four in the prior art becomes two. Therefore, the circuit configuration can be simplified and the time required for layout design can be shortened. Also,
Since the mutual influence of the high frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high frequency circuit are improved and the chip area can be reduced without disturbing the balance state of the high frequency signal. [Second Embodiment] Referring to FIG. 2, a balanced amplifier 24 according to a second embodiment is a 90-degree hybrid 20 for dividing an input signal into two with a phase difference of 90 degrees and outputting a divided signal. And unit amplifiers 12a and 12b connected to the two outputs of the 90-degree hybrid 20 for amplifying the distributed signal and outputting the amplified signal, respectively.
of the unit amplifiers 12a and 12b via the 90-degree hybrid 22 and the 90-degree hybrid 20 which are connected to the outputs of a and 12b to return the amplified signals having the phase difference of 90 degrees to the phase difference of 0 degree and combine and output. DC bias supply circuit 9 for supplying a DC bias to the bases of the respective transistors 1a and 1b.
And the transistor 1 via 90 degree hybrid 22
It includes a DC bias supply circuit 10 for supplying a DC bias to the collectors of a and 1b, respectively, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The 90-degree hybrid 20 is a 90-degree phase delay line 1 for delaying the input phase by 90 degrees and outputting it.
4e, 14f, 14g and 21a, and a terminating resistor 17. A DC bias supply circuit 9 is connected to the 90-degree phase delay line 21a.

The 90-degree hybrid 22 is a 90-degree phase delay line 1 for delaying the input phase by 90 degrees and outputting it.
4h, 14i, 14j and 21b, and a terminating resistor 17.

DC bias supply circuits 9 and 10 are connected to the 90-degree phase delay lines 21a and 21b, respectively. 90 degree phase delay lines 14e, 14f, 14
g, 14h, 14i, 14j, 21a and 21b are
It is composed of microstrip lines and coplanar lines.

Next, the operation of the balanced amplifier 24 will be described. The input signal is split by the 90-degree hybrid 20 into two split signals having different 90-degree phases. Two
The two divided signals are respectively input to the unit amplifiers 12a and 12b, amplified, and then output as amplified signals. The two amplified signals are 90 degree hybrid 22
Are input to, and are returned to the same phase, and then combined.

The 90-degree hybrid 20 outputs the input signal 2
Distribute to one. The operation is similar to that of 90-degree hybrid 80 described with reference to FIG. 8, and therefore the description thereof will not be repeated here.

Each of the unit amplifiers 12a and 12b receives the distributed signal and outputs an amplified signal. The distribution signal input to the unit amplifier 12b is the unit amplifier 12a.
The phase is delayed by 90 degrees with respect to the distribution signal input to.
Therefore, the same relationship is maintained between the amplified signals.

The 90-degree hybrid 22 is a unit amplifier 1
The amplified signals output from 2a and 12b are input, the respective signals are made to have the same phase, and then combined and output. The operation has been described with reference to FIG.
Since it is similar to the 0-degree hybrid 82, the description thereof will not be repeated here.

DC biases are supplied to the transistors 1a and 1b forming the unit amplifiers 12a and 12b from the DC bias supply circuits 9 and 10 connected to the 90-degree hybrids 20 and 22, respectively. Further, the DC voltage is blocked by the DC voltage blocking capacitor 8 provided at the input / output port, and only the high frequency signal can be passed. Furthermore, the terminating resistor 1
Due to the DC voltage blocking capacitor 8 provided between 7 and the ground, the terminating resistor 17 functions as a resistance for a high frequency signal and as an opening for a DC current.

In the balanced type amplifier 24, by supplying the DC bias before and after distributing the high frequency signal, the number of the DC bias supplying circuits which has been required to be four in the prior art becomes two. Therefore, the circuit configuration can be simplified and the time required for layout design can be shortened. Further, since the mutual influence of the high frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high frequency circuit are improved and the chip area can be reduced without breaking the balance state of the high frequency signal. [Third Embodiment] Referring to FIG. 3, an image rejection mixer 36 according to a third embodiment includes a Wilkinson divider / combiner 4 for dividing an LO signal into two in-phase and outputting the same. A 90-degree hybrid 20 for splitting a signal into two with a phase difference of 90 degrees and outputting a split signal.
And a unit mixer 30a that is connected to one output of the Wilkinson type distributor / combiner 4 and one output of the 90-degree hybrid 20, and outputs the IF signal (intermediate frequency signal) after frequency-combining the respective outputs. , The other output of the Wilkinson type distributor / combiner 4 and the other output of the 90-degree hybrid 20, and after frequency-combining the respective outputs, a unit mixer 30b for outputting an IF signal and the respective IF signals are output. 90-degree combiner 34 for combining and outputting 90-degree, and 90-degree hybrid 2
A DC bias supply circuit 9 for supplying a DC bias to the bases of the transistors 1a and 1b of the respective constituents of the unit mixers 30a and 30b, which are connected to 0 through the 90-degree hybrid 20, and a Wilkinson type distribution circuit. The transistors 1a and 1 are connected to the combiner 4 and pass through the Wilkinson distribution combiner 4.
It includes a DC bias supply circuit 10 for supplying a DC bias to each collector of b, and a DC voltage cutoff capacitor 8 for cutting off a DC voltage.

Since the main components of 90-degree hybrid 20 have been described with reference to FIG. 2, description thereof will not be repeated here.

The main components of the Wilkinson type distributor / combiner 4 have been described with reference to FIG. 7, and the description thereof will not be repeated here.

The unit mixer 30a includes the transistor 1a.
And matching circuits 2a and 3a, matching circuit IF filter 32a, and DC voltage cut-off capacitor 8 for cutting DC voltage. The unit mixer 30b includes a transistor 1b, matching circuits 2b and 3b, a matching circuit IF filter 32b, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The matching circuits 2a, 2b, 3a and 3b have a circuit configuration in which there is direct current conduction between the input and the output. Unit mixer 3
In 0a and 30b, matching circuits 2a, 2b,
Although an example in which only 3a and 3b are arranged is shown, various configurations such as a filter and a phase shifter can be considered in addition to the matching circuit.

Next, the image rejection mixer 36
The operation of will be described. The LO signal is split into two split signals in phase by the Wilkinson split / combiner 4. The RF signal is split by the 90-degree hybrid 20 into two split signals with a phase difference of 90 degrees. Unit mixer 3
0a is output from one of the distributed signal and the 90 degree hybrid 20 output from Wilkinson combiner 4
Performs frequency conversion and one distribution signal that outputs an IF signal. The unit mixer 30b frequency-synthesizes the other distribution signal output from the Wilkinson distribution combiner 4 and the other distribution signal output from the 90-degree hybrid 20, and outputs an IF signal. 90 degree synthesizer 34
Receives the two IF signals, synthesizes them by 90 degrees, and outputs a synthesized signal.

Transistors 1a and 1b forming unit mixers 30a and 30b, respectively, are connected to Wilkinson type distributor / combiner 4 and 90-degree hybrid 20 from bias supply lines 10 and 9, respectively.
The DC bias is supplied via the Wilkinson type distributor / combiner 4 and the 90-degree hybrid 20, respectively. Further, the DC bias is cut off by the DC voltage cut-off capacitor 8 provided at the two input ports,
Only high frequency signals can be passed. Further, due to the DC voltage blocking capacitor 8 provided between the terminating resistor 17 and the ground, the terminating resistor 17 functions as a resistance for a high frequency signal and as an open circuit for a DC current.

In the image rejection mixer 36,
By supplying the DC bias before and after distributing the high frequency signal, the number of the DC bias supply circuits, which conventionally required four, becomes two. Therefore, the circuit configuration can be simplified and the time required for layout design can be shortened. Further, since the mutual influence of the high frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high frequency circuit are improved and the chip area can be reduced without breaking the balance state of the high frequency signal. [Fourth Embodiment] With reference to FIG. 4, an image rejection mixer 38 according to a fourth embodiment includes a Wilkinson divider / combiner 4 for dividing and outputting an RF signal into two signals in phase. A 90-degree hybrid 20 for splitting a signal into two with a phase difference of 90 degrees and outputting a split signal.
, A unit mixer 30a connected to one output of the Wilkinson type distributor / combiner 4 and one output of the 90-degree hybrid 20, frequency-synthesizing the respective outputs, and then outputting an IF signal, and a Wilkinson type distributor / combiner. Connected to the other output of the instrument 4 and the other output of the 90-degree hybrid 20, and after frequency-combining the respective outputs,
The unit mixer 30b for outputting the IF signal, the 90-degree combiner 34 for combining the respective IF signals by 90 degrees and outputting the combined IF signal, and the 90-degree hybrid 20 are connected to each other.
Connected to the Wilkinson type distributor / combiner 4 and the DC bias supply circuit 10 for supplying DC bias to the bases of the transistors 1a and 1b of the constituent elements of the unit mixers 30a and 30b, respectively. , Via the Wilkinson type distributor / combiner 4 to the collectors of the transistors 1a and 1b.
A DC bias supply circuit 9 for supplying a C bias, and a DC voltage cutoff capacitor 8 for cutting off a DC voltage are included.

Since the main components of 90-degree hybrid 20 have been described with reference to FIG. 2, description thereof will not be repeated here.

Since the main components of the Wilkinson type distributor / combiner 4 have been described with reference to FIG. 7, the description thereof will not be repeated here.

The main constituent elements of the unit mixers 30a and 30b have been described with reference to FIG.
The description will not be repeated here.

Next, the image rejection mixer 38
The operation of will be described. The RF signal is split into two split signals in phase by the Wilkinson split / combiner 4. The LO signal is split by the 90-degree hybrid 20 into two split signals with a phase difference of 90 degrees. Unit mixer 3
0a performs frequency synthesis of one distribution signal output from the Wilkinson distribution / combiner 4 and one distribution signal output from the 90-degree hybrid 20, and outputs an IF signal. The unit mixer 30b frequency-synthesizes the other distribution signal output from the Wilkinson distribution combiner 4 and the other distribution signal output from the 90-degree hybrid 20, and outputs an IF signal. 90 degree synthesizer 34
Receives the two IF signals, synthesizes them by 90 degrees, and outputs a synthesized signal.

Transistors 1a and 1b constituting unit mixers 30a and 30b, respectively, are connected to 90-degree hybrid 20 and Wilkinson type distributor / combiner 4 from bias supply lines 10 and 9, respectively.
The DC bias is supplied via the 90-degree hybrid 20 and the Wilkinson type distributor / combiner 4, respectively. Further, the DC bias is cut off by the DC voltage cut-off capacitor 8 provided at the two input ports,
Only high frequency signals can be passed. Further, due to the DC voltage blocking capacitor 8 provided between the terminating resistor 17 and the ground, the terminating resistor 17 functions as a resistance for a high frequency signal and as an open circuit for a DC current.

In the image rejection mixer 38,
By supplying the DC bias before and after distributing the high frequency signal, the number of the DC bias supply circuits, which conventionally required four, becomes two. Therefore, the circuit configuration can be simplified and the time required for layout design can be shortened. Further, since the mutual influence of the high frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high frequency circuit are improved and the chip area can be reduced without breaking the balance state of the high frequency signal. [Fifth Embodiment] Referring to FIG. 5, single-balance mixer 54 according to the fifth embodiment divides an input signal of frequency f1 into two in opposite phases to output a divided signal, and outputs a signal of frequency f2. A 180-degree hybrid 50 for distributing the LO signal in the same phase and outputting the distribution signal, and frequency combining and amplifying one distribution signal of one of the input signal of frequency f1 and one distribution signal of the LO signal of frequency f2 to obtain a frequency. f1-f
A unit amplifier 12a for outputting an amplified signal of 2 and the other distribution signal of the input signal of frequency f1 and the frequency f2
Unit LO 12b for frequency-combining and amplifying the other distributed signal of the LO signal and outputting an amplified signal of frequencies f1-f2, and the phase difference between these two amplified signals is set to 0 degrees, and then combined. 180 degree hybrid 52 for output and 180 degree hybrid 50 are connected,
Via the hybrid 50, the transistor 1a is a component of each of the unit amplifiers 12a and 12b.
And a DC bias supply circuit 9 for supplying a DC bias to the bases of 1b and 1b, respectively, and connected to a 180 degree hybrid 52, and supplies a DC bias to the collectors of the transistors 1a and 1b via the 180 degree hybrid 52, respectively. DC bias supply circuit 1 for
0, a terminating resistor 17, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The 180-degree hybrid 50 is a 90-degree phase delay line 14k, 14l, 14m, 14n, 14p and 14q for delaying the input phase by 90 degrees and outputting it.
including. The 180 degree hybrid 52 has a phase of 9
90 degree phase delay line 14 for delaying by 0 degree and outputting
r, 14s, 14u, 14v, 14w and 14x.

The unit amplifier 12a is composed of the transistor 1a.
And matching circuits 2a and 3a. Unit amplifier 12
b includes transistor 1b and matching circuits 2b and 3b.

Next, the operation of the single balance mixer 54 will be described. The input signal of the frequency f1 is distributed by the 180-degree hybrid 50, and is distributed to two distribution signals whose phases are different by 180 degrees. The LO signal of frequency f2 is distributed by the 180-degree hybrid 50, and is distributed to two in-phase distribution signals. The unit amplifier 12a frequency-synthesizes and amplifies one distribution signal of the input signal of the frequency f1 and one distribution signal of the LO signal of the frequency f2, and outputs the amplified signal of the frequencies f1-f2. The unit amplifier 12b frequency-synthesizes and amplifies the other distribution signal of the input signal of the frequency f1 and the other distribution signal of the LO signal of the frequency f2, and outputs the amplified signal of the frequencies f1-f2. These signals are 180 degrees out of phase.
The two amplified signals are phase-converted by the 180-degree hybrid 52 so that the signal components of the frequencies f1 and f2 have the same phase, and are combined to output a combined signal.

The amplified signals output from the unit amplifiers 12a and 12b respectively include LO signal components. However, this signal component is a 180 degree hybrid 5
Since the two phases are combined in reverse phase, they cancel each other out and are not output.

Transistors 1a and 1b, which form unit amplifiers 12a and 12b, respectively, have bias supply lines 9 and 10 connected to 180-degree hybrid 50 and 180-degree hybrid 52, respectively.
80 degree hybrid 50 and 180 degree hybrid 5
A DC bias is supplied via each of the two. Further, the DC bias is cut off by the DC voltage cut-off capacitor 8 provided at the input / output port, and only the high frequency signal can be passed. Furthermore, the terminating resistor 1
Due to the DC voltage blocking capacitor 8 provided between 7 and the ground, the terminating resistor 17 functions as a resistance for a high frequency signal and as an opening for a DC current.

In the single balance mixer 54, by supplying the DC bias before and after distributing the high frequency signal, the number of the DC bias supply circuits, which is required to be four in the prior art, becomes two. Therefore, the circuit configuration can be simplified and the time required for layout design can be shortened. Also,
Since the mutual influence of the high frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high frequency circuit are improved and the chip area can be reduced without disturbing the balance state of the high frequency signal. [Sixth Embodiment] With reference to FIG. 6, a double balance mixer 64 according to a sixth embodiment includes a Wilkinson type distributor / combiner 4 for distributing an input signal into two in-phase and outputting a distributed signal. , 180-degree hybrid 60 for dividing the LO signal into two in reverse phase and outputting the divided signal,
A single balanced mixer 54a for receiving one output signal of the 0 degree hybrid 60 and one output of the Wilkinson type distributor / combiner 4 and outputting a synthesized signal after frequency conversion, and the other output of the 180 degree hybrid 60. And a single balance mixer 54b for receiving the other output of the Wilkinson type distributor / combiner 4 to output a combined signal after frequency conversion, and a combined signal output from each of the single balance mixers 54a and 54b. A 180-degree hybrid 62 for returning two combined signals to the same phase and then combining and outputting the combined signals, and the Wilkinson distribution / combiner 4, and via the Wilkinson distribution / combiner 4, the components of the single balance mixer 54a. Transistors 1a and 1b and a single balance The base of the transistor 1c and 1d is a component of the support 54b and the DC bias supply circuit 9 for supplying DC bias to each connected to a 180 degree hybrid 62, 180-degree hybrid 62
Via transistors 1a, 1b, 1c and 1d
A DC bias supply circuit 10 for respectively supplying a DC bias to the collectors of C, a terminating resistor 17, and a DC voltage blocking capacitor 8 for blocking a DC voltage.

The structure of the 180-degree hybrid 60 is shown in FIG.
Since the configuration is the same as that of the 180-degree hybrid 50 described with reference to, the description thereof will not be repeated. The main components of 180-degree hybrid 62 are similar to those of 180-degree hybrid 52 described with reference to FIG. 5, and therefore description thereof will not be repeated. Main components of single balance mixers 54a and 54b are similar to those of single balance mixer 54 described with reference to FIG. 5, and therefore description thereof will not be repeated.

Next, the operation of the double balance mixer 64 will be described. The input signal of the frequency f1 is divided into two in-phase by the Wilkinson distribution combiner 4 and the divided signal is output. The LO signal of frequency f2 is distributed by the 180 degree hybrid 60 into two distribution signals so that the phase difference is 180 degrees. The single balance mixer 54a receives one of the divided signals of the input signal of the frequency f1 and the frequency f2.
Receiving one of the distribution signals of the LO signal of
The composite signal of is output. Single balance mixer 54b
Receives the other distribution signal of the input signal of frequency f1 and the other distribution signal of the LO signal of frequency f2,
The synthetic signal of f2 is output. The combined signal of these two is
Since the phase difference is 180 degrees, the 180 degree hybrid 62
After the phase difference is set to 0 degree and the signals are combined, a combined signal is output.

Single balance mixers 54a and 54
The operation of b is similar to that of single balance mixer 54 described with reference to FIG. 5, and therefore description thereof will not be repeated.

Transistors 12a, 12 constituting unit amplifiers 12a, 12b, 12c, 12d, respectively.
b, 12c and 12d, from the bias supply lines 9 and 10 connected to the Wilkinson distribution combiner 4 and the 180 degree hybrid 62, respectively, via the Wilkinson distribution combiner 4 and the 180 degree hybrid 62, the DC bias. Are supplied respectively. Also,
Capacitor 8 for blocking DC voltage provided at the input / output port
As a result, the DC bias is cut off and only the high frequency signal can be passed. Further, due to the DC voltage blocking capacitor 8 provided between the terminating resistor 17 and the ground, the terminating resistor 17 functions as a resistance for high frequency signals and as an open circuit for DC current.

In the double balance mixer 64, the DC bias supply circuit, which conventionally required eight, is provided by supplying the DC bias before and after distributing the high frequency signal.
Become a book. Therefore, the circuit configuration can be simplified,
The time required for layout design is reduced. Further, since the mutual influence of the high frequency signal line and the DC bias supply circuit is eliminated, the characteristics of the high frequency circuit are improved and the chip area can be reduced without breaking the balance state of the high frequency signal.

The high frequency circuit as shown in the first to sixth embodiments can simplify the circuit structure. Also,
Since the layout becomes easy, the circuit design time is shortened. Further, the characteristics of the high frequency circuit are improved, and the chip area can be reduced without disturbing the balance of the high frequency signals.

[Brief description of drawings]

FIG. 1 is a circuit diagram of a Wilkinson amplifier according to a first embodiment of the present invention.

FIG. 2 is a circuit diagram of a balanced amplifier according to a second embodiment of the present invention.

FIG. 3 is a circuit diagram of an image rejection mixer according to a third embodiment of the present invention.

FIG. 4 is a circuit diagram of an image rejection mixer according to a fourth embodiment of the present invention.

FIG. 5 is a circuit diagram of a single balance mixer according to a fifth embodiment of the present invention.

FIG. 6 is a circuit diagram of a double balance mixer according to a sixth embodiment of the present invention.

FIG. 7 is a circuit diagram of a conventional Wilkinson type amplifier.

FIG. 8 is a circuit diagram of a conventional balanced amplifier.

FIG. 9 is a circuit diagram of a conventional image rejection mixer.

FIG. 10 is a circuit diagram of a conventional single balance mixer.

FIG. 11 is a circuit diagram of a conventional double balance mixer.

[Explanation of symbols] 1a, 1b transistors 2a, 2b, 3a, 3b matching circuit 4,5 Wilkinson type distributor / combiner 8 DC voltage blocking capacitors 9,10 DC bias supply circuit 15 Wilkinson type amplifier

─────────────────────────────────────────────────── ─── Continuation of the front page (58) Fields surveyed (Int.Cl. ⁷ , DB name) H03D 7/18 H03D 7/14 H03F 3/68

Claims (6)

(57) [Claims] 1. A first input signal is distributed in-phase and two outputs are provided.
Wilkinson type distributor / combiner for outputting in-phase distributed signals
And the second input signal is split into two outputs with a phase difference of 90 degrees,
Outputs 1st phase difference distribution signal and 2nd phase difference distribution signal
A 90-degree hybrid and one of the two outputs of the in-phase distribution signal and the first
First intermediate frequency signal by frequency-synthesizing the phase difference distribution signal
A first unit mixer for outputting the second unit, and the other of the two outputs for the in-phase distribution signal and the second unit.
A second intermediate frequency signal obtained by frequency-synthesizing the phase difference distribution signal
A second unit mixer for outputting the first intermediate frequency signal and the second intermediate frequency signal
And a 90-degree combiner for combining and outputting 90 degrees and a 90-degree hive connected to the 90-degree hybrid.
The first unit mixer and the second unit via a lid.
First transition of each component of the unit mixer of
And a DC bias on the first electrode of the second transistor
DC bias supply circuit for first electrode for supplying respective
When the Huy connected to the Wilkinson combiner
The first transistor is transferred via a Lukinson type distributor / combiner.
And a DC electrode on the second electrode of the second transistor.
DC bias supply for the second electrode that supplies each bias
A circuit, an input terminal for the first input signal, and the Wilkinson type
Firstly inserted between the distributor and the combiner to cut off DC voltage
Input signal input terminal DC cutoff capacitor, the second input signal input terminal and the 90 degree hybrid.
The second input signal that is inserted between the
DC voltage is cut off at the DC input blocking capacitor of the signal input terminal and the output terminal of the first intermediate frequency signal
A first intermediate frequency signal output end DC cutoff capacitor and a second intermediate frequency signal output end cut off DC voltage
A second intermediate frequency signal output terminal DC blocking capacitor, the first unit mixer and the second unit mixer
Includes terminating resistors that absorb the output reflected power.
High frequency circuit forming an image rejection mixer
Road. 2. The first input signal is output twice with a phase difference of 90 degrees.
The first phase difference distribution signal and the second phase difference
A 90-degree hybrid that outputs a split signal and a 2-output in-phase split signal that splits the second input signal in phase
And a Wilkinson type distributor / combiner for outputting the in-phase distributor signal of one of the two outputs and the first unit.
First intermediate frequency signal by frequency-synthesizing the phase difference distribution signal
A first unit mixer for outputting the second unit, and the other of the two outputs for the in-phase distribution signal and the second unit.
A second intermediate frequency signal obtained by frequency-synthesizing the phase difference distribution signal
A second unit mixer for outputting the first intermediate frequency signal and the second intermediate frequency signal
And a 90-degree combiner for combining and outputting 90-degree hybrid, and a 90-degree hybrid connected to the 90-degree hybrid.
Through the first unit mixer and the second unit.
The first transistor of each component of the mixer
And a DC bias is applied to the first electrode of the second transistor.
The DC bias supply circuit for the first electrode, which is supplied respectively, and the Wilkinson type distributor / combiner
And a first transistor and a first transistor
And a DC bias to the second electrode of the second transistor
A second electrode DC bias supply circuit for supplying the second electrode, an input terminal for the first input signal, and the 90-degree hybrid.
The first input signal that is inserted between the
Signal input terminal DC blocking capacitor, the input terminal for the second input signal, and the Wilkinson type
Second, which is inserted between the distributor and the combiner to cut off the DC voltage
Input signal input end of the DC cutoff capacitor, and cuts off the DC voltage at the output terminal of the first intermediate frequency signal
A first intermediate frequency signal output end DC cutoff capacitor and a second intermediate frequency signal output end cut off DC voltage
A second intermediate frequency signal output terminal DC blocking capacitor, the first unit mixer and the second unit mixer
Includes terminating resistors that absorb the output reflected power.
High frequency circuit forming an image rejection mixer
Road. 3. Outputting an input signal of a first frequency in two opposite phases
To distribute to the first opposite phase distribution signal and the second opposite phase distribution
Signal and output the second frequency input signal in phase
180 degree high to distribute and output 2-phase in-phase distribution signal
A bridge and one of the first negative phase distribution signal and two outputs
The first amplified signal is obtained by frequency-synthesizing and amplifying the phase distribution signal.
A first unit amplifier that outputs a signal, and the other of the second output signal and the second opposite-phase distribution signal.
The second amplification signal is obtained by frequency-synthesizing and amplifying the phase distribution signal.
A second unit amplifier for outputting a phase difference between the first amplified signal and the second amplified signal.
A 180 degree hybrid that synthesizes at 0 degree and outputs a synthesized signal.
And a 180 degree hive connected to the 180 degree hybrid
Via the lid, the first unit amplifier and the second unit amplifier;
The first transformer, which is a component of each of the unit amplifiers of
DC bias is applied to the first electrode of the transistor and the second transistor.
DC bias supply circuit for the first electrode that supplies asbestos respectively
And a 180 degree hive connected to the 180 degree hybrid
Via the lid, the first transistor and the first transistor
DC bias is applied to the second electrode of the second transistor
DC bias supply circuit for supplying second electrode , input terminal for input signal of the first frequency, and 180 degrees
Inserted between the hybrid and cut off DC voltage
1 input signal input terminal DC blocking capacitor, the input terminal of the input signal of the second frequency and the 180 degree
Inserted between the hybrid and cut off DC voltage
2 input signal input terminal DC blocking capacitor, and a composite signal output for blocking DC voltage at the output terminal of the composite signal
From the power-end DC blocking capacitor, the first unit amplifier and the second unit amplifier,
And a terminating resistor that absorbs the output reflected power.
High frequency circuit forming a single balanced mixer including. 4. The first input signal is distributed to two outputs in phase with each other.
Wilkinson type components that output two-phase in-phase distribution signals
A divider / combiner, which divides the second input signal into two outputs in opposite phase to divide the first opposite phase component.
180 degree output that outputs the distribution signal and the second anti-phase distribution signal
The hybrid and one of the first negative phase distribution signal and the two outputs
Phase-combined signal and frequency-combined and amplified
A first single-balanced mixer that outputs a signal, and the second opposite-phase distribution signal and the other of the two outputs.
Phase-combined signal and frequency combine and amplify
A second single-balanced mixer that outputs a signal, and inputs the first combined signal and the second combined signal
180 degree hive that returns to the same phase and outputs a composite output signal
A lid and a Wilkinson type distributor / combiner are connected to the Wilkinson
The first single unit via the Nson type distributor / combiner.
A first transistor which is a component of the mixer and
Second transistor and second single balun
The third transistor and the third transistor which are components of the mixer
DC bias is applied to the first electrode of transistor 4
A DC bias supply circuit for supplying a first electrode and a 180 degree hive connected to the 180 degree hybrid.
Via the lid, the first transistor and the first transistor
Second transistor and the third transistor, the fourth transistor
DC bias is applied to the second electrode of each transistor.
DC bias supply circuit for supplying second electrode , input terminal for the first input signal, and Wilkinson type
Firstly inserted between the distributor and the combiner to cut off DC voltage
Input signal input terminal of the DC blocking capacitor, the input terminal of the second input signal and the 180 degree hybrid.
The second input which is inserted between the head and the DC voltage to cut off the DC voltage
DC blocking capacitor for signal input and synthetic output for blocking DC voltage at the output of the composite output signal
Force signal output DC blocking capacitor, the first single balance mixer and the second system.
The reflected power output from the single balance mixer.
Form a double balance mixer that includes a
High-frequency circuit to make. 5. The method according to any one of claims 1 to 4.
The first electrode and the second electrode of each transistor are
A high-frequency circuit that is a connector. 6. The method according to any one of claims 1 to 4.
The first electrode and the second electrode of each transistor are
High frequency circuit that is in.