JP2015033268A - Controller of electric motor - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide a controller of electric motor which allow a current, close to normal state, to be fed to a normal phase, even upon occurrence of an abnormality in any one phase of a multi-phase motor where the phase coils are connected in the star form.SOLUTION: A controller of electric motor includes a multi-phase motor where the phase coils are connected in the star form, an inverter circuit (drive means), a phase relay (switching means) to be connected in series with the phase coils, and a neutral drive circuit to be connected with the neutral of star connection. Upon occurrence of a failure in any one phase of the multi-phase motor, the faulty phase is interrupted by means of a phase relay, and the output from the neutral drive circuit is changed depending on the electrical angle of a magnetic field vector to be generated, under the interrupted state.

Description

  The present invention relates to a control device for a multiphase electric motor in which each phase coil is star-connected.

  In Patent Document 1, the neutral point of a star-connected coil of a three-phase brushless motor is connected to a predetermined power source or drive circuit, and if an abnormality occurs in one phase of the three-phase brushless motor, the neutral point is abnormal. An electric motor control device is disclosed in which a magnetic field vector generated inside a motor is used in place of the phase thus rotated to continue driving the three-phase brushless motor.

Japanese Patent No. 4710528

  However, in the conventional control device, when an abnormality occurs in one phase of the three-phase brushless motor, the neutral point drive circuit is driven at a fixed duty (50%), so the voltage range that can be applied to the motor coil is small, When the rotational speed of the motor becomes high, it becomes impossible to flow a current (target current) necessary for normal two phases against the induced voltage.

  The present invention has been made in view of the above circumstances, and even when an abnormality occurs in any phase of a multiphase electric motor in which each phase coil is star-connected, a current close to a normal state is poured into the normal phase. An object of the present invention is to provide a control device for an electric motor that can be used.

  Therefore, the control device for an electric motor according to the present invention is connected in series with a multiphase electric motor in which each phase coil is star-connected, a driving means for driving the multiphase electric motor, and each phase coil. In a control device for an electric motor comprising switching means and a neutral point drive circuit connected to a neutral point of the star connection, a failure occurs in any one of the polyphases of the multiphase electric motor. When the failure occurs, the phase in which the failure has occurred is blocked by the switching means, and the output of the neutral point driving circuit is changed in the blocked state.

  According to the above invention, when a failure occurs in any one of the phases of the multiphase electric motor, the power supply voltage can be effectively used to flow a current into a normal phase, Motor controllability can be improved.

1 is a schematic configuration diagram of an electric power steering apparatus according to an embodiment of the present invention. It is a circuit diagram which shows the drive device of the electric motor in embodiment of this invention. It is a figure for demonstrating the control process in the W-phase fault state in embodiment of this invention. It is a diagram which shows the magnetic field component parallel to U phase and the magnetic field component orthogonal to U phase according to the electrical angle of a magnetic field vector in embodiment of this invention. It is a diagram which shows a U-phase electric current, a V-phase electric current, and a neutral point electric current according to embodiment of this invention according to the electrical angle of a magnetic field vector. It is a figure for demonstrating the characteristic of the drive duty of the V phase in the embodiment of this invention, a U phase, and a neutral point in a W-phase fault state. It is a circuit diagram which shows the example of arrangement | positioning of the phase relay in embodiment of this invention. FIG. 6 is a diagram showing regions of fixed High output, fixed Low output, and fixed high impedance output according to an electric angle of a magnetic field vector in the embodiment of the present invention. It is a figure which shows the electric angle of the magnetic field vector in each area | region of high output fixed, low output fixed, and high impedance output fixed in the embodiment of this invention, and a high impedance output fixed state. FIG. 6 is a circuit diagram applied when controlling to one of high output fixed, low output fixed, and high impedance output fixed in the embodiment of the present invention. FIG. 6 is a circuit diagram applied when controlling to one of high output fixed, low output fixed, and high impedance output fixed in the embodiment of the present invention. It is a circuit diagram for demonstrating a control process when the neutral point in embodiment of this invention has a ground fault.

Embodiments of the present invention will be described below.
FIG. 1 shows an electric power steering device as an application example of an electric motor control device according to the present invention.

An electric power steering apparatus 100 shown in FIG. 1 is an apparatus that is provided in a vehicle 200 and generates a steering assist force by an electric motor 130. The electric power steering device 100 includes a steering wheel 110, a steering torque sensor 120, an electric motor 130, a driving device 140 for the electric motor 130, a control unit (control device) 150, and a rotation of the electric motor 130 to reduce the rotation of the steering shaft 170 ( It includes a reduction gear 160 that transmits to a pinion shaft.
The steering torque sensor 120 and the speed reducer 160 are provided in a steering column 180 that includes a steering shaft 170.

A pinion gear 171 is provided at the tip of the steering shaft 170. When the pinion gear 171 rotates, the rack gear 172 moves horizontally in the direction of travel of the vehicle 200. Steering mechanisms 202 for the wheels 201 are provided at both ends of the rack gear 172, and the direction of the wheels 201 is changed by the horizontal movement of the rack gear 172.
The steering torque sensor 120 detects the steering torque generated in the steering shaft 170 when the driver of the vehicle performs a steering operation, and outputs the detected steering torque signal ST to the control unit 150.

In addition to the steering torque signal ST, a vehicle speed signal VSP output from the vehicle speed sensor 190 and the like are input to the control unit 150 including a microcomputer (arithmetic processing unit).
The control unit 150 controls the driving device 140 based on the steering torque signal ST, the vehicle speed signal VSP, and the like, thereby controlling the torque generated by the electric motor 130, that is, the steering assist force.
The control unit 150 and the driving device 140 can be provided integrally.

Next, an example of the circuit configuration of the driving device 140 will be described with reference to FIG.
The electric motor 130 is a three-phase DC brushless motor (three-phase synchronous motor) having a three-phase coil of a U-phase coil 130U, a V-phase coil 130V, and a W-phase coil 130W. One end of the U-phase coil 130U, V-phase coil 130V, and W-phase coil 130W of the electric motor 130 is connected to each other to form a star connection, and the U-phase coil 130U, the V-phase coil 130V, and the W-phase coil 130W are connected to each other. The point forms a neutral point NP.
The drive device 140 includes an inverter circuit (drive means) 300, a pre-driver 400 (drive means), a power relay device 500, and a neutral point drive circuit 600.

The inverter circuit 300 includes three sets of semiconductor switches 320UH, 320UL, 320VH, and 320VL that respectively drive the U-phase coil 130U, the V-phase coil 130V, and the W-phase coil 130W of the electric motor 130 via the drive lines 310U, 310V, and 310W. , 320WH, 320WL, and a three-phase bridge circuit.
In the present embodiment, N-channel MOSFETs are used as the semiconductor switches 320UH, 320UL, 320VH, 320VL, 320WH, and 320WL.

In the semiconductor switches 320UH and 320UL, the drain and source are connected in series between the power supply line 510 and the ground point, and one end of the drive line 310U is connected to the connection point between the semiconductor switch 320UH and the semiconductor switch 320UL. A U-phase coil 130U of the electric motor 130 is connected to the other end of the motor.
In the semiconductor switches 320VH and 320VL, the drain and source are connected in series between the power supply line 510 and the ground point, one end of the drive line 310V is connected to the connection point between the semiconductor switch 320VH and the semiconductor switch 320VL, and the drive line 310V. A V-phase coil 130V of the electric motor 130 is connected to the other end.

In the semiconductor switches 320WH and 320WL, the drain-source is connected in series between the power supply line 510 and the ground point, and one end of the drive line 310W is connected to the connection point between the semiconductor switch 320WH and the semiconductor switch 320WL. W-phase coil 130W of electric motor 130 is connected to the other end.
A current detector (current detection resistor) 340 that detects the drive current of the electric motor 130 is connected between the sources of the MOSFETs 320UL, 320VL, and 320WL and the ground point. The current value detected by the current detector 340 is amplified by an amplifier (not shown) or the like and then input to the control unit 150.

Further, the drive lines 310U, 310V, 310W between the neutral point NP and the U-phase coil 130U, the V-phase coil 130V, and the W-phase coil 130W are provided with phase relays 330U, 330V, 330W as switching means. These phase relays 330U, 330V, and 330W can be configured as either electromagnetic relays or a combination of a semiconductor switch such as a MOSFET and a driver of the semiconductor switch.
Control unit 150 individually controls on / off of phase relays 330U, 330V, and 330W.

Here, power supply from the inverter circuit 300 to the U-phase coil 130U, the V-phase coil 130V, and the W-phase coil 130W is cut off by turning off the phase relays 330U, 330V, and 330W (energization cut-off state). By setting relays 330U, 330V, and 330W to an on state (energized state), power can be supplied from inverter circuit 300 to U-phase coil 130U, V-phase coil 130V, and W-phase coil 130W.
The neutral point driving circuit 600 includes an upper arm side semiconductor switch 600H and a lower arm side semiconductor switch 600L formed of N-channel MOSFETs. The semiconductor switches 600H and 600L include a power line 510, a ground point, and the like. Between the drain and source are connected in series.

Then, the other end of the drive line 610 having one end connected to the neutral point NP is connected to a connection point between the semiconductor switch 600H and the semiconductor switch 600L.
The drive line 610 is provided with a neutral point relay 620 that is controlled to be turned on and off by the control unit 150. The neutral point relay 620 can be configured as either an electromagnetic relay or a combination of a semiconductor switch such as a MOSFET and a driver of the semiconductor switch.

The pre-driver 400 includes three H-side drivers 410H that respectively drive semiconductor switches 320VH, 320UH, and 320WH, which are upstream drive elements (upper arms) in the inverter circuit 300, and downstream drive elements (lower arms) in the inverter circuit 300. ), And three L-side drivers 410L for driving the semiconductor switches 320VL, 320UL, and 320WL, respectively.
Note that the pre-driver 400 can be configured by SOI (Silicon on Insulator), whereby stray capacitance is reduced, and the pre-driver 400 can be increased in speed and power consumption. In addition, when a specific part fails, the possibility of spreading to another part and causing another failure can be reduced.

The pre-driver 400 also includes three bootstrap circuits (boost circuits) 430 for driving the upper arms (MOSFETs 320UH, 320VH, and 320WH) with electric charges charged in the bootstrap capacitor C for each phase of the electric motor 130. I have.
The gates of MOSFETs 320UH, 320VH, and 320WH are connected to the output terminals of the H-side driver 410H, and the MOSFETs 320UH, 320VH, and 320WH are controlled to be turned on and off according to the output of the H-side driver 410H.

Similarly, the gates of MOSFETs 320UL, 320VL, and 320WL are connected to the output terminal of the L-side driver 410L, and the MOSFETs 320UL, 320VL, and 320WL are controlled to be turned on and off in accordance with the output of the L-side driver 410L.
The pre-driver 400 includes an H-side driver 420H that drives the semiconductor switch 600H in the neutral point driving circuit 600 and an L-side driver 420L that drives the semiconductor switch 600L in the neutral point driving circuit 600.

The gate of the MOSFET 600H is connected to the output terminal of the H-side driver 420H, the gate of the MOSFET 600L is connected to the output terminal of the L-side driver 420L, and the MOSFETs 600H and 600L are turned on and off according to the outputs of the drivers 420H and 420L. Be controlled.
The pre-driver 400 includes a charge pump (boost circuit) 440 that is a boost circuit that boosts the voltage of the battery 700 that is a power source of the pre-driver 400.

The microcomputer 151 included in the control unit 150 includes output ports 152A and 152B that output PWM operation signals for PWM control of the drivers 410H and 410L and the drivers 420H and 420L.
The power relay device 500 is interposed in a power line 510 that supplies power from the battery (power source) 700 toward the inverter circuit 300 and the neutral point driving circuit 600, and is connected to the first circuit breaker 501A and the second circuit breaker 501A connected in parallel to each other. Circuit breaker 501B.

The circuit breakers 501A and 501B constituting the power relay device 500 can be configured by either an electromagnetic relay or a combination of a semiconductor switch such as a MOSFET and a driver of the semiconductor switch.
In each MOSFET constituting the inverter circuit 300 and the neutral point driving circuit 600, the drain-source diode is a parasitic (internal) diode.

When each phase of the electric motor 130 is normal, the control unit 150 controls the phase relays 330U, 330V, and 330W to be in an on state, while controlling the neutral point relay 620 to be in an off state (energization cut-off state). The electric motor 130 is driven by PWM control of on / off of the semiconductor switches 320UH, 320UL, 320VH, 320VL, 320WH, and 320WL of the inverter circuit 300 via the pre-driver 400.
Here, the control unit 150 controls the rotational speed (torque) of the electric motor 130 by changing the duty ratio of the PWM signal based on the steering torque signal ST and the vehicle speed signal VSP.

Further, the control unit 150 has a function (diagnosis function) for detecting the presence or absence of a failure in the U phase, V phase, and W phase of the electric motor 130. For example, the control unit 150 compares the PWM signal (pulse width modulation signal) output to the pre-driver 400 with the motor voltage of each phase, thereby diagnosing the presence / absence of a U-phase, V-phase, and W-phase failure.
The failure of each phase includes an inverter failure for each phase, a disconnection or ground fault of the phase coil, and an open failure of the phase relay.

Here, when the control unit 150 detects a failure in any one of the U phase, the V phase, and the W phase, the control unit 150 controls the phase relay 330 provided in the drive line of the phase in which the failure is detected to be in an OFF state. By shutting off the power supply to the phase in which the failure has occurred and controlling the neutral point relay 620 to the on state (energized state), the neutral point NP is driven to the neutral point. The circuit 600 can be controlled.
Then, the control unit 150 determines the target of the current flowing in the normal two phases according to the magnetic field vector to be generated, and controls the inverter circuit 300 and the neutral point driving circuit 600 according to this, The drive of the electric motor 130 is continued in a state where a failure has occurred in one phase.

A process of controlling the phase current by the control unit 150 when a failure occurs in one of the three phases will be described with reference to FIG.
Taking a case where a failure occurs in the W phase as an example, the control unit 150 keeps the phase relays 330U and 330V in the on state, while switching the phase relay 330W to the off state and shuts off the W phase. The relay 620 is controlled to be in the ON state, and the relay control state shown in FIG. 3 is set.

Further, the control unit 150 decomposes the magnetic field vector to be generated determined according to the magnetic pole position into, for example, a component parallel to the normal U phase and a component orthogonal to the normal U phase.
Here, the component parallel to the U phase can be generated in the U phase and the V phase, but the component orthogonal to the U phase can be generated only in the V phase which is the other of the normal two phases. Therefore, the control unit 150 obtains a V-phase generated magnetic field vector (V-phase target current) that generates a component orthogonal to the U-phase in the V-phase.
Further, the control unit 150 obtains a component parallel to the U phase of the generated magnetic field vector of the V phase, and a component parallel to the U phase of the magnetic field vector desired to be generated and a component parallel to the U phase of the generated magnetic field vector of the V phase. From the components, a U-phase generated magnetic field vector (U-phase target current) is finally obtained.

FIG. 4 shows a state in which the magnetic field vector to be generated is decomposed into a component parallel to the U phase and a component orthogonal to the U phase for each electrical angle (each magnetic pole position) of the magnetic field vector to be generated (target magnetic field vector). Show.
FIG. 5 exemplifies the U-phase and V-phase target currents determined based on the component parallel to the U-phase and the component orthogonal to the U-phase in FIG. The total of the current and the target current is an inflow / outflow current (neutral point current) to the neutral point drive circuit 600.

  In the above description, the magnetic field vector to be generated is decomposed into a component parallel to the U phase and a component orthogonal to the U phase. However, in the W phase failure state, the magnetic field vector to be generated is converted to a component parallel to the V phase. It is clear that the target current of two normal phases (U phase, V phase) can be determined even if it is decomposed into components orthogonal to the V phase, and a failure occurs in the U phase or V phase other than the W phase. In this case, it is apparent that a normal two-phase target current can be determined in the same manner.

As described above, when the control unit 150 determines the normal two-phase target current, the control unit 150 then determines the normal two-phase driving duty and the driving duty of the neutral point driving circuit 600.
For example, when the driving duty of the neutral point driving circuit 600 is fixed to 50%, the voltage that can be applied to the normal phase of the electric motor 130 is ½ of the power supply voltage, and the power supply voltage becomes effective in a one-phase failure state. Cannot be used.

Therefore, the control unit 150 increases the output voltage and duty (on-duty) of the neutral point drive circuit 600 when current is supplied from the neutral point drive circuit 600 to the normal phase of the electric motor 130, When it is desired to draw a current from the normal phase of the electric motor 130 to the neutral point drive circuit 600, the output voltage and the duty (on duty) of the neutral point drive circuit 600 are reduced so as to effectively use the power supply voltage. .
For example, when a failure occurs in the W phase and the electric motor 130 is driven by driving the U phase and the V phase, as shown in FIG. 5, the neutrality is obtained when the electrical angle of the magnetic field vector to be generated is 240 deg. Driving the neutral point driving circuit 600 so that the current flowing from the point driving circuit 600 is maximized and the current drawn to the neutral point driving circuit 600 is maximized when the electrical angle of the magnetic field vector to be generated is 60 degrees. Determine the duty. In the present application, the angular position of the U-phase coil is expressed as a position where the electrical angle of the magnetic field vector is 0 deg.

The control unit 150 calculates, for example, the duty of the neutral point driving circuit 600 in the W phase failure state as 50% + 50% × sin (θ−150 deg), where θ is the electrical angle of the magnetic field vector to be generated. To do.
By setting the duty of the neutral point driving circuit 600 to 50% + 50% × sin (θ−150 deg), sin (θ−150 deg) = 1 when the electric angle of the magnetic field vector to be generated is 240 deg. The duty of the neutral point driving circuit 600 is set to 100%, and the inflow current from the neutral point driving circuit 600 is maximized. When the electrical angle of the magnetic field vector to be generated is 60 deg, sin (θ−150 deg) = − 1 and the duty of the neutral point driving circuit 600 is set to 0%. Maximum current draw.

Further, when the electrical angle of the magnetic field vector to be generated is 150 deg and 330 deg, the duty of the neutral point driving circuit 600 is set to 50%, and the duty of the neutral point driving circuit 600 is as shown in FIG. The electrical angle of the magnetic field vector changes so as to show a sine wave between 0% and 100% with 360 deg as one period.
Note that the semiconductor switch 600H and the semiconductor switch 600L of the neutral point driving circuit 600 are driven by PWM waves having opposite phases by the complementary control method, and the driving duty of the neutral point driving circuit 600 is the upper stage ( The driving duty on the H side) shall be indicated.

  Therefore, the duty 100% of the neutral point driving circuit 600 is a state where the semiconductor switch 600H is fixed on and the semiconductor switch 600L is fixed off, that is, a state where the output of the neutral point driving circuit 600 is fixed high. Conversely, the duty 0% of the neutral point driving circuit 600 means that the semiconductor switch 600H is fixed off and the semiconductor switch 600L is fixed on, that is, the output of the neutral point driving circuit 600 is fixed low. It is.

However, the method of determining the drive duty of the neutral point drive circuit 600 is not limited to the method of continuously changing between 0% and 100% according to the electrical angle of the magnetic field vector to be generated as described above. .
For example, the control unit 150 fixes the driving duty of the neutral point driving circuit 600 to 50% when the voltage to be applied to the normal phase of the electric motor 130 is sufficient to be 1/2 of the power supply voltage. When the voltage to be applied to the phase is insufficient at half the power supply voltage, the duty fluctuation centered on 50% can be expanded.

  That is, taking the W-phase failure state as an example, 50% + f (voltage to be applied) × sin (θ−150 deg) can be set as the driving duty of the neutral point driving circuit 600. For example, if the duty determined by the function f having the voltage to be applied as a variable is 30%, the driving duty of the neutral point driving circuit 600 continuously changes in the range of 20% to 80% and is generated. When the electrical angle of the magnetic field vector to be generated is 240 deg, the driving duty of the neutral point driving circuit 600 is set to 80%, and when the electrical angle of the magnetic field vector to be generated is 60 deg, the neutral point driving circuit 600 The duty is set to 20%.

  When the control unit 150 determines the driving duty of the neutral point driving circuit 600 as described above, the control unit 150 then calculates the applied voltage of each normal phase coil and sets the normal driving duty for each phase based on the applied voltage. decide. The control unit 150 calculates the applied voltage of each phase coil necessary to energize the target current of each phase set based on the magnetic field vector to be generated, and the output voltage of the neutral point driving circuit 600 is used as the applied output pressure. Add the minutes to determine the final voltage and drive duty for each phase.

FIG. 6 illustrates a case where the W phase is in a failure state and a target magnetic field vector can be generated by flowing a current twice as large as the current flowing in the V phase to the U phase.
Assuming that the neutral point NP is at the ground potential, the V-phase drive duty is set to 10% and the U-phase drive duty is set to 20% in order to flow a current twice as large as the current flowing in the V-phase to the U-phase. Is required, the V-phase and U-phase drive duties are corrected by the amount by which the potential of the neutral point NP changes from the ground point potential under the control of the neutral point drive circuit 600.
By the above operation, the sum of the normal two-phase currents becomes the inflow / outflow current to the neutral point driving circuit 600, and a current close to the target current can be supplied to the normal two phases.

In the example shown in FIG. 2, phase relays 330U, 330V, and 330W are provided on drive lines 310U, 310V, and 310W between neutral point NP and U-phase coil 130U, V-phase coil 130V, and W-phase coil 130W. However, it is not limited to the arrangement of the phase relays 330U, 330V, and 330W.
For example, as shown in FIG. 7, phase relays 330U, 330V, and 330W are provided on the drive lines 310U, 310V, and 310W between the U-phase coil 130U, the V-phase coil 130V, the W-phase coil 130W, and the inverter circuit 300, and the control is performed. The unit 150 can control the phase relay 330 of the phase in which the failure has occurred to be turned off.

By the way, as illustrated in FIG. 5, when a failure occurs in one phase, a phase difference between currents (target currents) flowing through two normal phases to generate a target magnetic field vector is 60 deg. Since the inflow / outflow current to the drive circuit 600 is the sum of the currents of the normal phase, the peak (current amplitude) of the inflow / outflow current to the neutral point drive circuit 600 is the normal current peak (current) of each phase. The amplitude).
Therefore, when the same element as the semiconductor switch (MOSFET) constituting the inverter circuit 300 is used in the neutral point driving circuit 600, the peak of the inflow / outflow current of the neutral point driving circuit 600 constitutes the neutral point driving circuit 600. This is within the current withstand capability of the current, and the size of the magnetic field vector that can be generated in normal two phases is limited. The magnitude of the magnetic field vector that can be generated in the state where one phase has failed is larger than that in the case where all phases are normal. About 1/3.

Further, the switching loss in the neutral point driving circuit 600 is larger than the switching loss in the normal PWM driving of each phase by the amount of the current peak, resulting in weakening the torque generated by the electric motor 130.
Therefore, in order to reduce the switching loss in the neutral point driving circuit 600, the control unit 150 makes the PWM control frequency (carrier frequency) of the neutral point driving circuit 600 lower than the PWM control frequency of the inverter circuit 300.

For example, the control unit 150 sets the PWM control frequency (carrier frequency) of the neutral point driving circuit 600 to about ¼ of the PWM control frequency of the inverter circuit 300.
Thereby, the switching loss in the neutral point drive circuit 600 is reduced, and a larger torque can be generated by the electric motor 130.

Further, as a technique for reducing the switching loss in the neutral point driving circuit 600 when a failure occurs in one phase of the electric motor 130 and driving the normal two phases, the output of the neutral point driving circuit 600 is used as the target magnetic field vector. It is possible to employ a control process that changes stepwise according to the electrical angle (magnetic pole position).
FIG. 8 shows the correlation between the U-phase current, the V-phase current, the neutral point current, and the output of the neutral point driving circuit 600 when a failure occurs in the W phase and drives the U phase and the V phase.

In FIG. 8, the output of the neutral point driving circuit 600 is switched in stages to three types of fixed high output, fixed low output, and fixed high impedance (Hi-Z) output.
Here, “High output fixed” means that the drive duty of the semiconductor switch 600H is fixed to 100% (the semiconductor switch 600H is in the on state), and the drive duty of the semiconductor switch 600L is fixed to 0% (the semiconductor switch 600L is in the off state). Mode.

The low output fixing is a mode in which the driving duty of the semiconductor switch 600H is fixed to 0% (the semiconductor switch 600H is in an off state), and the driving duty of the semiconductor switch 600L is fixed to 100% (the semiconductor switch 600L is in an on state). It is.
Further, the high impedance output fixing is a mode in which the drive duty of the semiconductor switch 600H and the semiconductor switch 600L is fixed to 0% (both the semiconductor switches 600H and 600L are in the off state).
That is, in any of the fixed high output, fixed low output, and fixed high impedance output, the semiconductor switches 600H and 600L are fixed to the on state or the off state without switching operation (without duty control).

The control unit 150 drives the neutral point when the directions of the currents in the U phase and the V phase are both positive, that is, when the directions of the currents in the U phase and the V phase are both flowing out from the inverter circuit 300. The drive duty of the circuit 600 is fixed to a low output.
Further, the control unit 150 has a neutral point driving circuit 600 when the current directions in the U phase and the V phase are both negative, that is, when the current directions in the U phase and the V phase are both flowing into the inverter circuit 300. The drive duty is fixed to High output.

Further, the control unit 150 determines that the current direction in the U phase is different from the current direction in the V phase, that is, the current direction in the U phase is positive and the current direction in the V phase is negative, or When the current direction in the U phase is negative and the current direction in the V phase is positive, the driving duty of the neutral point driving circuit 600 is fixed to a high impedance (Hi-Z) output.
In the W-phase fault state shown in FIG. 8, the low output is fixed when the electrical angle of the target magnetic field vector is 0 deg to 120 deg, and the high output is fixed when the electrical angle of the target magnetic field vector is 180 deg to 300 deg. The high impedance output is fixed in the region where the electric angle of the magnetic field vector is 120 deg to 180 deg and in the region where 300 deg to 360 deg.

As described above, when the output of the neutral point driving circuit 600 is switched step by step to three types of fixed high output, fixed low output, and fixed high impedance output according to the electrical angle (magnetic pole position) of the target magnetic field vector, As shown in FIG. 9, in the region where the high output is fixed or the low output is fixed, the sum of the U-phase current and the V-phase current becomes the inflow / outflow current to the neutral point drive circuit 600. Can be generated.
On the other hand, in the region where the output of the neutral point driving circuit 600 is fixed to the high impedance output, the currents flowing in the U phase and the V phase have the same magnitude, and the direction of the magnetic field vector that can be generated is the VE1 direction shown in the figure, It will be fixed in the VE2 direction.

Therefore, although the motor output torque fluctuates with respect to the change in the rotation angle of the electric motor 130, a magnetic field vector can be generated at an electrical angle of at least every 30 degrees even in a region where the high impedance output is fixed. It is possible to make it.
In addition, in the electrical angle region (120 deg to 180 deg region and 300 deg to 360 deg region) of the target magnetic field vector to be fixed as the high impedance output, the current flowing through the neutral point NP is small. It is also possible to perform duty control (duty output state) in which the semiconductor switch 600H is switched with a duty of 50% and the semiconductor switch 600L is switched with a reverse phase duty of 50%.

  As described above, in the configuration of switching to the three types of fixed high output, fixed low output, fixed high impedance output, or three types of fixed high output, fixed low output, fixed duty output, the high output fixed region, The semiconductor switches 600H and 600L of the neutral point driving circuit 600 are not switched in each of the low output fixed region and the high impedance output fixed region, or in the high output fixed region and the low output fixed region (PWM drive). Therefore, switching loss can be reduced. Therefore, the absolute value of the amount of current that can be passed through the neutral point NP can be increased as compared with the case of PWM driving, and the magnitude of the generated magnetic field vector and the motor output torque can be increased. .

Further, in the configuration of switching to the three types of fixed high output, fixed low output, and fixed high impedance output, the switching loss can be made substantially zero, so the switching speed in selecting the semiconductor switch constituting the neutral point drive circuit 600 The semiconductor switch can be selected by giving priority to a small on-resistance.
If a semiconductor switch with low on-resistance is used, the loss in the neutral point driving circuit 600 can be further reduced, the absolute value of the amount of current that can be passed through the neutral point NP is further increased, and the magnitude of the generated magnetic field vector and The motor output torque can be further increased.

  Further, in the configuration in which the output is fixed to high output, fixed to low output, or fixed to high impedance output, the neutral point driving circuit 600 is not PWM driven, so the driver and the control terminal of the microcomputer 151 must also support PWM driving. Since the gate resistance connected to the gate of the semiconductor switch (FET) constituting the neutral point drive circuit 600 can be a large resistance value, the lower arm semiconductor switch 600L is connected to the microcomputer 151. Even if it is directly driven by the control terminal, it is possible to suppress the failure of the microcomputer 151 due to the propagation of the surge applied to the semiconductor switch side.

Therefore, when the driving state of the neutral point driving circuit 600 is switched to three types of fixed high output, fixed low output, and fixed high impedance output, the neutral point driving circuit 600 shown in FIGS. 2 and 7 is driven. This makes it possible to simplify the circuit configuration.
FIG. 10 shows an example of a simplified driving device 140 that can apply control for switching the driving state of the neutral point driving circuit 600 to three types of fixed high output, fixed low output, and fixed high impedance output. .

The circuit configuration of FIG. 10 is different from the circuit shown in FIG. 2 in that the upper arm side semiconductor switch constituting the neutral point driving circuit 600 is changed, and the H-side driver 420H and the L-side driver 420L of the pre-driver 400 are changed. The difference is that the semiconductor switch constituting the neutral point driving circuit 600 is directly driven by the control terminal of the microcomputer 151.
In FIG. 10, the same components as those in FIG. 2 are denoted by the same reference numerals, and detailed description thereof is omitted.

  In the driving device 140 shown in FIG. 10, a P-channel type MOSFET is used as the semiconductor switch 600H constituting the upper arm of the neutral point driving circuit 600, and N as the semiconductor switch 600L constituting the lower arm of the neutral point driving circuit 600. A channel type MOSFET is used, the source and drain of the P channel type MOSFET 600H are connected in series between the power supply line 510 and the ground point, and the drain of the N channel type MOSFET 600L is connected to the drain of the P channel type MOSFET 600H. The drain-source of the N-channel MOSFET 600L is connected in series between the drain of the P-channel MOSFET 600H and the ground point.

The source and gate of the P-channel MOSFET 600H are connected via a resistor R1, and the collector and emitter of the NPN transistor TR are connected in series between the gate of the P-channel MOSFET 600H and the ground point. The base of the NPN transistor TR and the general-purpose port 152C of the microcomputer 151 are connected.
On the other hand, the gate of the N-channel MOSFET 600L and the general-purpose port 152C of the microcomputer 151 are connected via a resistor (gate resistor) R2.

In the above configuration, when a high signal is output from the general-purpose port 152C of the microcomputer 151 to the base of the NPN transistor TR, a current flows between the collector and the emitter of the NPN transistor TR (the NPN transistor TR is turned on). .
In the ON state of the NPN transistor TR, the gate voltage is lower than that of the source of the P-channel MOSFET 600H, and a current flows between the source and the drain of the P-channel MOSFET 600H (the ON state of the P-channel MOSFET 600H). .

On the other hand, when a low signal is output from the general-purpose port 152C of the microcomputer 151 to the base of the NPN transistor TR and the NPN transistor TR is turned off, the voltage between the source and gate of the P-channel MOSFET 600H becomes the same. Thus, the P-channel MOSFET 600H is turned off, and no current flows between the source and drain of the P-channel MOSFET 600H.
Further, when a high signal is output from the general-purpose port 152C of the microcomputer 151 to the gate of the N-channel MOSFET 600L, the N-channel MOSFET 600L is turned on and a current flows between the drain and source.

On the other hand, when a low signal is output from the general-purpose port 152C of the microcomputer 151 to the gate of the N-channel MOSFET 600L, the N-channel MOSFET 600L is turned off and no current flows between the drain and source.
Therefore, if a low signal is output from the general-purpose port 152C of the microcomputer 151 to the base of the NPN transistor TR and a high signal is output from the general-purpose port 152C of the microcomputer 151 to the gate of the N-channel MOSFET 600L, a neutral point driving circuit is obtained. 600 becomes a low output fixed state.

Further, if a high signal is output from the general-purpose port 152C of the microcomputer 151 to the base of the NPN transistor TR and a low signal is output from the general-purpose port 152C of the microcomputer 151 to the gate of the N-channel MOSFET 600L, the neutral point driving circuit 600 is fixed to High output.
Further, if a low signal is output from the general-purpose port 152C of the microcomputer 151 to the base of the NPN transistor TR, and a low signal is output from the general-purpose port 152C of the microcomputer 151 to the gate of the N-channel MOSFET 600L, a neutral point driving circuit is obtained. 600 is fixed to a high impedance output.

  That is, in the circuit configuration shown in FIG. 10, for example, assuming that the W-phase failure state shown in FIG. 8 has occurred, the microcomputer 151 has a general-purpose port 152C in the region where the electrical angle of the target magnetic field vector is 0 deg to 120 deg. A low signal is output from the NPN transistor TR to the base of the NPN transistor TR and a high signal is output to the gate of the N-channel MOSFET 600L, thereby fixing the Low output.

In the region where the electrical angle of the target magnetic field vector is 180 ° to 300 °, the microcomputer 151 outputs a high signal from the general-purpose port 152C to the base of the NPN transistor TR, and outputs a low signal to the gate of the N-channel MOSFET 600L. Thus, the high output is fixed.
Further, in the region where the electrical angle of the target magnetic field vector is 120 deg. To 180 deg. And 300 deg. To 360 deg., The microcomputer 151 outputs a low signal from the general-purpose port 152C to the base of the NPN transistor TR, and the gate of the N-channel MOSFET 600L. The low impedance signal is output to the high impedance output fixed state.

As described above, if the circuit configuration shown in FIG. 10 is applied to the configuration in which the output is fixed to high output, fixed to low output, or fixed to high impedance output, the circuit configuration for driving the neutral point driving circuit 600 is simplified. In addition, the failure of the microcomputer 151 due to the propagation of surge can be suppressed by increasing the resistance value of the resistor R2.
In the circuit configuration shown in FIG. 10, phase relays 330U, 330V, and 330W are provided on drive lines 310U, 310V, and 310W between neutral point NP and U-phase coil 130U, V-phase coil 130V, and W-phase coil 130W. However, as shown in FIG. 11, phase relays 330U, 330V, and 330W may be provided on the drive lines 310U, 310V, and 310W between the U-phase coil 130U, the V-phase coil 130V, and the W-phase coil 130W and the inverter circuit 300. it can.

By the way, when the neutral point NP has a ground fault, if the drive of the electric motor 130 is continued in the same manner as in the normal state, an overcurrent may flow in the phase coil and cause further failure. Normal energization of the motor and generation of the intended motor output torque cannot be realized.
Therefore, the control unit 150 performs the control described later on the ground fault at the neutral point NP, thereby realizing the continuous operation of the electric motor 130 while suppressing the excessive current from flowing through the phase coil.
Note that the control of the control unit 150 when the neutral point NP described below has a ground fault is applicable to any of the circuit configurations of FIGS. 2, 7, 10, and 11.

For example, the control unit 150 detects the current flowing into the semiconductor switches 320UH, 320VH, and 320WH constituting the upper arm of the inverter circuit 300 with the current detector 341 (see FIG. 12) while the neutral point relay 620 is turned off. The occurrence of an overcurrent due to a ground fault at the neutral point NP is detected.
When the control unit 150 detects a ground fault at the neutral point NP (a ground fault between the neutral point NP and the neutral point relay 620), the control unit 150 switches the neutral point relay 620 from the off state to the on state. Further, the neutral point driving circuit 600 is fixed to the low output state, that is, the driving duty of the semiconductor switch 600H is fixed to 0% (the semiconductor switch 600H is turned off), and the driving duty of the semiconductor switch 600L is set to 100% ( The semiconductor switch 600L is fixed to the ON state.

Even if the neutral point relay 620 is controlled to be in the ON state, if the neutral point driving circuit 600 is set to the low output fixed state, an excessive current does not flow between the neutral point driving circuit 600 and the ground fault point. In addition, although the impedance of the ground fault is unknown, the neutral point NP can be connected to the ground GND potential with low impedance by setting the neutral point driving circuit 600 to the low output fixed state.
As described above, when the neutral point relay 620 is controlled to be in the ON state and the neutral point driving circuit 600 is set to the low output fixed state, the inverter circuit 300 can only flow out the current. The electric motor 130 can be driven by generating an arbitrary magnetic field vector by changing the output duty of each phase in 300 to control the energization current (flowing current) to each phase coil.

FIG. 12 is a diagram for explaining the control operation of the control unit 150 when the neutral point NP has a ground fault.
When the neutral point relay 620 is in the ON state and the neutral point driving circuit 600 is set to the low output fixed state, as described above, the inflow / outflow current in the inverter circuit 300 only flows out to each phase. The direction of the magnetic field vector when the current is supplied only to the phase coil 130U is the 180 deg direction shown in FIG. 12, and the direction of the magnetic field vector when the current is supplied only to the V phase coil 130V is the 300 deg shown in FIG. The direction of the magnetic field vector when the current flows only through the W-phase coil 130W is the direction of 60 degrees shown in FIG.

Therefore, when the direction of the magnetic field vector generated by the current flow to one of the three phases differs from the direction of the magnetic field vector to be generated by 120 degrees or more, the control unit 150 sets the output of the phase to Low. Output fixed or high impedance output fixed.
For example, as shown in FIG. 12, when the electrical angle of the magnetic field vector to be generated is within a range of 300 deg to 60 deg, the electrical angle region 300 deg to 60 deg of the magnetic field vector and the current flow to the U phase are generated. Since the electric angle of the magnetic field vector is 180 degrees or more different from the electric angle of 180 deg, the control unit 150 fixes the U-phase output in the inverter circuit 300 to the low output when the electric angle of the magnetic field vector to be generated is in the range of 300 deg to 60 deg. Or fixed high impedance output.

The low output fixed state of the U-phase output means that the drive duty of the semiconductor switch 320UH on the upper arm side is fixed to 0% (the semiconductor switch 320UH is turned off), and the drive duty of the semiconductor switch 320UL on the lower arm side is 100% ( This is a control state in which the semiconductor switch 320UL is fixed to the ON state.
The high-impedance output fixed state of the U-phase output is a control state in which the drive duties of the semiconductor switch 320UH and the semiconductor switch 320UL are both fixed to 0% (both the semiconductor switches 320UH and 320UL are in the off state).

The electrical angle of the magnetic field vector generated by the current flow to the V phase is 300 deg, and the electrical angle of the magnetic field vector generated by the current flow to the W phase is 60 deg.
Therefore, when the electrical angle of the magnetic field vector to be generated is within the range of 60 deg to 180 deg, the control unit 150 generates the V-phase output in the inverter circuit 300 by fixing it to the low output or fixing the high impedance output. When the electrical angle of the magnetic field vector to be set is within the range of 180 deg to 300 deg, the W phase output in the inverter circuit 300 is fixed to the low output or the high impedance output is fixed.

For example, when the electrical angle of the magnetic field vector to be generated is in the range of 300 deg to 60 deg, the control unit 150 adjusts the current flowing in the V phase and the current flowing in the W phase by duty control, respectively, to 300 deg. The electric angle of the magnetic field vector is changed within a range of ˜60 deg.
A magnetic field vector having an electrical angle of 300 deg is generated by flowing current to the V phase, and a magnetic field vector having an electrical angle of 60 deg is generated by flowing current to the W phase.

  Therefore, when the direction of the magnetic field vector to be generated is 300 deg, the current flow to the W phase is interrupted and the current is supplied to the V phase, and the inverter changes in response to the change in the electrical angle of the magnetic field vector to be generated. By reducing the current flowing out from the circuit 300 to the V phase (V phase output duty) and relatively increasing the current flowing out from the inverter circuit 300 to the W phase (W phase output duty), the electric angle of the magnetic field vector is 300 deg. The electrical angle of the magnetic field vector can be set to 60 deg by finally increasing the current angle from the current angle, and finally shutting off the current flow to the V phase and flowing the current to the W phase.

Similarly, when the electrical angle of the magnetic field vector to be generated is in the range of 60 deg to 180 deg, the control unit 150 adjusts the current flowing in the U phase and the current flowing in the W phase by duty control, respectively, When the electric angle of the magnetic field vector is changed within the range of 180 deg and the electric angle of the magnetic field vector desired to be generated is within the range of 180 deg to 300 deg, the control unit 150 Are respectively adjusted by duty control to change the electric angle of the magnetic field vector within a range of 180 deg to 300 deg.
As a result, the control unit 150 can drive the electric motor 130 to rotate even in the event of a failure in which the neutral point NP is grounded.

  Note that, as described above, when the neutral point NP is grounded, the neutral point driving circuit 600 is fixed to the low output, so that the neutral point driving circuit 600 is composed of the semiconductor switch 600H and the semiconductor switch 600L. Instead, a semiconductor switch such as a transistor provided on a line connecting the neutral point NP and the ground point may be configured, and the semiconductor switch may be turned on when the neutral point NP is grounded.

Further, the above-mentioned ground fault is a ground fault at the neutral point NP (between the neutral point NP and the neutral point relay 620), but the control unit 150 is connected to the neutral point relay 620 from the neutral point. The presence / absence of a ground fault with the drive circuit 600 is detected. When a ground fault has occurred between the neutral point relay 620 and the neutral point drive circuit 600, the neutral point relay 620 is turned off. The neutral point driving circuit 600 is fixed to a low output while being held in a state.
The presence or absence of a ground fault between the neutral point relay 620 and the neutral point driving circuit 600 is determined by connecting a current detector 342 (see FIG. 12) between the neutral point relay 620 and the neutral point driving circuit 600. When the semiconductor switch 600H is turned on and the semiconductor switch 600L is turned off when the neutral point relay 620 is off (when the neutral point driving circuit 600 is fixed to High output), the current is detected by the current detector 342. Diagnosis can be made based on whether or not it is done.

  When a ground fault occurs between the neutral point relay 620 and the neutral point drive circuit 600, the neutral point relay 620 is held in the off state and the neutral point drive circuit 600 is fixed to the low output. Thus, if each phase of the electric motor 130 is normal, the driving of the electric motor 130 can be continued, and an overcurrent can be suppressed from flowing through the neutral point driving circuit 600.

The technical ideas described in the above embodiments can be used in appropriate combination as long as no contradiction arises.
Although the contents of the present invention have been specifically described with reference to preferred embodiments, it is obvious that those skilled in the art can take various modifications based on the basic technical idea and teachings of the present invention. is there.

For example, the electric motor 130 is not limited to a three-phase DC brushless motor, and can be a synchronous motor having four or more phase coils.
Further, when the phase relays 330U, 330V, and 330W are constituted by semiconductor switches, they can be N-channel MOSFETs or P-channel MOSFETs.
Further, the electric motor 130 is not limited to the electric motor that generates the steering assist force in the electric power steering apparatus 100. For example, the electric motor 130 may be an electric motor that drives a fluid pump that circulates oil or cooling water in the vehicle. Can do.

Here, technical ideas other than the claims that can be grasped from the above embodiment will be described together with effects.
(A) the multi-phase electric motor is a three-phase electric motor;
When one of the three phases fails, the duty of the neutral point driving circuit is increased from 50% as the current flowing from the normal two phases into the driving unit becomes higher. The control apparatus for an electric motor according to claim 2, wherein the duty of the neutral point drive circuit is reduced from 50% as the flow-out current to the normal two-phase increases.
According to the above configuration, the duty is increased when it is desired to draw current from the neutral point driving circuit, and the duty is lowered when the current is desired to be drawn into the neutral point driving circuit, thereby effectively using the power supply voltage. be able to.

(B) The control device for an electric motor according to claim 2, wherein the duty of the neutral point drive circuit is changed around 50% according to the electrical angle of the magnetic field vector to be generated.
According to the above configuration, based on the electrical angle of the magnetic field vector to be generated (in other words, the magnetic pole position), the region where current is to flow from the neutral point driving circuit and the region where current is to be drawn into the neutral point driving circuit are By effectively changing the duty, the power supply voltage can be effectively used.

(C) Depending on the electrical angle of the magnetic field vector to be generated, the output of the neutral point drive circuit is in two states, high output fixed and low output fixed, or high output fixed and low output fixed and high impedance. The electric motor control device according to claim 3, wherein the control is switched to three states of fixed output.
According to the above invention, based on the electrical angle of the magnetic field vector to be generated (in other words, the magnetic pole position), the region where current is to flow from the neutral point driving circuit and the region where current is to be drawn into the neutral point driving circuit are By distinguishing and switching the output fixed state of the neutral point driving circuit, the power supply voltage can be effectively used.

(D) the multi-phase electric motor is a three-phase electric motor;
When one of the three phases fails, if both normal two-phase currents are flowing out from the driving means, the neutral point driving circuit is fixed at a low output, and the normal two-phase When both currents are flowing into the driving means, the neutral point driving circuit is fixed at high output, and when the normal two-phase current directions are different from each other, the neutral point driving circuit is set to high impedance. 4. The electric motor control device according to claim 3, wherein the output is fixed.
According to the above configuration, since the neutral point drive circuit is set to one of fixed low output, fixed high output, and fixed high impedance output, the current that can be applied to the neutral point by reducing the switching loss of the neutral point drive circuit Can be increased, and the motor output torque can be increased.

(E) The neutral point driving circuit comprises an FET constituting the upper arm and an FET constituting the lower arm,
The gate of the FET constituting the lower arm and a control terminal of the microcomputer are connected via a gate resistor, and the FET constituting the lower arm is directly driven by the control terminal of the microcomputer. The control apparatus of the electric motor of description.
According to the above configuration, the circuit for driving the gate of the FET constituting the lower arm can be omitted, and the propagation of the surge to the microcomputer can be suppressed by the gate resistance, and the microcomputer can be protected.

(F) connecting the base of the transistor provided on the line connecting the gate of the FET constituting the upper arm and the ground point to the control terminal of the microcomputer, and connecting the base of the transistor with the control terminal of the microcomputer The electric motor control device according to claim 6, wherein the FET constituting the upper arm is switched on and off by switching on and off.
According to the above configuration, since there is no need to perform switching operation of the FET constituting the upper arm, the gate drive circuit of the FET is omitted, and the on / off of the transistor is switched by the output of the microcomputer. Can be switched on and off.

(G) the multi-phase electric motor is a three-phase electric motor;
When one of the three phases fails, if both normal two-phase currents are flowing out from the driving means, the neutral point driving circuit is fixed at a low output, and the normal two-phase When both currents are flowing into the driving means, the neutral point driving circuit is fixed at a high output, and when the normal two-phase current directions are different from each other, the neutral point driving circuit is set to 50%. The electric motor control device according to claim 4, wherein PWM control is performed with a duty.
According to the above configuration, the motor can be continuously driven by PWM control to 50% duty instead of fixing the neutral point driving circuit to the high impedance output.

(H) The electric motor control device according to any one of claims 1 to 3, wherein when the neutral point of the multiphase electric motor has a ground fault, the neutral point driving circuit is fixed at a low output. .
According to the above configuration, the electric motor can be driven even if the neutral point has a ground fault.

(Li) The electric motor control device according to any one of claims 1 to 3, wherein the multiphase electric motor is an electric motor that generates a steering assist force in an electric power steering device for a vehicle.
According to the above configuration, even if a failure occurs in any phase of the multiphase electric motor that generates the steering assist force, the drive of the electric motor can be continued by effectively using the power supply voltage. It is possible to suppress the outbreak from occurring.

  DESCRIPTION OF SYMBOLS 100 ... Electric power steering apparatus, 130 ... Electric motor, 130U, 130V, 130W ... Phase coil, 140 ... Drive apparatus, 150 ... Control unit, 151 ... Microcomputer, 300 ... Inverter circuit (drive means), 330U, 330V, 330W ... Phase relay (switching means), 400 ... Pre-driver (drive means), 500 ... Power relay device, 600 ... Neutral point drive circuit, 600H, 600L ... Semiconductor switch, 620 ... Neutral point relay, 700 ... Battery (power supply) )

Claims (5)

A multiphase electric motor in which each phase coil is star-connected,
Driving means for driving the multiphase electric motor;
Switching means connected in series with each of the phase coils;
A neutral point drive circuit connected to a neutral point of the star connection;
In an electric motor control device comprising:
When a failure occurs in any one of the phases of the multiphase electric motor, the phase in which the failure has occurred is blocked by the switching means, and the output of the neutral point drive circuit is changed in the cutoff state An electric motor control device.   The electric motor control device according to claim 1, wherein the output of the neutral point driving circuit is continuously changed by duty control.   The output of the neutral point driving circuit is switched between two states of fixed high output and fixed low output, or three states of fixed high output, fixed low output, and fixed high impedance output. Control device for electric motor.   The electric motor control device according to claim 1, wherein the output of the neutral point driving circuit is switched between three states of fixed high output, fixed low output, and duty output state.   5. The electric motor control device according to claim 2, wherein a frequency of PWM control of the neutral point drive circuit is smaller than a frequency of PWM control of the drive unit. 6.