JP2008271485A - Bandpass filter, high-frequency module using the same, and radio communication device using them - Google Patents

Abstract

<P>PROBLEM TO BE SOLVED: To provide a band pass filter having a pass band width appropriate as a bandpass filter for UWB and an attnuation pole in the vicinity of the both sides of the pass band. <P>SOLUTION: The present invention relates to a bandpass filter including: a layered body configured by layering a plurality of dielectric layers 11; first and second grounding electrodes 21 and 22 disposed on upper and lower surfaces of the layered body; band-like first resonance electrodes 30a, 30b, 30c, 30d disposed laterally side by side in a portion between layers; an input coupling electrode 40a that is disposed to oppose to the resonance electrode 30a of an input stage between upper layers; an output coupling electrode 40b disposed to oppose to the resonance electrode 30d of an output stage; a resonance electrode coupling conductor 32 disposed between lower layers and including regions facing the resonance electrodes, respectively, so as to approximately equally couple an electromagnetic field to the resonance electrode 30a on the input stage and the resonance electrode 30d on the output stage; and second resonance electrodes 33a, 33b formed, between further lower layers, with a length different from that of the first resonance electrodes. <P>COPYRIGHT: (C)2009,JPO&INPIT

Description

  The present invention relates to a bandpass filter, a high-frequency module using the same, and a wireless communication device using the same, and more particularly to a bandpass filter having a very wide passband that can be suitably used for UWB (Ultra Wide Band) and The present invention relates to a high-frequency module using the same and a wireless communication device using the same.

  In recent years, UWB has attracted attention as a new communication means. UWB realizes large-capacity data transfer using a wide frequency band over a short distance of about 10 m. For example, according to US FCC (Federal Communication Commission) regulations, a plan to use a frequency band of 3.1 to 10.6 GHz It has become. Thus, the feature of UWB is that it uses a very wide frequency band. In Japan and ITU-R, a low band that uses a band of about 3.1 to 4.7 GHz and a high band that uses a band of about 6 GHz to 10.6 GHz in a form avoiding 5.3 GHz used in IEEE802.11.a. Standards divided into “high band” have been drafted, and a filter for low band (low band) is required to have a characteristic of sharply attenuating at 2.5 GHz and 5.3 GHz.

  In recent years, research on ultra-wideband filters that can be used for UWB has been actively conducted. For example, a bandpass filter that applies the principle of a directional coupler has a passband width of a specific bandwidth (bandwidth / center). There is a report that a broadband characteristic exceeding 100% is obtained in (frequency) (for example, see Non-Patent Document 1).

  On the other hand, as a filter often used conventionally, there is known a band-pass filter configured by connecting a plurality of quarter-wavelength stripline resonators to each other (see, for example, Patent Document 1).

Also, a plurality of resonator internal conductors (¼ wavelength stripline resonators) arranged in an interdigital manner so that the short-circuited end and the open end are staggered are provided, and each resonator internal conductor is provided. A multilayer dielectric filter having a configuration in which a short-circuit end connection pattern that connects between outer resonator conductors in the vicinity of a short-circuit end of an adjacent resonator inner conductor is embedded in a layer different from the layer is known (for example, Patent Documents). 2).
“Ultra-wideband bandpass filter using microstrip-CPW broadside coupling structure” Proceedings of the March 2005 IEICE General Conference C-2-114 p.147 JP 2004-180032 A JP 11-88009 A

  However, each of the bandpass filters described above has problems, and is not suitable for a UWB bandpass filter.

  For example, the bandpass filter proposed in Non-Patent Document 1 has a problem that the passband width is too wide. That is, UWB finally uses a frequency band of 3.1 GHz to 10.6 GHz, but initially it is planned to use a frequency band of about 3.1 GHz to 4.7 GHz, and the specific band is about 40%. Therefore, the filter used for this is required to have a pass bandwidth of about 40% in a specific band. In addition, it is necessary to consider the influence with W-LAN (IEEE 802.11.a), and attenuation at 5.15 GHz is required. Therefore, the bandpass filter proposed in Non-Patent Document 1 having a characteristic such that the passband width exceeds 100% in the specific band cannot be used because the passband width is too wide.

  Further, the pass band width of a bandpass filter using a conventional quarter wavelength resonator is too narrow, and even if the pass band width of the band pass filter described in Patent Document 1 is intended to be wide, it is 10 It was less than%. Therefore, it cannot be used as a bandpass filter for UWB requiring a wide pass bandwidth corresponding to about 40% in the specific band.

  Furthermore, in the bandpass filter described in Patent Document 2, since only one attenuation pole can be generated on either the low band side or the high band side of the pass band, 2.5 GHz in the vicinity of both sides of the pass band. However, it was not usable as a low band filter for UWB that needs to be attenuated sharply at 5.3 GHz.

  The present invention has been devised in view of such problems in the prior art, and its purpose is to provide an ultra-wideband and appropriate passband that can be suitably used as a UWB Low Band bandpass filter. An object of the present invention is to provide a bandpass filter having a width and having attenuation poles in the vicinity of both sides of a passband, a high-frequency module using the same, and a wireless communication device using them.

  The band-pass filter of the present invention includes a laminated body in which a plurality of dielectric layers are laminated, a first ground electrode that is disposed on the lower surface of the laminated body and connected to a ground potential, and an upper surface of the laminated body And a second ground electrode connected to the ground potential and arranged side by side so as to be electromagnetically coupled to each other between one layer of the laminate, each having one end connected to the ground potential Four or more band-shaped first resonance electrodes functioning as quarter-wave resonators, and the four or more first resonance electrodes disposed between the layers above the one layer of the laminate. And a strip-shaped input coupling electrode that is electromagnetically coupled to the resonance electrode of the input stage, a strip-shaped output coupling electrode that is electromagnetically coupled to the resonance electrode of the output stage, and a lower layer than the one layer of the laminate. Disposed at one end through the first through conductor Near the one end of the foremost resonance electrode constituting the resonance electrode group composed of four or more adjacent first resonance electrodes, the other end is connected via the first through conductor. Connected to a ground potential in the vicinity of the one end of the last-stage resonance electrode constituting the resonance electrode group, and the first-stage resonance electrode of the resonance electrode group and the last-stage resonance of the resonance electrode group A resonance electrode coupling conductor having a region facing each resonance electrode so as to be electromagnetically coupled to the electrode; and an interlayer below the one layer of the multilayer body where the resonance electrode coupling conductor is disposed; Are arranged between different layers in parallel to the first resonance electrode, one end of which is connected to the ground potential via a second through conductor, and is formed in a strip shape having a length different from that of the first resonance electrode. , Cut outside the passband A band-pass filter comprising one or more second resonance electrodes having a resonance frequency in the vicinity of an off-frequency, wherein the one or more ends of the four or more first resonance electrodes are staggered. The input coupling electrode is disposed so as to face a region extending over half the length direction of the resonance electrode of the input stage, and a position to which an electric signal input from an external circuit is supplied Is located closer to the other end of the resonance electrode of the input stage than the center in the length direction, and the output coupling electrode is opposed to a region extending over half of the length direction of the resonance electrode of the output stage. And the position from which the electrical signal output to the external circuit is taken out is closer to the other end of the resonance electrode of the output stage than the center in the length direction. It is.

  In the bandpass filter of the present invention, in the above configuration, the resonance electrode coupling conductor includes a front-side coupling region facing the front-stage resonance electrode of the resonance electrode group, and the last-stage resonance electrode group. It is composed of a rear side coupling region facing the resonance electrode, and a connection region that connects the front side coupling region and the rear side coupling region perpendicularly to these regions.

  Furthermore, the band-pass filter of the present invention has the above-described configuration, wherein the front-side coupling region faces the input coupling electrode through the coupling electrode of the input stage, and the rear-side coupling region is a resonance electrode of the output stage. The front-side coupling region has a band shape, and a central axis extending in the length direction of the front-side coupling region as viewed from above extends in the length direction of the input coupling electrode. Arranged so as not to overlap the central axis, the rear-side coupling region has a strip shape, and a central axis extending in the length direction of the rear-side coupling region when viewed from above extends in the length direction of the output coupling electrode. It is arrange | positioned so that it may not overlap with a center axis line.

  Furthermore, the band-pass filter of the present invention is arranged so that the front-side coupling region does not overlap with the central axis extending in the length direction of the input coupling electrode when viewed from above, in the above configuration. As seen, the rear-stage coupling region is arranged so as not to overlap a central axis extending in the length direction of the output coupling electrode.

  Furthermore, the band-pass filter of the present invention includes an even number of the first resonance electrodes and an even number of the second resonance electrodes in each of the above configurations, and these second resonance electrodes are viewed from above. A line segment connecting one end of the resonance electrode of the input stage and one end of the resonance electrode of the output stage and a line segment connecting the other end of the resonance electrode of the input stage and the other end of the resonance electrode of the output stage. They are arranged symmetrically with respect to the intersection.

  Furthermore, the band-pass filter of the present invention is formed in an annular shape surrounding the four or more first resonance electrodes between the one layer in each of the above-described configurations, and the one end of the first resonance electrode. An annular ground electrode connected to the ground potential is arranged and connected to the ground potential.

  Still further, the band-pass filter of the present invention is arranged so as to have a region facing the annular ground electrode and a region facing the first resonance electrode between layers different from the one layer in the above configuration. A region facing the first resonance electrode is connected to the other end side of the first resonance electrode by a third through conductor penetrating the dielectric layer located between the first resonance electrode and the first resonance electrode. The auxiliary resonance electrodes formed are arranged corresponding to each of the four or more first resonance electrodes.

  Furthermore, the band-pass filter of the present invention is the above-described configuration, wherein the input-stage resonance electrode among the four or more auxiliary resonance electrodes is disposed between the one layer and a layer different from the layer where the auxiliary resonance electrode is disposed. The dielectric is disposed so as to have a region facing the auxiliary resonance electrode connected to the region and a region facing the input coupling electrode, and the region facing the input coupling electrode is located between the input coupling electrode and the dielectric An auxiliary input coupling electrode connected to a side closer to the other end of the resonance electrode of the input stage than a center in the length direction of the input coupling electrode by a fourth through conductor penetrating the layer; and the one interlayer and A region facing the auxiliary resonance electrode connected to the resonance electrode of the output stage among four or more auxiliary resonance electrodes between layers different from the layer where the auxiliary resonance electrode is disposed, and the output coupling electrode A length of the output coupling electrode by a fifth through conductor penetrating the dielectric layer located between the output coupling electrode and the region facing the output coupling electrode. And an auxiliary output coupling electrode connected to the side closer to the other end of the resonance electrode of the output stage than the center of the direction.

  Still further, the band-pass filter of the present invention is a band-shaped input coupling resonance electrode that is electromagnetically coupled to the input coupling electrode and functions as a ¼ wavelength resonator with one end connected to the ground potential in each of the above configurations. And at least one of the strip-shaped output coupling resonance electrodes that electromagnetically couple with the output coupling electrode is outside the arrangement region from the resonance electrode of the input stage to the resonance electrode of the output stage when viewed from above, and It is characterized in that the input coupling electrode and the output coupling electrode are arranged between the layers above the layer where the input coupling electrode and the output coupling electrode are arranged.

  A high-frequency module according to the present invention includes the band-pass filter according to the present invention having any one of the above-described configurations.

  The wireless communication device of the present invention is characterized by using the band-pass filter of the present invention having any one of the above-described configurations or the high-frequency module of the present invention having the above-described configuration.

  In the band-pass filter of the present invention, four or more strip-shaped first resonance electrodes that function as quarter-wave resonators with one end connected to the ground potential are mutually electromagnetically coupled between one layer of the laminate. Thus, the one end and the other end of each of the four or more first resonance electrodes are alternately arranged side by side. Since one end and the other end of each of the four or more first resonance electrodes are alternately arranged, the first and second resonance electrodes are coupled in an interdigital manner. A stronger bond occurs compared to a type bond. As a result, it is suitable as a bandpass filter for UWB, in which the frequency interval between the resonance frequencies in each resonance mode far exceeds the range that could be realized by a filter using a conventional quarter wavelength resonator. In order to obtain a wide pass bandwidth of about 40% in a specific bandwidth, it can be made appropriate.

  Further, the band-pass filter of the present invention has four or more adjacent one ends disposed through the first through conductor, disposed between the layers below the layer where the first resonance electrode of the multilayer body is disposed. Near the one end of the foremost resonance electrode constituting the resonance electrode group composed of an even number of first resonance electrodes, the other end is connected to the ground potential via the first through conductor. Connected to the ground potential in the vicinity of one end of the last-stage resonance electrode, and connected to each resonance electrode so as to be electromagnetically coupled to the foremost resonance electrode of the resonance electrode group and the last-stage resonance electrode of the resonance electrode group. A resonant electrode coupling conductor having opposing regions is provided. With this configuration, inductive coupling is generated by the resonance electrode coupling conductor between the resonance electrode at the foremost stage and the resonance electrode at the last stage of the resonance electrode group including four or more adjacent first resonance electrodes. Adjacent resonant electrodes are coupled in an interdigital manner, and are strongly coupled with the addition of magnetic field coupling and electric field coupling, but as a whole, capacitive coupling. For this reason, by inductive coupling via the resonant electrode coupling conductor between the frontmost resonance electrode and the last resonance electrode of the resonance electrode group composed of four or more adjacent first resonance electrodes. A phase difference of 180 ° is generated between the transmitted signal and the signal transmitted by capacitive coupling between the adjacent resonance electrodes, thereby causing a phenomenon in which they cancel each other. Since this phenomenon can occur near both sides of the passband of the bandpass filter, an attenuation pole that hardly transmits a signal near both sides of the passband can be formed in the pass characteristics of the bandpass filter.

  Note that the number of resonance electrodes constituting the resonance electrode group that causes inductive coupling via the resonance electrode coupling conductor between the first-stage resonance electrode and the last-stage resonance electrode is an even number of 4 or more. It is necessary to have the effect of the present invention.

  For example, if the number of resonance electrodes constituting the resonance electrode group is an odd number, even if inductive coupling is caused by the resonance electrode coupling conductor between the first resonance electrode and the last resonance electrode. Phenomenon in which a phase difference of 180 ° occurs between a signal transmitted by inductive coupling via a resonant electrode coupling conductor and a signal transmitted by capacitive coupling between adjacent resonant electrodes, thereby canceling each other Is generated only on the high frequency side of the pass band of the band pass filter, and therefore, attenuation poles cannot be formed near both sides of the pass band in the pass characteristic of the band pass filter.

  In addition, when the number of resonance electrodes constituting the resonance electrode group is two, even if the resonance electrodes are connected by a resonance electrode coupling conductor, LC caused by inductive coupling and capacitive coupling between the resonance electrodes Since only a parallel resonant circuit is formed, only one attenuation pole is formed, and no attenuation pole can be formed near both sides of the passband.

  Furthermore, in the bandpass filter of the present invention, the front-side coupling region faces the input coupling electrode through the input-stage coupling electrode, and the rear-stage coupling region faces the output coupling electrode through the output-stage resonance electrode. In addition, the front-side coupling region has a band shape, and the central axis extending in the length direction of the front-side coupling region when viewed from above is disposed so as not to overlap the central axis extending in the length direction of the input coupling electrode. The side coupling region has a band shape, and is arranged so that the central axis extending in the length direction of the rear side coupling region as viewed from above does not overlap with the central axis extending in the length direction of the output coupling electrode. As a result, the central axis extending in the length direction of the front-side coupling region when viewed from above overlaps with the central axis extending in the length direction of the input coupling electrode, and the central axis extending in the length direction of the rear-side coupling region is the output coupling electrode. As compared with the case where the center axis extends in the length direction, the attenuation characteristic outside the passband of the bandpass filter can be improved. This mechanism can be estimated as follows. That is, the input coupling electrode and the output coupling electrode are respectively opposed to the front-side coupling region and the rear-side coupling region of the resonant electrode coupling conductor via the resonant electrode of the input stage and the resonant electrode of the output stage, respectively. Since the resonance electrode coupling conductor is coupled by a magnetic field coupling, spurious is generated in the pass characteristic of the band-pass filter at a frequency at which the resonance electrode coupling conductor resonates at ½ wavelength. Here, the central axis extending in the length direction of the front-side coupling region of the resonant electrode coupling conductor and the central axis extending in the length direction of the rear-side coupling region are respectively the central axis and output coupling extending in the length direction of the input coupling electrode. By arranging so as not to overlap the central axis extending in the length direction of the electrode, inductive coupling between the front-side coupling region of the resonant electrode coupling conductor and the input coupling electrode, and the rear-side coupling region and the output coupling region of the resonant electrode coupling conductor This is probably because the inductive coupling with each other becomes smaller.

  Still further, according to the bandpass filter of this example, one or more second resonance electrodes that function as a reaction resonator (notch filter) and have a resonance frequency near the cutoff frequency outside the passband are, for example, By arranging between the resonant electrode at the input stage and the resonant electrode at the second stage as viewed from above and coupling with the first resonant electrode, the attenuation pole formed by the resonant electrode coupling conductor and the cutoff frequency can be reduced. A further attenuation pole is formed between them, so that a steeper attenuation characteristic can be obtained.

  Furthermore, according to the band-pass filter of the present invention, the input coupling electrode is disposed so as to face a region extending over half the length direction of the resonance electrode of the input stage, and is an electric signal input from an external circuit Is provided on the side closer to the other end of the resonance electrode of the input stage than the center in the length direction, and the output coupling electrode is in a region extending over half of the length of the resonance electrode of the output stage. The position where the electrical signal output to the external circuit is arranged so as to face each other is the side closer to the other end of the resonance electrode of the output stage than the center in the length direction. With this configuration, the input coupling electrode and the input stage resonance electrode are coupled in an interdigital manner, and similarly, the output coupling electrode and the output stage resonance electrode are coupled in an interdigital manner. In the same manner as above, the coupling by the magnetic field and the coupling by the electric field are added to produce a strong coupling. As a result, even at a wide passband far exceeding the range that could be realized by a filter using a conventional quarter wavelength resonator, insertion at a frequency located between the resonance frequencies of the respective resonance modes It is possible to obtain a bandpass filter having flat and low-loss pass characteristics over the entire wide passband with no significant increase in loss.

  Furthermore, according to the bandpass filter of the present invention, the ground potential is formed in an annular shape surrounding the periphery of four or more first resonance electrodes between one layer, and one end of the first resonance electrodes is connected. When the annular ground electrodes connected to the first resonant electrode are arranged, there are electrodes connected to the ground potential on both sides in the length direction of the first resonant electrode. One end of each resonance electrode can be easily connected to the ground potential.

  Furthermore, according to the bandpass filter of the present invention, there are four or more auxiliary resonant electrodes arranged so as to have a region facing the annular ground electrode and connected to the first resonant electrode by the third through conductor. When each of the first resonance electrodes is arranged corresponding to each of the first resonance electrodes, an electrostatic capacity is generated between the auxiliary resonance electrode and the annular ground electrode. Can be shortened, and a small bandpass filter can be obtained.

  Still further, according to the bandpass filter of the present invention, the auxiliary input coupling electrode connected to the input coupling electrode, arranged to have a region facing the auxiliary resonant electrode connected to the resonant electrode of the input stage, and the output An auxiliary output coupling electrode connected to the output coupling electrode and having an area opposed to the auxiliary resonance electrode connected to the stage resonance electrode, the auxiliary connected to the input stage resonance electrode. Electromagnetic field coupling occurs between the resonant electrode and the auxiliary input coupling electrode, which is added to the electromagnetic coupling between the resonant electrode and the input coupling electrode of the input stage, and similarly connected to the resonant electrode of the output stage. An electromagnetic field coupling occurs between the auxiliary resonance electrode and the auxiliary output coupling electrode, and is added to the electromagnetic field coupling between the resonance electrode and the output coupling electrode in the output stage. As a result, the electromagnetic coupling between the input coupling electrode and the resonance electrode of the input stage and the electromagnetic coupling between the output coupling electrode and the resonance electrode of the output stage are further strengthened. However, a bandpass filter having a flatter and lower-loss pass characteristic over a wide passband, in which an increase in insertion loss at a frequency located between the resonance frequencies of the respective resonance modes is further reduced. Obtainable.

  Furthermore, according to the bandpass filter of the present invention, the auxiliary input coupling electrode is connected to the side closer to the other end of the resonance electrode of the input stage than the center in the length direction of the input coupling electrode by the fourth through conductor, Similarly, when the auxiliary output coupling electrode is connected to the side closer to the other end of the resonance electrode of the output stage than the center in the length direction of the output coupling electrode by the fifth through conductor, the electric signal input from the outside is Even when an electrical signal supplied to the input coupling electrode via the auxiliary input coupling electrode and taken out from the output coupling electrode is output to an external circuit via the auxiliary output coupling electrode, the input coupling electrode and the resonance electrode of the input stage Is coupled to the interdigital type, and the output coupling electrode and the output stage resonance electrode are coupled to the interdigital type. It can be generated.

  Furthermore, an input coupling electrode that functions as a quarter-wave resonator with one end connected to ground potential so as to couple to the input coupling electrode and the output coupling electrode without affecting the first resonant electrode; At least one of the band-like input coupling resonance electrode that electromagnetically couples and the band-like output coupling resonance electrode that electromagnetically couples to the output coupling electrode is from an arrangement region from the resonance electrode of the input stage to the resonance electrode of the output stage when viewed from above. Is formed outside the layer where the input coupling electrode and the output coupling electrode are disposed, and forms an attenuation pole separate from the attenuation pole formed by the second resonance electrode. By increasing the attenuation pole in the vicinity of the high-frequency passband without changing the size of the passband, it is possible to obtain steep filter characteristics in which the amount of attenuation changes abruptly from the passband to the stopband. That.

  According to the high-frequency module of the present invention and the wireless communication device of the present invention, the band-pass filter of the present invention with a small loss of the signal passing over the entire communication band is used for filtering the transmission signal and the reception signal. Since the attenuation of the reception signal and the transmission signal passing through the pass filter is reduced, the reception sensitivity is improved, and the amplification degree of the transmission signal and the reception signal can be reduced, so that the power consumption in the amplifier circuit is reduced. Therefore, a high-performance high-frequency module and wireless communication device with high reception sensitivity and low power consumption can be obtained.

  Hereinafter, a band-pass filter of the present invention, a high-frequency module using the same, and a wireless communication device using the same will be described in detail with reference to the accompanying drawings.

(First example of embodiment)
FIG. 1 is a schematic exploded perspective view of a bandpass filter of the present invention.

  The band-pass filter of this example includes a laminated body in which a plurality of dielectric layers 11 are laminated, a first ground electrode 21 arranged on the lower surface of the laminated body, and a second electrode arranged on the upper surface of the laminated body. The ground electrode 22, the strip-shaped first resonance electrodes 30a, 30b, 30c, and 30d arranged side by side between one layer of the multilayer body, and the first resonance electrodes 30a, 30b, An annular ground electrode 23 formed in an annular shape surrounding the periphery of 30c, 30d and connected to one end of the first resonance electrodes 30a, 30b, 30c, 30d, and an input stage between layers above one layer of the laminate. A strip-shaped input coupling electrode 40a disposed so as to face the resonance electrode 30a, a strip-shaped output coupling electrode 40b disposed so as to face the resonance electrode 30d of the output stage, and one layer below the laminate. Between one side and the other end via the first through conductor 51 A resonant electrode coupling conductor 32 connected to the ground electrode 23 and having a region facing each resonant electrode so as to be substantially electromagnetically coupled to the resonant electrode 30a at the input stage and the resonant electrode 30d at the output stage; The first resonance electrodes 30a, 30b, 30c, and 30d are arranged in parallel to the lower layers below the layer where the electrode coupling conductor 32 is arranged, and one end thereof is connected to the ground potential via the second through conductor. Second resonance electrodes 33a and 33b formed to have different lengths from the first resonance electrodes 30a, 30b, 30c and 30d, and an input terminal electrode 60a which is disposed on the upper surface of the laminate and connected to the input coupling electrode 40a And an output terminal electrode 60b connected to the output coupling electrode 40b.

  Although the first ground electrode 21 is hidden in the drawing, the first ground electrode 21 is disposed on the entire lower surface of the multilayer body (the back surface of the dielectric layer 11 on which the second resonance electrodes 33a and 33b are formed). 22 is arranged on almost the whole surface except for the periphery of the input terminal electrode 60a and the output terminal electrode 60b on the upper surface of the laminate, and both are connected to the ground potential and are striplined together with the resonance electrodes 30a, 30b, 30c and 30d. It constitutes a resonator.

  The strip-shaped first resonance electrodes 30 a, 30 b, 30 c, and 30 d constitute a stripline resonator together with the first ground electrode 21 and the second ground electrode 22, and one end thereof is connected to the annular ground electrode 23. By being connected to the ground potential, it functions as a quarter wavelength resonator.

  The first resonance electrodes 30a, 30b, 30c, and 30d are arranged side by side between one layer of the multilayer body and are electromagnetically coupled to each other. Since the layers are arranged side by side between the same layers and are electromagnetically coupled, the coupling between the first resonance electrodes 30a, 30b, 30c, and 30d is not broadside coupling but edge coupling. If the distance between the first resonance electrodes 30a, 30b, 30c, and 30d is small, strong coupling is obtained. However, if the distance is small, manufacturing becomes difficult, so the distance is set to about 0.05 to 0.5 mm, for example. Further, the first resonance electrodes 30a, 30b, 30c, and 30d have their one end and the other end arranged alternately so as to be coupled to each other in an interdigital manner. It is added, and it is strongly coupled compared with the case of coupling to the combline type. In this way, the resonant electrodes 30a, 30b, 30c, and 30d are edge-coupled to each other and coupled in an interdigital manner, so that the frequency interval between the resonant frequencies in each resonant mode can be changed to the conventional 1/4 wavelength resonance. It is reasonable to obtain a wide passband width of about 40% in a specific band suitable as a bandpass filter for UWB, far exceeding the range that could be realized by a filter using a filter.

  If the first resonant electrodes 30a, 30b, 30c, and 30d are coupled in an interdigital manner and are broad-side coupled to each other, the coupling becomes too strong and the pass bandwidth is about 40% in the specific band. It was found by examination that it is not preferable for realizing the above.

  In the band-pass filter of the present invention, the number of first resonance electrodes may be four or more. However, as the number of first resonance electrodes increases, the size of the band-pass filter and the loss in the passband increase. Therefore, in practice, the number of first resonance electrodes is often set to about 10 or less.

  The annular ground electrode 23 is formed in an annular shape surrounding one of the first resonance electrodes 30a, 30b, 30c, and 30d between one layer of the laminate, and one of the first resonance electrodes 30a, 30b, 30c, and 30d. Connected to the end. And it has a function which connects one end of 1st resonance electrode 30a, 30b, 30c, 30d to earth potential by connecting itself to earth potential. By providing the annular ground electrode 23, the first resonant electrodes 30a, 30b, 30c, 30d arranged in an interdigital manner can be used even when a band-pass filter is formed in a part of the module substrate. Can be easily connected to the ground potential. Further, the annular ground electrode 23 surrounds the first resonance electrodes 30a, 30b, 30c, and 30d in an annular shape, thereby leaking electromagnetic waves generated from the first resonance electrodes 30a, 30b, 30c, and 30d to the surroundings. Can be reduced. This effect is particularly useful in preventing adverse effects on other areas of the module substrate when a bandpass filter is formed in a partial area of the module substrate.

  The band-shaped input coupling electrode 40a is different from the layer in which the first resonance electrodes 30a, 30b, 30c, 30d are arranged (above the layer in which the first resonance electrodes 30a, 30b, 30c, 30d are arranged). Almost all of them are arranged so as to face the resonance electrode 30a of the input stage, and face a region extending over half of the length direction of the resonance electrode 30a of the input stage. Therefore, the input coupling electrode 40a and the input stage resonance electrode 30a are broadside coupled, and are strongly coupled as compared to the edge coupling. Further, in the band-like input coupling electrode 40a, the end where the connection point between the input coupling electrode 40a and the through conductor 50 is closer to the other end of the resonance electrode 30a in the input stage than the center in the length direction of the input coupling electrode 40a. The opposite end is an open end. An electrical signal input from an external circuit is supplied to the input coupling electrode 40a from this connection point. As a result, the input coupling electrode 40a and the input stage resonance electrode 30a are coupled in an interdigital manner, and the coupling due to the magnetic field and the coupling due to the electric field are added and coupled in the combline type or simply capacitively coupled. The bond is stronger than in the case. Thus, the input coupling electrode 40a is broad-side coupled to the input stage resonance electrode 30a and is interdigitally coupled to the entire input coupling electrode 40a. Are connected. Similarly, the output coupling electrode 40b is broadside-coupled to the output-stage resonance electrode 30d and is also interdigitally coupled.

  In this way, the input coupling electrode 40a and the input stage resonance electrode 30a are very strongly coupled, and the output coupling electrode 40b and the output stage resonance electrode 30d are very strongly coupled. Even in a wide passband far exceeding the region that could be realized with a filter using a resonator, the insertion loss at frequencies located between the resonance frequencies of the respective resonance modes does not increase significantly. A bandpass filter having flat and low-loss pass characteristics over the entire wide passband can be obtained.

  It is preferable that the shape and dimensions of the input coupling electrode 40a and the output coupling electrode 40b are set to the same level as the resonance electrode 30a at the input stage and the resonance electrode 30d at the output stage. If the distance between the input coupling electrode 40a and the input stage resonance electrode 30a and the distance between the output coupling electrode 40b and the output stage resonance electrode 30d are reduced, the coupling becomes stronger but difficult to manufacture. It is set to about 0.5 mm.

  The resonance electrode coupling conductor 32 is different from the layer where the first resonance electrodes 30a, 30b, 30c, 30d are disposed (lower than the layer where the first resonance electrodes 30a, 30b, 30c, 30d are disposed). Between the two layers). Then, one end is connected to the annular ground electrode 23 in the vicinity of one end of the input stage resonance electrode 30a through the first through conductor 51, and the other end is connected to the output stage resonance through the first through conductor 51. The electrode 30d is connected to the annular ground electrode 23 in the vicinity of one end thereof, and has an electromagnetic field coupling region opposite to the input stage resonant electrode 30a and the output stage resonant electrode 30d. According to this structure, the resonance electrode 30a at the input stage and the resonance electrode 30d at the output stage are inductively coupled via the resonance electrode coupling conductor 32.

  Here, the first resonance electrodes 30a, 30b, 30c, and 30d constitute a resonance electrode group including four adjacent first resonance electrodes, and the resonance electrode 30a in the input stage constitutes the resonance electrode group. The resonance electrode 30d at the output stage is the last-stage resonance electrode constituting the resonance electrode group. Therefore, the input stage resonance electrode 30a, which is the foremost resonance electrode of the resonance electrode group composed of four adjacent first resonance electrodes, and the output stage resonance electrode 30d, which is the last resonance electrode of the resonance electrode group, Inductive coupling is caused by the resonant electrode coupling conductor 32 between the two. The adjacent first resonance electrodes 30a, 30b, 30c, and 30d are coupled in an interdigital manner, and are strongly coupled by adding a coupling by a magnetic field and a coupling by an electric field. It is a combination of.

  For this reason, the resonance electrode coupling conductor 32 is interposed between the first resonance electrode and the last resonance electrode of the resonance electrode group composed of the four adjacent first resonance electrodes 30a, 30b, 30c, and 30d. A phase difference of 180 ° occurs between the signal transmitted by the inductive coupling and the signal transmitted by the capacitive coupling between the adjacent first resonance electrodes 30a, 30b, 30c, and 30d, thereby canceling each other. A matching phenomenon can be generated. Since this phenomenon can occur near both sides of the passband of the bandpass filter, an attenuation pole that hardly transmits a signal near both sides of the passband can be formed in the pass characteristics of the bandpass filter.

  The resonance electrode coupling conductor 32 includes a front-side coupling region 321 that faces the resonance electrode 30a at the input stage, a rear-side coupling region 322 that faces the resonance electrode 30d at the output stage, a front-side coupling region 321 and a rear-side coupling. The region 322 includes a connection region 323 that is orthogonally connected to these regions, and has a so-called crank structure. According to this structure, the side close to one end (short-circuit end) of the resonance electrode 30a in the input stage and the side close to one end (short-circuit end) of the resonance electrode 30d in the output stage are coupled. Here, this resonant electrode coupling conductor 32 is point-symmetric about the point equidistant from one end and the other end of the resonant electrode coupling conductor 32 from the viewpoint of ensuring the structural and electrical symmetry of the bandpass filter. It is preferable to be formed in such a shape. Further, the shape of the resonance electrode coupling conductor 32 is such that the connection region 323 is orthogonal to the front-side coupling region 321 and the rear-side coupling region 322 arranged in parallel to the first resonance electrodes 30a, 30b, 30c, 30d. By doing so, the first resonance electrodes 30a, 30b, 30c, 30d and the connection region 323 are orthogonal to each other when viewed in plan, so the first resonance electrodes 30a, 30b, 30c, 30d and the connection region Deterioration of electrical characteristics due to unnecessary coupling with 323 can be prevented. For example, a structure in which a bent portion is rounded or a structure in which the connection region 323 is not orthogonal to the front-side coupling region 321 and the rear-side coupling region 322 can be adopted as other shapes. Further, by arranging the respective regions of the resonance electrode coupling conductor 32 between different layers and connecting them using through conductors, the resonance electrode coupling conductor 32 and the resonance electrode 30a at the input stage and the resonance electrode 30d at the output stage are connected. The amount of coupling with may be adjusted.

  The band-like second resonance electrodes 33a and 33b are arranged in parallel to the first resonance electrodes 30a, 30b, 30c and 30d between layers below the layer where the resonance electrode coupling conductor 32 is arranged, The resonant electrodes 30a, 30b, 30c, and 30d are formed to have a different length (in this example, a shorter length). One end of each of the second resonance electrodes 33 a and 33 b is connected to the annular ground electrode 23 via the second through conductor 52. Specifically, the second resonant electrode 33a is connected to the vicinity of one end of the first resonant electrode 30b via the second through conductor 52, and the second resonant electrode 33b is connected to the second through conductor 52. Is connected in the vicinity of one end of the first resonance electrode 30c. This structure has a resonance frequency in the vicinity of the cutoff frequency outside the passband, and functions as a so-called reaction resonator (notch filter). The vicinity of the cut-off frequency outside the passband refers to a frequency region between the attenuation pole formed by the resonant electrode coupling conductor 32 and the cutoff frequency, and the attenuation formed by the resonant electrode coupling conductor 32. The pole means an attenuation pole formed near both sides of the pass band in the configuration in which the second resonance electrodes 33a and 33b are not arranged.

  Here, the number of the second resonance electrodes may be one or more so long as the loss in the pass band of the filter does not increase. Since the directionality is lost and the design of the filter is facilitated, the second resonance electrode is preferably arranged point-symmetrically with respect to the center of the filter region surrounded by the annular ground electrode 23. Therefore, as shown in FIG. 1, the band-pass filter of the present invention includes an even number of first resonance electrodes (four in this example) and an even number of second resonance electrodes (two in this example). When viewed from above, a line segment connecting one end of the input stage resonance electrode 30a and one end of the output stage resonance electrode 30d, the other end of the input stage resonance electrode 30a, and the other end of the output stage resonance electrode 30d. It is preferable that the second resonance electrode is arranged point-symmetrically around the intersection with the line segment connecting the two.

  In this example, the second resonance electrodes 33a and 33b are formed shorter than the first resonance electrodes 30a, 30b, 30c and 30d, but this is the second resonance electrode higher than the passband. This is because an attenuation pole is formed by the electrodes 33a and 33b. That is, when the attenuation pole is formed on the lower side of the pass band, the lengths of the second resonance electrodes 33a and 33b are formed longer than the first resonance electrodes 30a, 30b, 30c and 30d, and are longer than the pass band. When the attenuation pole is formed on the high frequency side, the second resonance electrodes 33a and 33b are formed shorter than the first resonance electrodes 30a, 30b, 30c and 30d.

  Further, in this example, the layer where the second resonance electrodes 33a and 33b are arranged is located below the layer where the resonance electrode coupling conductor 32 is arranged, but this arrangement may be reversed.

  According to the configuration in which the band-like second resonance electrodes 33a and 33b are provided in this way, compared with the attenuation characteristic obtained in the configuration in which the second resonance electrodes 33a and 33b are not arranged, the passband is a stop band. Attenuation characteristics that change more steeply can be obtained.

  Here, when the second resonance electrode is provided, it is necessary to consider the amount of coupling between the second resonance electrode and the first resonance electrode. Specifically, when the second resonance electrode is longer than the first resonance electrode, the ratio of the length (area) overlapping the first resonance electrode to the entire length direction of the second resonance electrode is small. Therefore, in order to increase the amount of coupling, it is arranged to be close to the first resonance electrode that is interdigital (the side connected to the ground potential is reversed) when viewed from above, and when it is most desired to couple, the interdigital relationship It is preferable to arrange so as to face the first resonance electrode. On the other hand, when the second resonance electrode is shorter than the first resonance electrode, the entire length direction of the second resonance electrode overlaps with the first resonance electrode. The first resonance electrode is preferably disposed so as to be close to the first resonance electrode having a comb line relationship (the side connected to the ground potential is the same). It is preferable that the first electrode is disposed close to the first resonance electrode having a comb line relationship so that all the regions of the resonance electrode do not face each other. The amount of coupling between the first resonance electrode and the second resonance electrode is such that the thickness of the dielectric layer interposed between the first resonance electrode and the second resonance electrode, the width of each resonance electrode, and the opposite amount. It depends on the area of the part. Therefore, it is preferable to dispose the second resonance electrode at a position where a desired coupling amount can be obtained in consideration of these.

  In this example, the second resonance electrode 33a is disposed so as to partially face the first resonance electrode 30b when viewed from above, and the second resonance electrode 33b is identical to the first resonance electrode 30c when viewed from above. It arrange | positions so that a part may oppose.

  Thus, according to the band-pass filter of this example, a very wide passband of 40% in a ratio band far exceeding the range that could be realized by a filter using a conventional quarter wavelength resonator. It is possible to obtain a high-performance band-pass filter that can be suitably used as a UWB filter, having a flat and low-loss pass characteristic over the entire area, and having attenuation poles in the vicinity of both sides of the pass band.

  FIG. 2A is a schematic perspective view of the resonant electrode coupling conductor 32 and the first resonant electrodes 30a, 30b, 30c, and 30d shown in FIG. 1 as viewed from above, and FIG. 1 schematically shows the positional relationship among the front-side coupling region 321 and the rear-side coupling region 322 of the resonant electrode coupling conductor 32 shown in FIG. 1, the first resonant electrodes 30a, 30b, 30c, and 30d, the input coupling electrode 40a, and the output coupling electrode 40b. It is the schematic explanatory drawing seen from the side shown.

  As shown in FIGS. 2A and 2B, in the resonance electrode coupling conductor 32, the front-side coupling region 321 has a strip shape, and a central axis extending in the length direction of the front-side coupling region 321 when viewed from above. Is arranged so as not to overlap the central axis extending in the length direction of the input coupling electrode 40a, and the rear-side coupling region 322 has a strip shape, and the central axis extending in the length direction of the rear-side coupling region 322 when viewed from above Is preferably arranged so as not to overlap the central axis extending in the length direction of the output coupling electrode 40b. Accordingly, inductive coupling between the front-side coupling region 321 and the input coupling electrode 40a and inductive coupling between the rear-side coupling region 322 and the output coupling electrode 40b can be reduced. The level of spurious generated by resonance can be reduced and the pass characteristics of the bandpass filter can be improved.

  Furthermore, as shown in FIG. 2B, when viewed from above, the front-side coupling region 321 is disposed so as not to overlap the central axis extending in the length direction of the input coupling electrode 40a, and the rear-stage side The coupling region 322 is preferably arranged so as not to overlap the central axis extending in the length direction of the output coupling electrode 40b, whereby the first resonant electrodes 30a, 30b, 30c, 30d of the resonant electrode coupled conductor 32 are arranged. The inductive coupling between the front-side coupling region 321 and the input coupling electrode 40a and the inductive coupling between the rear-side coupling region 322 and the output coupling electrode 40b can be further weakened. Also in this case, when viewed from above, the entire front-side coupling region 321 overlaps with the input-stage resonance electrode 30a, and the entire rear-side coupling region 322 overlaps with the output-stage resonance electrode 30d. This can prevent the coupling between the front-side coupling region 321 and the input-stage resonance electrode 30a and the coupling between the rear-side coupling region 322 and the output-stage resonance electrode 30d from weakening.

(Second example of embodiment)
FIG. 3 is an exploded perspective view schematically showing another example of the embodiment of the bandpass filter of the present invention. Note that in this example, only differences from the first example described above will be described, and the same components will be denoted by the same reference numerals, and redundant description will be omitted.

  The difference from the first example of the bandpass filter of this example is that the first resonance electrode is a six-stage bandpass filter composed of 30a, 30b, 30c, 30d, 30e, and 30f. The resonant electrode coupling conductor 32 has one end connected to the annular ground electrode 23 in the vicinity of one end of the input stage resonant electrode 30a via the first through conductor 51, and the other end connected to the first through conductor 51. Is connected to the annular ground electrode 23 in the vicinity of one end of the output stage resonant electrode 30f, and has an electromagnetic field coupling region facing the input stage resonant electrode 30a and the output stage resonant electrode 30f. is doing.

  Also in the band pass filter of this example, one end is connected to the annular ground electrode 23 in the vicinity of one end (short-circuit end) of the resonance electrode 30a of the input stage via the first through conductor 51 and the other end is the first end. A resonance electrode coupling conductor 32 connected to the annular ground electrode 23 in the vicinity of one end (short-circuit end) of the output stage resonance electrode 30f through one through conductor 51, and one end (short-circuit) of the input stage resonance electrode 30a. And the side near the one end (short-circuit end) of the output stage resonance electrode 30f are coupled to each other from the six adjacent first resonance electrodes 30a, 30b, 30c, 30d, 30e, 30f. An input stage resonance electrode 30a, which is the foremost resonance electrode of the resonance electrode group, and an output stage resonance electrode 30f, which is the last resonance electrode of the resonance electrode group, are inductively coupled via the resonance electrode coupling conductor 32. As a result, the resonance electrode coupling conductor is provided between the first resonance electrode and the last resonance electrode of the resonance electrode group composed of the six adjacent first resonance electrodes 30a, 30b, 30c, 30d, 30e, and 30f. 180 ° between the signal transmitted by the inductive coupling via 32 and the signal transmitted by the capacitive coupling between the adjacent first resonance electrodes 30a, 30b, 30c, 30d, 30e, 30f. This causes a phase difference that cancels each other. Since this phenomenon can occur near both sides of the passband of the bandpass filter, an attenuation pole that hardly transmits a signal near both sides of the passband can be formed in the pass characteristics of the bandpass filter. Thereby, it is possible to have a filter characteristic that attenuates sharply outside the passband.

  According to the band-pass filter of this example, since the band-pass filter has a six-stage configuration including the first resonance electrodes 30a, 30b, 30c, 30d, 30e, and 30f, the first resonance electrodes 30a, 30b, 30c, and 30d are used. Compared with the band-pass filter of the first example of the embodiment which is a four-stage band-pass filter according to the above, a steeper band-pass filter can be obtained.

(Third example of embodiment)
FIG. 4 is an exploded perspective view schematically showing still another example of the embodiment of the bandpass filter of the present invention. In this example, only points different from the second example described above will be described, and the same components will be denoted by the same reference numerals, and redundant description will be omitted.

  The difference of the bandpass filter of this example from the second example described above is that the resonance electrode coupling conductor 32 is annular at one end near the one end of the input stage resonance electrode 30a via the first through conductor 51. The other end is connected to the annular ground electrode 23 in the vicinity of one end of the resonance electrode 30d via the first through conductor 51, and is connected to the resonance electrode 30a and the resonance electrode 30d in the input stage, respectively. It has the area | region which opposes an electromagnetic field coupling facing.

  Also in the band pass filter of this example, one end is connected to the annular ground electrode 23 in the vicinity of one end (short-circuit end) of the resonance electrode 30a of the input stage via the first through conductor 51 and the other end is the first end. One end (short circuit) of the resonance electrode 30a of the input stage is connected by a resonance electrode coupling conductor 32 connected to the annular ground electrode 23 in the vicinity of one end (short circuit end) of the first resonance electrode 30d via one through conductor 51. Resonant electrode composed of four adjacent first resonance electrodes 30a, 30b, 30c, 30d by combining the side close to the end) and the side close to one end (short-circuit end) of the first resonance electrode 30d. The resonance electrode 30a of the input stage that is the foremost resonance electrode of the group and the resonance electrode 30d that is the last stage of the resonance electrode group are inductively coupled via the resonance electrode coupling conductor 32. Thus, the resonance electrode coupling conductor 32 is interposed between the first resonance electrode and the last resonance electrode of the resonance electrode group including the four adjacent first resonance electrodes 30a, 30b, 30c, and 30d. A phase difference of 180 ° occurs between the signal transmitted by the inductive coupling and the signal transmitted by the capacitive coupling between the adjacent first resonance electrodes 30a, 30b, 30c, and 30d, thereby canceling each other. A matching phenomenon can be generated. Since this phenomenon can occur near both sides of the passband of the bandpass filter, an attenuation pole that hardly transmits a signal near both sides of the passband can be formed in the pass characteristics of the bandpass filter. As described above, the resonance electrode group may be configured by a part of the plurality of resonance electrodes constituting the band pass filter.

(Fourth example of embodiment)
FIG. 5 is an exploded perspective view schematically showing another example of the embodiment of the bandpass filter of the present invention. Note that in this example, only differences from the first example described above will be described, and the same components will be denoted by the same reference numerals, and redundant description will be omitted.

  The difference from the first example of the bandpass filter of this example is that the first ground electrodes 30a, 30b, 30c, 30d and the annular ground electrode 23 are disposed above the layer where the annular ground electrode 23 is disposed. Auxiliary resonance electrodes 31a, 31b, 31c, and 30d having regions facing each other and regions facing the first resonance electrodes 30a, 30b, 30c, and 30d are arranged, and the first resonance electrodes are designated as 30a, 30b, and 30c. , 30d and an auxiliary resonance having a region opposed to the annular ground electrode 23 and a region opposed to the first resonant electrodes 30a, 30b, 30c, 30d between layers below the layer where the annular ground electrode 23 is disposed. That is, the electrodes 31a, 31b, 31c, and 30d are arranged. The first resonant electrodes 30a, 30b, 30c, 30d and the auxiliary resonant electrodes 31a, 31b, 31c, 31d are connected by a third through conductor 53 that penetrates the dielectric layer 11. As a result, the capacitance between the auxiliary resonant electrodes 31a, 31b, 31c, 31d and the annular ground electrode 23 is added, so the other ends (open ends) of the first resonant electrodes 30a, 30b, 30c, 31d. Since the electrostatic capacitance between the first resonant electrode 30a, 30b, 30c, and 30d can be shortened, a smaller bandpass filter can be obtained.

  In the embodiment shown in FIG. 5, the auxiliary resonance electrodes 31a, 31b, 31c, and 31d are provided in a pair in the upper and lower directions. However, it is necessary to shorten the lengths of the first resonance electrodes 30a, 30b, 30c, and 30d so much. If not, the auxiliary resonance electrodes 31a, 31b, 31c, 31d are provided on either the upper side or the lower side between the layers where the first resonance electrodes 30a, 30b, 30c, 30d and the annular ground electrode 23 are disposed. It may be a structure.

  In addition, with the formation of the auxiliary resonance electrodes 31a and 31d, the layers where the first resonance electrodes 30a, 30b, 30c and 30d and the annular ground electrode 23 are arranged, and the auxiliary resonance electrodes 31a, 31b, 31c and 31d are arranged. An auxiliary input coupling electrode 41a is provided corresponding to the input coupling electrode 40a, and an auxiliary output coupling electrode 41b is provided corresponding to the output coupling electrode 40b.

  In the first example described above, the second resonance electrodes 33a and 33b are formed shorter than the first resonance electrodes 30a, 30b, 30c, and 30d, but the first resonance electrodes 30a, 30b, 30c, and 30d are formed. As a result, the second resonance electrodes 33a and 33b become longer. Therefore, as shown in FIG. 5, by forming the other end opposite to the one end connected to the ground potential of the second resonance electrodes 33a and 33b so as to protrude toward one side, The capacitance formed between the annular ground electrode 23 and the annular ground electrode 23 is increased, thereby shortening the lengths of the second resonance electrodes 33a and 33b as compared with the first example described above. . As for the shape of the second resonance electrodes 33a and 33b, not only the shape as shown in FIG. 5, but also a structure in which the other end is simply bent or a shape in which the other end is formed in a T shape can be adopted.

  Further, since the second resonance electrode is longer than the first resonance electrode as compared with the first example described above, the first resonance electrode is in an interdigital relationship as viewed from above in order to increase the coupling amount. The amount of coupling between the first resonance electrode and the second resonance electrode is adjusted by shifting the second resonance electrodes 33a and 33b closer to each other.

  Although the second resonant electrode is apparently longer than the first resonant electrode, the resonant frequency of the second resonant electrode is higher than the first resonant frequency, so that it is the same as that shown in FIG. In addition, a resonance frequency is provided in the vicinity of the cut-off frequency on the higher frequency side than the passband.

  Thus, according to the bandpass filter of this example, a smaller bandpass filter can be obtained as compared with the bandpass filter of the first example of the embodiment of the present invention described above.

  Further, the auxiliary input coupling electrode 41a shown in FIG. 5 has a band shape, and is arranged to have a region facing the auxiliary resonance electrode 31a and a region facing the input coupling electrode 40a, and the region facing the input coupling electrode 40a is an input. It is connected to the input coupling electrode 40a by a fourth through conductor 54 that penetrates the dielectric layer 11 located between the coupling electrode 40a. As a result, the auxiliary input coupling electrode 41a and the auxiliary resonant electrode 31a are broadside coupled, and this coupling is added to the coupling between the input coupling electrode 40a and the resonant electrode 30a of the input stage, so that the coupling is stronger as a whole. It becomes.

  Similarly, the auxiliary output coupling electrode 41b has a band shape and is disposed so as to have a region facing the auxiliary resonance electrode 31d and a region facing the output coupling electrode 40b, and the region facing the output coupling electrode 40b is the output coupling electrode. It is connected to the output coupling electrode 40b by a fifth through conductor 55 penetrating through the dielectric layer 11 located between the output coupling electrode 40b and 40b. As a result, the auxiliary output coupling electrode 41b and the auxiliary resonant electrode 31d are broadside coupled, and this coupling is added to the coupling between the output coupling electrode 40b and the resonant electrode 30d of the output stage, so that the coupling is stronger as a whole. It becomes.

  As described above, the joint of the input stage resonance electrode 30a and the auxiliary resonance electrode 31a connected thereto, and the input coupling electrode 40a and the joint of the auxiliary input coupling electrode 41a connected thereto are broad-side coupled. In addition, the coupling is very strong by coupling to the interdigital type, and similarly, a joined body of the resonance electrode 30d of the output stage and the auxiliary resonance electrode 31d connected thereto, the output coupling electrode 40b and the auxiliary connected thereto Since the joint of the output coupling electrode 41b is broad-side coupled as a whole and is very strongly coupled by interdigital coupling, the resonance frequency of each resonance mode can be achieved even in a very wide pass band. The insertion loss increase at frequencies located between is further reduced, and the flatter and lower loss pass characteristics across the wide passband. Can be obtained.

  Note that the widths of the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b are set to be approximately the same as the input coupling electrode 40a and the output coupling electrode 40b, for example, and the lengths of the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b are For example, it is set slightly longer than the length of the auxiliary resonance electrodes 31a and 31d. The smaller distances between the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b and the auxiliary resonance electrodes 31a and 31d are desirable in terms of causing strong coupling, but are difficult to manufacture. For example, 0.01 to 0.5 mm Set to degree.

(Fifth example of embodiment)
FIG. 6 is an exploded perspective view schematically showing still another example of the embodiment of the bandpass filter of the present invention. The structural difference from the embodiment shown in FIG. 5 is that a band-like input coupled resonant electrode 34a that is electromagnetically coupled to the input coupled electrode 40a, which functions as a quarter wavelength resonator with one end connected to the ground potential and an output. The band-shaped output coupling resonance electrode 34b electromagnetically coupled to the coupling electrode 40b is located outside the arrangement region from the input stage resonance electrode 30a to the output stage resonance electrode 30d when viewed from above, and the input coupling electrode 40a and This is that the output coupling electrode 40b is disposed between the upper layers than the layer where the output coupling electrodes 40b are disposed.

  According to this structure, since the input coupling resonance electrode 34a and the output coupling resonance electrode 34b function as a reaction resonator, it is possible to form an attenuation pole separate from the attenuation pole formed by the second resonance electrode, By adjusting the lengths of the input coupling resonance electrode 34a and the output coupling resonance electrode 34b, the attenuation pole on the higher frequency side than the pass band is increased without changing the size of the pass band, and more sharply from the pass band to the stop band. It is possible to obtain a pass characteristic in which the amount of attenuation changes.

  Here, the input coupling resonance electrode 34a is coupled to the input coupling electrode 40a, and the output coupling resonance electrode 34b is coupled to the output coupling electrode 40b. If the input coupling resonance electrode 34a enters the inside of the arrangement region from the resonance electrode 30a at the input stage to the resonance electrode 30d at the output stage, the coupling between the input coupling resonance electrode 34a and the input coupling electrode 40a becomes excessively strong, There is a case where the coupling between the coupling electrode 40a and the resonance electrode 30a at the input stage becomes weak, and a problem that the characteristics of the band-pass filter are destroyed may occur. Further, there may be a problem that the characteristics of the bandpass filter are lost due to the coupling of the input coupled resonant electrode 34a with the first resonant electrode 30b and the like. On the other hand, when the input coupling resonance electrode 34a is positioned at the same level or lower side of the layer where the input coupling electrode 40a is disposed, there is a problem that the characteristics of the bandpass filter are destroyed due to coupling with the resonance electrode 30a of the input stage. May occur. The same applies to the output coupling resonance electrode 34b.

  In this embodiment, the input coupling resonance electrode 34a and the output coupling resonance electrode 34b are provided to facilitate the design as a filter having a symmetric structure between the input and output, but either one is arranged. It may be a configuration.

(Sixth example of embodiment)
FIG. 7 is a block diagram showing a configuration example of a high-frequency module 80 using the band-pass filter of the present invention and a radio communication device 85 using the same.

  The high-frequency module 80 of the present invention includes a MAC (Medium Access Control) IC 81 that performs medium access control, and a PHY (physical layer) IC 82 that transmits and receives a multi-band OFDM (Orthogonal Frequency Division Multiplexing) signal, The wireless communication device 85 of the present invention is configured by connecting the antenna 84 to the band pass filter 83. When the transmission signal output from the PHY IC 82 passes through the band-pass filter 83, the signal having a frequency other than the communication band is attenuated and transmitted from the antenna 84. Further, when the received signal received by the antenna 84 passes through the band pass filter 83, a signal of a frequency other than the communication band is attenuated and input to the PHY IC.

  According to the high-frequency module 80 and the radio communication device 85 of the present invention, the bandpass filter of the present invention with a small loss of a signal passing over the entire communication band is used for filtering the transmission signal and the reception signal. Since the attenuation of the reception signal and the transmission signal passing through the filter is reduced, the reception sensitivity is improved, and the amplification degree of the transmission signal and the reception signal can be reduced, so that the power consumption in the amplifier circuit is reduced. Therefore, a high-performance high-frequency module 80 and a wireless communication device 85 with high reception sensitivity and low power consumption can be obtained.

In the band-pass filter of the present invention, as the material of the dielectric layer 11, for example, a resin such as an epoxy resin or a ceramic such as a dielectric ceramic can be used. For example, a dielectric ceramic material such as BaTiO ₃ , Pb ₄ Fe ₂ Nb ₂ O ₁₂ , or TiO ₂ and a glass material such as B ₂ O ₃ , SiO ₂ , Al ₂ O ₃ , or ZnO, and 800 to 1200 ° C. Glass-ceramic materials that can be fired at relatively low temperatures are preferably used. Further, the thickness of the dielectric layer 11 is set to about 0.05 to 0.1 mm, for example.

  Examples of the materials for the various electrodes and through conductors described above include conductive materials mainly composed of Ag alloys such as Ag, Ag-Pd, and Ag-Pt, Cu-based, W-based, Mo-based, and Pd-based conductive materials. Are preferably used. The thicknesses of the various electrodes are set to 0.001 to 0.05 mm, for example.

  The bandpass filter of the present invention can be manufactured, for example, as follows. First, an appropriate organic solvent or the like is added to and mixed with the ceramic raw material powder to form a slurry, and a ceramic green sheet is formed by a doctor blade method. Next, a through hole to be a through conductor is formed in the obtained ceramic green sheet using a punching machine or the like, and a through conductor is formed by filling a conductor paste such as Ag, Ag-Pd, Au, Cu or the like. Next, the various electrodes described above are formed on the ceramic green sheet using a printing method. Next, these are laminated, pressure-bonded using a hot press device, and fired at 800 to 1050 ° C.

(Modification)
The present invention is not limited to the first to sixth examples of the embodiment described above, and various modifications and improvements can be made without departing from the gist of the present invention.

  In the example of the embodiment described above, an example in which the input terminal electrode 60a and the output terminal electrode 60b are provided is shown. However, when a band-pass filter is formed in one region in the module substrate, the input terminal electrode 60a and The output terminal electrode 60b is not always necessary.

  In the example of the embodiment described above, an example in which the input coupling electrode 40a, the output coupling electrode 40b, and the auxiliary resonance electrodes 31a, 31b, 31c, and 31d are arranged between the same layers of the stacked body is shown. The coupling electrode 40a, the output coupling electrode 40b, and the auxiliary resonance electrodes 31a, 31b, 31c, 31d may be arranged between different layers, and the input coupling electrode 40a and the output coupling electrode 40b are arranged between different layers. Alternatively, the auxiliary resonance electrodes 31a, 31b, 31c, and 31d may be arranged between different layers.

  Further, in the example of the embodiment described above, the example in which the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b are arranged between the same layers of the stacked body is shown, but they may be arranged between different layers. Absent.

  Furthermore, in the example of the above-described embodiment, the example in which the first ground electrode 21 is disposed on the lower surface of the multilayer body and the second ground electrode 22 is disposed on the upper surface of the multilayer body. The dielectric layer 11 may be further disposed under the first ground electrode 21, or the dielectric layer 11 may be further disposed over the second ground electrode 22.

  Furthermore, in the example of the above-described embodiment, an example of the high-frequency module 80 configured by the MAC IC 81 that performs medium access control, the PHY IC 82 connected thereto, and the bandpass filter 83 connected thereto. Although shown, a one-chip IC in which the MAC IC 81 and the PHY IC 82 are integrated may be used. Further, for example, the radio communication device 85 may be configured by configuring a high-frequency module only by the PHY IC 82 and the band pass filter 83 connected thereto, and connecting the MAC IC 81 and the antenna 84 thereto.

  Furthermore, although the band pass filter used for UWB has been described above as an example, it goes without saying that the band pass filter of the present invention is effective in other applications that require a wide band.

The transmission characteristics of the bandpass filter having the structure of FIG. 5 were calculated by electromagnetic field simulation. The calculation conditions were such that the dielectric constant of the dielectric layer 11 was 9.4, the dielectric loss tangent was 0.0005, and the conductivity of the conductor forming the various electrodes was 3.0 × 10 ⁷ S / m. As the shape dimensions, the thickness of the dielectric layer 11 was set such that the uppermost layer and the lowermost layer of the seven layers had a thickness of 0.3 mm, and the other layers had a thickness of 0.075 mm. The first resonance electrodes 30a, 30b, 30c, and 30d have a width of 0.4 mm and a length of 2.85 mm, and the first resonance electrode (input stage resonance electrode) 30a, the first resonance electrode 30b, and the first resonance. The distance between the electrode 30c and the first resonance electrode (output stage resonance electrode) 30d was 0.15 mm, and the distance between the first resonance electrode 30b and the first resonance electrode 30c was 0.14 mm. The input coupling electrode 40a and the output coupling electrode 40b have a width of 0.3 mm and a length of 2.5 mm, and the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b have a width of 0.3 mm and a length of 1.45 mm. The auxiliary resonance electrodes 31a, 31b, 31c, 31d are a rectangle having a width of 0.45 mm and a length of 0.8 mm arranged 0.3 mm away from the other end of the first resonance electrodes 30a, 30b, 30c, 30d, and the first A rectangular shape having a width of 0.2 mm and a length of 0.4 mm toward one resonance electrode 30a, 30b, 30c was joined. The input terminal electrode 60a and the output terminal electrode 60b were square with sides of 0.3 mm, and the distance from the second ground electrode 22 was 0.2 mm. The outer shape of the first earth electrode 21, the second earth electrode 22, and the annular earth electrode 23 was 3 mm wide and 5 mm long, and the opening of the annular earth electrode 23 was 2.4 mm wide and 3 mm long. The overall shape of the bandpass filter was 3 mm wide, 5 mm long, and 0.975 mm thick. The distance between the layer where the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b are arranged and the layer where the upper auxiliary resonance electrodes 31a, 31b, 31c and 31d are arranged is 0.065 mm. The thicknesses of the various electrodes were 0.013 mm, and the diameters of the various through conductors were 0.1 mm. In the resonant electrode coupling conductor for forming the attenuation pole, the width of the front-side coupling region 321 and the rear-side coupling region 322 is 0.3 mm, and the width of the connection region 323 is 0.1 mm.

  The second resonance electrodes 33a and 33b operated as the reaction resonator have a wide region (width is set so as to protrude toward the one side surface at the other end of the strip region having a width of 0.1 mm and a length of 3.4 mm. 0.4 mm, length 0.36 mm). The position where the second resonance electrode 33a is provided is opposed so that the edge of the first resonance electrode 30b on the input stage resonance electrode 30a side and the edge of the second resonance electrode 33a coincide with each other when viewed from above. Using the position as a reference, the position was shifted by 0.03 mm so as to approach the resonance electrode 30a of the input stage. Similarly, the position where the second resonance electrode 33b is provided is opposed so that the edge of the first resonance electrode 30c on the output stage resonance electrode 30d side and the edge of the second resonance electrode 33b coincide with each other when viewed from above. Using the position as a reference, the position was shifted by 0.03 mm so as to approach the resonance electrode 30d of the output stage.

  FIG. 8 is a graph showing the calculation results, in which the horizontal axis represents frequency and the vertical axis represents loss, and shows transmission characteristics (S21) and reflection characteristics (S11). According to the results shown in FIG. 8, the pass characteristic (S21) has a low loss characteristic in a very wide frequency range exceeding 30% in the specific band, and is attenuated to 2.5 GHz outside the pass band. And one attenuation pole are formed at 5.3 GHz. Further, jumping between attenuation poles on the high frequency side from the pass band is also suppressed. In this way, an excellent pass characteristic is obtained that is flat and low-loss over the entire wide passband and that is sufficiently attenuated outside the passband, confirming the effectiveness of the present invention. It was.

  On the other hand, a simulation was also performed for a structure having the same structure as this, except that only the positions of the second resonance electrodes 33a and 33b were changed. This is based on the position where the edge of the first resonance electrode 30b facing the input stage resonance electrode 30a and the edge of the second resonance electrode 33a face each other so as to coincide with each other. The position was shifted 0.03 mm away from the electrode 30a. Similarly, the position where the second resonance electrode 33b is provided is opposed so that the edge of the first resonance electrode 30c on the output stage resonance electrode 30d side and the edge of the second resonance electrode 33b coincide with each other when viewed from above. The position was shifted 0.03 mm away from the resonance electrode 30d of the output stage with reference to the position.

  FIG. 9 is a graph showing the calculation results, where the horizontal axis represents frequency and the vertical axis represents loss, and shows the transmission characteristic (S21) and the reflection characteristic (S11). According to the graph shown in FIG. 9, in the pass characteristic (S21), one attenuation pole is formed at 2.5 GHz and two attenuation poles are formed at 5.3 GHz outside the pass band, and the characteristic shown in FIG. As in Fig. 8, a steep attenuation characteristic is obtained in the vicinity of the cutoff frequency, but a jump is observed in the vicinity of the high-frequency side of the first attenuation pole on the high-frequency side from the pass band, which is compared with the characteristic shown in FIG. And it turns out that it is a little inferior. Therefore, in order to eliminate this jumping, the positions of the second resonance electrodes 33a and 33b are adjusted to couple the second resonance electrodes 33a and 33b to the first resonance electrodes 30a, 30b, 30c and 30d. It turns out that the amount needs to be adjusted.

  In FIG. 10, parameters such as dimensions relating to the basic structure are the same as those in the above-described embodiment. In addition, the input coupling resonance electrode 34a is higher than the input coupling electrode 40a and the first resonance electrodes 30a and 30b. , 30c and 30d, and the output coupling resonance electrode 34b is higher than the output coupling electrode 40b and outside the arrangement region of the first resonance electrodes 30a, 30b, 30c and 30d. It is the calculation result of the transmission characteristic S21 which simulated the structure of the arrange | positioned FIG. A new attenuation pole is generated in the vicinity of 5 GHz, and a steeper filter characteristic can be obtained.

Note that the transmission characteristics of the structure in which the second resonance electrode is removed from the structure of FIG. 5 were also calculated by electromagnetic field simulation. The calculation conditions were such that the dielectric constant of the dielectric layer 11 was 9.4, the dielectric loss tangent was 0.0005, and the conductivity of the conductor forming the various electrodes was 3.0 × 10 ⁷ S / m. As the shape dimensions, the thickness of the dielectric layer 11 was set such that the uppermost layer and the lowermost layer among the six layers had a thickness of 0.3 mm, and the other layers had a thickness of 0.075 mm. The first resonance electrodes 30a, 30b, 30c, and 30d have a width of 0.4 mm and a length of 2.85 mm, and the first resonance electrode (input stage resonance electrode) 30a, the first resonance electrode 30b, and the first resonance electrode 30c. The distance between the first resonance electrode 30d and the first resonance electrode 30d is 0.15 mm, and the distance between the first resonance electrode 30b and the first resonance electrode 30c is 0.15 mm. The input coupling electrode 40a and the output coupling electrode 40b have a width of 0.3 mm and a length of 2.5 mm, and the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b have a width of 0.3 mm and a length of 1.45 mm. The auxiliary resonance electrodes 31a, 31b, 31c, 31d are a rectangle having a width of 0.45 mm and a length of 0.8 mm arranged 0.3 mm away from the other end of the first resonance electrodes 30a, 30b, 30c, 30d, and the first A rectangular shape having a width of 0.2 mm and a length of 0.4 mm toward one resonance electrode 30a, 30b, 30c, or 31d was joined. The input terminal electrode 60a and the output terminal electrode 60b were square with sides of 0.3 mm, and the distance from the second ground electrode 22 was 0.2 mm. The outer shape of the first earth electrode 21, the second earth electrode 22, and the annular earth electrode 23 was 4 mm wide and 6 mm long, and the opening of the annular earth electrode 23 was 2.4 mm wide and 3 mm long. The overall shape of the bandpass filter was 3 mm wide, 5 mm long, and 0.9 mm thick. The distance between the layer where the auxiliary input coupling electrode 41a and the auxiliary output coupling electrode 41b are arranged and the layer where the upper auxiliary resonance electrodes 31a, 31b, 31c and 31d are arranged is 0.065 mm. The thicknesses of the various electrodes were 0.013 mm, and the diameters of the various through conductors were 0.1 mm. In the resonance electrode coupling conductor 32 for forming the attenuation pole, the width of the front-side coupling region 321 and the rear-side coupling region 322 is 0.2 mm, and the width of the connection region 323 is 0.1 mm.

  FIG. 11 is a graph showing the calculation results, in which the horizontal axis represents frequency and the vertical axis represents loss, and shows transmission characteristics (S21) and reflection characteristics (S11). According to FIG. 11, in the pass characteristic (S21), the characteristic is low loss in a very wide frequency range exceeding 30% in the specific band, and one attenuation pole is provided at 2.5 GHz outside the pass band. One attenuation pole is formed at 5.3 GHz. In this way, an excellent pass characteristic is obtained that is flat and low-loss over the entire wide passband, and that sufficient attenuation is ensured outside the passband. It can be seen that a characteristic in which the attenuation changes rapidly from the high frequency side of the band to the stop band is not obtained. Thereby, the effectiveness of the band pass filter of the present invention having the second resonance electrode was confirmed.

It is a typical exploded perspective view showing an example of an embodiment of a band pass filter of the present invention. (A) is a schematic perspective view of the resonant electrode coupling conductor and the first resonant electrode shown in FIG. 1 as viewed from above, and (b) is a front-side coupling region of the resonant electrode coupled conductor shown in FIG. It is the schematic explanatory drawing seen from the side which shows typically the positional relationship of a back | latter stage side coupling | bonding area | region, a 1st resonance electrode, an input coupling electrode, and an output coupling electrode. It is a disassembled perspective view which shows typically the other example of embodiment of the band pass filter of this invention. It is a disassembled perspective view which shows typically the further another example of embodiment of the band pass filter of this invention. It is a disassembled perspective view which shows typically the further another example of embodiment of the band pass filter of this invention. It is a disassembled perspective view which shows typically the further another example of embodiment of the band pass filter of this invention. It is a block diagram which shows the structural example of the high frequency module using the band pass filter of this invention, and a radio | wireless communication apparatus using the same. It is a figure which shows the simulation result of the transmission characteristic of an example of the band pass filter of this invention shown in FIG. It is a figure which shows the simulation result of the transmission characteristic of the other example of the band pass filter of this invention shown in FIG. It is a figure which shows the simulation result of the transmission characteristic of the other example of the band pass filter of this invention shown in FIG. It is a figure which shows the simulation result of the transmission characteristic at the time of removing the 2nd resonant electrode from the band pass filter shown in FIG.

Explanation of symbols

11: Dielectric layer
21: First ground electrode
22: Second ground electrode
23: Ring earth electrode
30a, 30b, 30c, 30d, 30e, 30f: first resonance electrode
31a, 31b, 31c, 31d: auxiliary resonance electrodes
32: Resonant electrode coupling conductor
321: Front side coupling area
322: Back side coupling area
33a, 33b, 33c, 33d: second resonance electrodes
34a: Input coupled resonant electrode
34b: Output coupled resonant electrode
40a: Input coupling electrode
40b: Output coupling electrode
41a: Auxiliary input coupling electrode
41b: Auxiliary output coupling electrode
50: Through conductor
51: First through conductor
52: Second through conductor
53: Third through conductor
54: Fourth through conductor
55: Fifth through conductor
80: High-frequency module
85: Wireless communication equipment

Claims (11)

A laminate in which a plurality of dielectric layers are laminated;
A first ground electrode disposed on the lower surface of the laminate and connected to a ground potential;
A second ground electrode disposed on the top surface of the laminate and connected to a ground potential;
Four or more first band-shaped resonators arranged side by side so as to be electromagnetically coupled to each other in one layer of the laminate, each having one end connected to a ground potential and functioning as a quarter-wave resonator. A resonant electrode;
The band-like input coupling electrode and the output stage resonance that are electromagnetically coupled to the resonance electrode of the input stage among the four or more first resonance electrodes disposed between the layers above the one layer of the laminate. A strip-shaped output coupling electrode that electromagnetically couples to the electrode;
A resonance electrode group is provided which is arranged between the layers below the one layer of the multilayer body and includes one or more even number of the first resonance electrodes adjacent to each other via the first through conductor. Connected to the ground potential near the one end of the foremost resonance electrode, and the other end is grounded near the one end of the last resonance electrode constituting the resonance electrode group via the first through conductor. Resonant electrode coupling that is connected to a potential and has a region facing each resonance electrode so as to be electromagnetically coupled to the foremost resonance electrode of the resonance electrode group and the last resonance electrode of the resonance electrode group Conductors,
The multilayer body is disposed below the one interlayer and in a layer different from the layer where the resonant electrode coupling conductor is disposed, and is disposed in parallel to the first resonant electrode, and one end thereof is a second through conductor. One or more second resonance electrodes that are connected to the ground potential via the first electrode and are formed in a strip shape having a length different from that of the first resonance electrode and have a resonance frequency near the cutoff frequency outside the passband A bandpass filter comprising:
The four or more first resonance electrodes have the one end and the other end arranged alternately.
The input coupling electrode is disposed so as to face a region extending over half the length direction of the resonance electrode of the input stage, and a position to which an electric signal input from an external circuit is supplied is the center in the length direction. Is closer to the other end of the resonance electrode of the input stage than
The output coupling electrode is disposed so as to face a region extending over half the length direction of the resonance electrode of the output stage, and the position from which the electric signal output to the external circuit is taken out from the center in the length direction. The band-pass filter is characterized in that it is on the side closer to the other end of the resonance electrode of the output stage.   The resonance electrode coupling conductor includes a front-side coupling region facing the front-stage resonance electrode of the resonance electrode group, a rear-side coupling region facing the last-stage resonance electrode of the resonance electrode group, and the front-side side The band-pass filter according to claim 1, wherein the band-pass filter includes a coupling region and a connection region that connects the second-stage coupling region orthogonally to these regions. The front-side coupling region is opposed to the input coupling electrode via the coupling electrode of the input stage, and the rear-side coupling region is opposed to the output coupling electrode via the resonance electrode of the output stage;
The front-side coupling region has a strip shape, and a central axis extending in the length direction of the front-side coupling region as viewed from above is arranged so as not to overlap a central axis extending in the length direction of the input coupling electrode,
The rear-side coupling region has a strip shape, and a central axis extending in the length direction of the rear-side coupling region as viewed from above is disposed so as not to overlap a central axis extending in the length direction of the output coupling electrode. The bandpass filter according to claim 2.   The front-side coupling region is disposed so as not to overlap with the central axis extending in the length direction of the input coupling electrode when viewed from above, and the rear-side coupling region is the length of the output coupling electrode when viewed from above. The band-pass filter according to claim 3, wherein the band-pass filter is disposed so as not to overlap a central axis extending in a direction.   An even number of the first resonance electrodes and an even number of the second resonance electrodes are provided, and these second resonance electrodes are seen from above, one end of the resonance electrode of the input stage and the resonance of the output stage. A line segment connecting one end of the electrode and a line segment connecting the other end of the resonance electrode of the input stage and the other end of the resonance electrode of the output stage are arranged point-symmetrically around the intersection. The band pass filter according to any one of claims 1 to 4.   An annular ground electrode that is formed in an annular shape surrounding the four or more first resonance electrodes and is connected to the ground potential and connected to the one end of the first resonance electrode is disposed between the one layer. The bandpass filter according to claim 1, wherein the bandpass filter is provided.   The first and second resonance electrodes are disposed so as to have a region facing the annular ground electrode and a region facing the first resonance electrode between layers different from the one layer, and the region facing the first resonance electrode is the first layer. The auxiliary resonance electrode connected to the other end side of the first resonance electrode by a third through conductor penetrating the dielectric layer located between the first resonance electrode and the resonance electrode is the four or more first resonance electrodes. The band-pass filter according to claim 6, wherein the band-pass filter is disposed corresponding to each of the resonance electrodes. Of the four or more auxiliary resonance electrodes between the one layer and the layer where the auxiliary resonance electrode is disposed, a region facing the auxiliary resonance electrode connected to the resonance electrode of the input stage and the input coupling And a region facing the input coupling electrode, and a region facing the input coupling electrode is disposed between the input coupling electrode and a fourth through conductor penetrating the dielectric layer. An auxiliary input coupling electrode connected to the side closer to the other end of the resonance electrode of the input stage than the center in the length direction;
A region facing the auxiliary resonance electrode connected to the resonance electrode of the output stage among four or more auxiliary resonance electrodes between the one layer and a layer different from the layer where the auxiliary resonance electrode is disposed, and the output coupling electrode A region opposite to the output coupling electrode, and a region facing the output coupling electrode is extended by a fifth through conductor penetrating the dielectric layer located between the output coupling electrode and the length of the output coupling electrode. The band-pass filter according to claim 7, further comprising: an auxiliary output coupling electrode connected to a side closer to the other end of the resonance electrode of the output stage than a center in the vertical direction.   A band-shaped input coupling resonance electrode that electromagnetically couples with the input coupling electrode and a band-shaped output coupling resonance electrode that electromagnetically couples with the output coupling electrode, one end of which is connected to the ground potential and functions as a quarter wavelength resonator At least one of them is located outside the region where the input stage resonance electrode and the output stage resonance electrode are arranged, and above the layer where the input coupling electrode and the output coupling electrode are arranged. The band pass filter according to claim 1, wherein the band pass filter is disposed between the layers.   A high-frequency module comprising the bandpass filter according to any one of claims 1 to 9.   A wireless communication device using the bandpass filter according to any one of claims 1 to 9 or the high-frequency module according to claim 10.

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