EP3363111A1

EP3363111A1 - Insulated dc/dc converter

Info

Publication number: EP3363111A1
Application number: EP16781456.5A
Authority: EP
Inventors: Luis De Sousa
Original assignee: Valeo Systemes de Controle Moteur SAS
Current assignee: Valeo eAutomotive France SAS
Priority date: 2015-10-16
Filing date: 2016-10-13
Publication date: 2018-08-22
Also published as: FR3042661A1; US20180309376A1; CN108475991A; JP2018530985A; US10193463B2; WO2017064220A1; FR3042661B1; CN108475991B

Abstract

The invention relates to an insulated DC/DC converter (1) including an insulated circuit (3) having: a first arm (A) comprising a first switch (MA1) that is in series with a second switch (MA2); a magnetic component (100) comprising two primary circuits (101, 101') and one secondary circuit (102) that are separated by at least one electrical insulation barrier, said magnetic component (100) being configured such that, during the conversion of an input voltage of the insulated DC/DC converter into an output voltage (Vo), it operates as a transformer from the primary circuits (101, 101') towards the secondary circuit (102) and as an impedance which stores energy in the primary circuits (101, 101'), and wherein: the first arm (A) includes a first capacitor (C1) in series with the two switches (MA1, MA2) and located between the two switches (MA1, MA2); one of said primary circuits, referred to as the second primary circuit (101'), is connected between a first end terminal of the first arm (A) and the connection point, referred to as the second connection point (P2), between the second switch (MA2) of the first arm (A) and the first capacitor (C1), the first end terminal of the first arm (A) corresponding to the terminal of the first switch (MA1) that is not connected to the first capacitor (C1); and the other primary circuit, referred to as the first primary circuit (101), is connected between a second end terminal of the first arm (A) and the connection point, referred to as the first connection point (P1), between the first switch (MA1) and the first capacitor (C1), the second end terminal of the first arm (A) corresponding to the terminal of the second switch (MA2) that is not connected to the first capacitor (C1).

Description

DC / DC ISOLATED CONVERTER

The present invention relates to an isolated DC / DC converter, as well as a voltage conversion method implemented with the converter according to the invention.

In the context of the present application, high voltage means a voltage greater than 60V, for example of the order of 100 V or a few hundred volts; low voltage means a voltage below 60V, for example of the order of 12V or a few tens of volts.

Isolated direct current / direct current (DC / DC) converters may have zero-voltage switching or ZVS (zero-voltage switching) or zero-current or ZCS switching (for zero current switching ") that reduce switching losses during voltage conversion. These converters are therefore particularly advantageous in an automotive application where the energy resource is limited. In a vehicle, a voltage converter can be used to adapt voltage levels between several electrical networks of the vehicle or to convert a voltage between a power source and an electrical consumer embedded in the vehicle.

There is known a DC / DC converter isolated from the patent US5754413, illustrated in Figure 1. The converter comprises two switches Q1, Q2 which are connected at their midpoint to a branch which comprises two transformers T, T 'in series. The converter is arranged in a half-bridge. The switches control the transmission of energy through the transformers to convert the input voltage of the converter to an output voltage. Diodes connected to the secondary of the transformers make it possible to straighten the output signal. The output voltage is obtained by controlling the duty cycle of the switches. By changing the duty cycle to reach an output voltage target value, the gain of the converter is adjusted to reach the output voltage target value.

The converter comprises a capacitor C in series with the two transformers T, T '. The capacitor C makes it possible to eliminate the DC component of the current received by the two transformers T, T '. In this circuit topology, the capacitor C is traversed by the current flowing in the transistors T, T '. However, in some high voltage applications, in particular applications in a motor vehicle, the current flowing in the transformers is high, of the order of, for example, 20 A. For example, in a 3kW power converter that converts between 400 and 12V, the capacity has the following characteristics 10μΕ / 300ν / 20Α rms. These characteristics make the capacity bulky, which has an impact on the integration of the converter in the vehicle.

It is therefore sought a solution to improve the performance of an isolated DC / DC converter so as to allow its use in a motor vehicle. In order to solve this problem, the invention relates to an isolated DC / DC converter comprising an isolated circuit having:

a first arm comprising a first switch, in series with a second switch;

a magnetic component comprising two primary circuits and a secondary circuit separated by at least one electrical insulation barrier, said magnetic component being configured for, when converting an input voltage of the isolated DC / DC converter into a voltage output, operate as a transformer from the primary circuits to the secondary circuit and as an impedance that stores energy at the primary circuits,

and wherein:

the first arm comprises a first capacitance in series with the two switches and situated between the two switches,

one of said primary circuits, said second primary circuit, is connected between a first extremal terminal of the first arm and the connection point, said second connection point, between the second switch of the first arm and the first capacitor, the first extreme terminal of the first arm corresponding to the terminal of the first switch which is not connected to the first capacitor; and

the other primary circuit, said first primary circuit, is connected between a second extremal terminal of the first arm and the connection point, said first connection point, between the first switch and the first capacitor, the second extremal terminal of the corresponding first arm. to the terminal of the second switch that is not connected to the first capacitor.

In particular, successions of opening and closing of the switches of the first arm make it possible to convert an input voltage into an output voltage via the magnetic component.

In particular, the second extremal terminal is connected to a ground of the isolated DC / DC converter, in particular to a ground on the primary side of the isolated DC / DC converter.

In particular, the output voltage of the isolated DC / DC converter is taken at the terminals of the secondary circuit of the magnetic component.

In the context of the present application, an isolated circuit is understood to mean a circuit comprising at least one electrical insulation barrier between functional elements of the converter.

Due to the configuration of the magnetic component and the first capacitance in the isolated DCDC converter, the current flowing in the first capacitance is lower than in the prior art which makes it possible to reduce the size of the capacitance used. In particular, the current flowing on the primary side in the magnetic component is distributed between the first and the second primary circuit, which decreases the current flowing in the first capacitor with respect to the prior art.

According to one embodiment, the magnetic component is configured so that:

on a first part of a period of operation of the converter, respective first portions of the primary circuits transfer energy to a first portion of the secondary circuit, and respective second portions of the primary circuits provide inductances that store energy;

- On a second part of the operating period of the converter, the respective second portions of the primary circuits transfer energy to a second portion of the secondary circuit, and the respective first portions of the primary circuits perform inductances storing energy.

In particular, the first portions of the primary circuits and the secondary circuit are perfectly coupled together; and the second portions of the primary circuits and the secondary circuit are perfectly coupled together.

In particular, the first arm is controlled by pulse width modulation; the first part of the operating period corresponds to a first part of the modulation period; and the second part of the operating period corresponds to a second part of the modulation period. These first and second parts are in particular determined by the duty ratio of the first arm.

According to one variant, the magnetic component comprises at least a first and a second isolation transformer in series, the transformers each having two primary ones, in which:

the primary of the first transformer respectively form the first parts of the primary circuits and the secondary of the first transformer forms the first part of the secondary circuit;

- The primary of the second transformer respectively form the second parts of the primary circuits and the secondary of the second transformer forms the second part of the secondary circuit.

According to one variant, the primary circuits of the magnetic component respectively comprise a primary winding; and the secondary circuit of the magnetic component comprises at least a first secondary winding and at least a second secondary winding not magnetically coupled to each other, said first and second secondary windings being magnetically coupled to the primary windings.

In particular, the magnetic component is configured to act as a transformer from the primary windings, either to the first secondary winding (s) or to the secondary winding (s); while operating as impedances that store energy at the primary windings.

According to one embodiment, the input of the isolated circuit, in particular of the isolated DC / DC converter, is at the level of the first extremal terminal of the first arm. In particular, an input voltage of the isolated circuit, in particular the isolated DC / DC converter, is delivered between the first and the second extremal terminals.

According to one embodiment, the converter comprises a regulation circuit connected to the first extremal terminal of the first arm and intended to regulate a voltage delivered to the first arm, the control circuit being configured to control the output voltage of the isolated DC / DC converter by modifying the voltage delivered to the first arm, the duty cycle of the first arm remaining substantially constant. In particular, the regulation circuit delivers a voltage to the first arm between said extremal terminals. In particular, the control circuit may be a DC / DC converter, in particular a converter of the Sepic, Cuk, step-down, elevator or step-down type, or others.

Thus, a desired output voltage value at the output of the isolated DC / DC converter can be obtained without changing the duty cycle of the first arm. The duty cycle of the first arm can therefore be set to a value which allows maximum efficiency of the isolated DC / DC converter, in particular the transmission of energy through the magnetic component.

At a given output voltage of the isolated DC / DC converter, the control circuit enables operation of the first arm with a constant duty cycle for any input voltage, in particular within an operating range of the isolated DC / DC converter. . For example, the difference between the minimum value and the maximum value of the input voltage of the isolated DC / DC converter is between 150 and 500V; for example, the minimum value of the input voltage is between 150 and 200 V; and the maximum value of the input voltage is between 400 and 500V, or even between 400 and 650V.

According to a variant, a second capacitor is connected between the first extremal terminal of the first arm and the second extremal terminal of the first arm.

According to one embodiment, the converter comprises:

a second arm comprising a first switch and a second electronic element in series, the free terminal of the second electronic element being connected to the second extremal terminal of the first arm,

an inductance connected between the second connection point and a third connection point, the third connection point corresponding to the terminal of the second electronic element which is on the side of the first switch of the second arm,

a second capacitor connected between the first extremal terminal of the first arm and the second extremal terminal of the first arm,

the second electronic element being a second switch or a diode having its cathode connected to the third connection point,

and wherein successions of opening and closing of the switch or switches of the second arm convert an input voltage to an output voltage through the magnetic component.

In particular, the input of the isolated DC / DC converter is at the extremal terminals of the second arm.

The second arm, as well as the second capacitance and inductance, contribute to the control of the energy transfer through the magnetic component. The duty ratio of the second arm is an additional parameter in the control of the energy transfer through the magnetic component. Thus, an isolated DC / DC converter is obtained in which control can be refined to improve performance, particularly with regard to the transmission of energy via the magnetic component.

A desired output voltage value at the output of the isolated DC / DC converter can be obtained without changing the duty ratio of the first arm. The duty cycle of the first arm can therefore be set to a value which allows maximum efficiency of the isolated DC / DC converter, in particular the transmission of energy through the magnetic component.

At a given output voltage of the isolated DC / DC converter, the second arm allows operation of the first arm with a constant duty cycle for any input voltage, in particular within an operating range of the isolated DC / DC converter. For example, the difference between the minimum value and the maximum value of the input voltage of the isolated DC / DC converter is between 150 and 500V; for example, the minimum value of the input voltage is between 150 and 200 V; and the maximum value of the input voltage is between 400 and 500V, or even between 400 and 650V.

According to a variant, the second arm is configured to control the output voltage of the isolated DC / DC converter by modifying an electrical parameter of a signal traversing the inductor.

Thus, a desired voltage value at the output of the isolated DC / DC converter is obtained by adjusting the electrical parameter of the signal flowing in the inductor. At each desired voltage value at the output of the isolated DC / DC converter corresponds a value of the electrical parameter of the signal flowing in the inductance.

According to one variant, the first arm is configured so that its duty cycle has a nominal value and varies around this nominal value as a function of a difference between a value of the electrical parameter of the signal traversing the inductance and a value of the electrical parameter. of the signal traveling through the magnetic component.

According to a variant, the first arm is configured so that its duty cycle has a nominal value and varies around this nominal value so that the value of the electrical parameter of the signal traversing the inductance and the value of the electrical parameter of the signal traveling through the magnetic component are equal

According to a variant, when the duty cycle of the first arm increases, the value of the electrical parameter of the magnetic component increases. When the duty ratio of the first arm decreases, the value of the electrical parameter of the magnetic component decreases.

According to one variant, the duty ratio of the first arm varies around this nominal value to plus or minus 2% with respect to the nominal value.

According to one variant, the electrical parameter is a mean current. In other words, the electrical parameter of the magnetic component is a mean current flowing through the inductor; and the electrical parameter of the magnetic component a mean current flowing through the magnetic component, in particular, the sum of currents flowing through the primary circuits. The electrical parameter can also be an average voltage. According to one embodiment, the converter further comprises:

a third capacitance in series between the first switch of the second arm and the second electronic element of the second arm, the third capacitor being connected between the third connection point and a fourth connection point corresponding to the terminal of the first switch which is on the the second electronic element of the second arm,

another inductor connected between the first connection point (PI) and the fourth connection point.

According to one embodiment, the duty ratio of the first arm remains substantially constant at a nominal value.

According to one embodiment, the nominal value is equal to 50%.

According to one embodiment, the isolated circuit further comprises at least a third arm comprising a first switch, a second switch, and a fourth capacitor in series with the two switches and located between the two switches; and wherein the magnetic component comprises at least two additional primary circuits separated from each other and with the secondary circuit by at least one electrical insulation barrier,

one of said additional primary circuits, said first additional primary circuit, is connected between a first extremal terminal of the third arm and the connection point between the second switch of the third arm and the fourth capacitance, the first extremal terminal of the corresponding third arm (E). at the terminal of the first switch of the third arm which is not connected to the fourth capacitance; and

the other of said additional primary circuits, said second additional primary circuit, is connected between a second extremal terminal of the third arm and the point of connection between the first switch of the third arm and the fourth capacitance, the second extremal terminal of the third arm (E ) corresponding to the terminal of the second switch of the third arm which is not connected to the fourth capacitor,

the extremal terminals of the first and third arms being respectively connected to each other.

The invention also relates to a voltage conversion method using an isolated DC / DC converter according to the invention, wherein the control of the output voltage of the isolated DC / DC converter comprises the steps of:

modifying an electrical parameter of a signal traversing the inductor by varying the duty ratio of the second arm,

- vary the duty ratio of the first arm around a nominal value according to a difference between a value of the electrical parameter of the signal traveling through the inductor and a value of the electrical parameter of the signal traveling through the magnetic component.

The method according to the invention may comprise one of the characteristics described above in relation to the isolated DC / DC converter according to the invention. The invention will be better understood with reference to the drawings, in which:

FIG. 1 illustrates an example of an isolated DC / DC converter according to the prior art;

FIG. 2 illustrates an example of an isolated DC / DC converter according to a first embodiment;

FIGS. 3 and 4 illustrate states of the converter of FIG. 2 over two parts of an operating period;

FIGS. 5 to 7 illustrate examples of the converter according to a second embodiment;

FIG. 8 illustrates a third embodiment of the converter according to the invention;

FIGS. 9 to 11 show equivalent diagrams of the circuit of FIG. 8 during its operation;

FIG. 12 illustrates a fourth embodiment of the converter according to the invention;

FIG. 13 illustrates a fifth embodiment that is compatible with the other embodiments of the converter according to the invention;

FIG. 14 illustrates a diode that can replace a switch in the converter examples according to the invention.

The converter according to the invention will be better understood by referring to FIG. 2 which presents an example of an isolated DC / DC converter 1 according to a first embodiment.

The isolated DC / DC converter 1 comprises a first arm A of switches in series. The arm A comprises MAI switches, MA2, a succession of openings and closures to control the output of the isolated DC / DC converter 1. In particular, the switch MA2, said second switch or switch side down, is connected to the lower terminal of a voltage source Ve. This lower terminal corresponds in particular to a first ground GND1 of the isolated DC / DC converter 1.

And the other switch MAI, said first switch or switch side up, is connected to the input voltage Ve at an extremal terminal of the first arm A.

Each switch MA1, MA2 may comprise a transistor in parallel with a freewheeling diode and / or a capacitance CA1, CA2. These CA1, CA2 capabilities are used to switch to zero voltage or ZVS (for "Zero Voltage

Switching "in English) when opening switches MAI, MA2. At the opening of a switch MAI, MA2 is used an inductor, including a leakage inductance of a magnetic component 100 described later, to discharge and recharge the capacitance CAl, CA2 which is across the switch. Once the voltage is close to 0V, the switch is commanded, and thus a commutation under zero voltage is performed, which greatly reduces the switching losses. These capacitances CA1, CA2 may be intrinsically present in the semiconductor structure composing the switches MA1, MA2, as elements parasites. The parasitic capacitances of the switches MAI, MA2 may therefore be sufficient to perform the switching to zero voltage without adding additional capacity. The switches MAI, MA2 could dispense with these capabilities CA1, CA2.

A first capacitance C1 is in series with the two switches MAI, MA2 and located between the switches MA1, MA2. Thus, the first capacitance C1 has a first terminal connected to the first switch MAI at a connection point PI, and a second terminal connected to the second switch MA2 at a second connection point P2. In particular, the first capacitance C1 is connected to the first switch MAI at the source electrode of the first switch MAI, and it is connected to the second switch MA2 at the drain electrode of the second switch MA2.

The isolated DC / DC converter 1 further comprises a magnetic component 100 which includes a first primary circuit 101, a second primary circuit 10 and a secondary circuit 102 separated from each other by electrical insulation barriers. In particular, the first primary circuit 101 forms a branch whose one end is connected to the first connection point PI and whose other end is connected to an extremal terminal, called the second extremal terminal, of the first arm A. The second extremal terminal corresponds to the terminal of the second switch MA2 which is not connected to the first capacitor C1. And the second primary circuit 101 'forms a branch whose one end is connected to the second connection point P2 and whose other end is connected to a terminal extremal terminal, said first extremal terminal, of the first arm A. The first extremal terminal corresponds to the terminal of the first switch MAI which is not connected to the first capacitance Cl.

In particular, the first primary circuit 101 has a first inductance LU in series with a second inductance L21. In particular, the positive terminal of the first inductor L1 is connected to the first connection point P1 and the positive terminal of the second inductor L21 is connected to the negative terminal of the first inductor L1. In particular, the second primary circuit 101 'has a first inductance LU' in series with a second inductor L21 '. In particular, the negative terminal of the first inductance LU 'is connected to the first extreme terminal of the arm A and the negative terminal of the second inductor L21' is connected to the positive terminal of the first inductance LU '. In particular, the secondary circuit 102 has a first inductor L12 in series with a second inductor L22. In particular, the positive terminal of the first inductor L12 is connected to a first secondary side switch Q1 and the positive terminal of the second inductor

L22 is connected to the negative terminal of the first inductor L12.

In particular, the first inductances LU, LU 'of the primary circuits 101, 10 and the first inductor L12 of the secondary circuit 102 are perfectly coupled together. Similarly, the second inductances L21, L21 'of the primary circuits 101, 10 and the second inductance L22 of the secondary circuit 102 are perfectly coupled together. However, the first inductances LU, LU ', L12 of the primary circuits 101, 10 and of the secondary circuit 102 are perfectly decoupled from the second inductances L21, L21 ', L22 of the primary circuits 101, 10 and the secondary circuit 102.

The transformation ratio NI between the first inductance LU of the first primary circuit 101 and the first inductor L12 of the secondary circuit 102 is for example equal to the transformation ratio Ν between the first inductance LU 'of the second primary circuit 10Γ and the first inductance L12 of the secondary circuit 102. However, these two ratios of transformations NI, Ν could be of different value. The transformation ratio N2 between the second inductor L21 of the first primary circuit 101 and the second inductor L21 of the secondary circuit 102 is for example equal to the transformation ratio N2 'between the second inductor

L21 'of the second primary circuit 10 and the second inductor L22 of the secondary circuit 102. However, these two transformation ratios N2, N2' could be of different value. In the following, the transformation ratios are equal to N. The case where the transformation ratios are different can be deduced from the example below.

In particular, the secondary circuit 102 is connected to a circuit R realizing a rectification of the signal delivered by the secondary circuit 102 in order to deliver a continuous voltage Vo at the output of the isolated DC / DC converter 1. In particular, a first switch Qi is arranged between a first end of the first inductor L12 of the secondary circuit 102 and a ground GND2 secondary side, and a second switch Q ₂ is disposed between a first end of the second inductor L22 of the secondary circuit 102 and GND2 secondary side mass. The second ends of the first L12 and the second L22 secondary inductances are connected to a connection point P5 delivering the output voltage Vo of the isolated DC / DC converter 1. The switches Q1, Q2 make it possible, for example, to obtain a synchronous rectification. at the output of the magnetic component 100.

The rectification of the signal delivered by the secondary circuit 102 could also be achieved by diodes in a manner known per se. For high-current applications to the secondary circuit 102, the use of the switches Q1, Q2 in place of the diodes makes it possible to improve the overall efficiency of the isolated DC / DC converter 1.

The voltage converter 1 may also include a capacitor Co for filtering the signal delivered by the secondary circuit 102.

During an input voltage conversion Ve through the isolated DC / DC converter 1, the magnetic component 100 functions as a transformer of the primary circuits 101, 10 to the secondary circuit 102, and as an impedance which stores energy. This will be better understood by referring to the operating examples illustrated in FIGS. 3 and 4, in which the instantaneous voltages and currents are represented by arrows.

In particular, the switches MA1, MA2 of the first arm A have a duty cycle which makes it possible to transfer energy through the magnetic component 100.

The switches MAI, MA2 are in particular controlled by a pulse width modulation with a modulation period T. The durations of first and second operating parts are defined by the duty cycle A switches MAI, MA2.

In particular, on a first operating part, that is to say on a first part of the modulation period T, illustrated in FIG. 3, the high side switch MAI is open and the low side switch MA2 is closed. . The first operating part has a duration (I- () T, A is the duty cycle applied to the first switch MAI of the first arm A and T the modulation period.The first switch MAI is open while the second switch MA2 is passing. .

In this phase, a voltage-Ve opposed to the input voltage Ve is applied to the magnetic component 100. The reflected voltage at the secondary circuit 102 is also negative so that the first diode D1 of the first switch Q1 of the rectifier circuit R is conducting. , while the second diode D2 of the second switch Q2 of the rectifier circuit R is blocking. The second portion L22 of the secondary circuit 102 then behaves as an open switch. The voltage across the first portion L12 of the secondary circuit 102 is equal to the opposite -Vo of the output voltage Vo; and therefore the voltage across the first portion LU of the first magnetic circuit is -NxVo and the voltage across the first portion LU 'of the second primary circuit 10 is NxVo. The first portions LU, LU 'of the primary circuits 101, 10 thus allow a transfer of energy to the secondary circuit 102.

The voltage across the second portion L21 of the first primary circuit 101 is equal to - (Ve-NxVo) and the voltage across the second portion L21 'of the second primary circuit 10 is equal to (Ve-NxVo). This energy is stored at the resulting magnetising inductance of the second part of the magnetic component 100.

In steady state on this first part, the first capacitance C1 has a voltage VC1 equal to the input voltage Ve. On average, the voltage VC1 across the first capacitor C1 during this first operating portion is equal to 1. Thus, on the first operating part, a first part of the first primary circuit 101 implemented by the first inductance LU and a first part of the second primary circuit 10 implemented by the second inductance LU 'transfer energy to the secondary circuit 102, in particular to a first portion of the secondary circuit 102 implemented by the first inductor L12 of the secondary circuit 102. A second part of the first primary circuit 101 implemented by the second inductor L21 and a second part of the second primary circuit 10 implemented by the second inductor L21 'store energy.

In particular, on a second operating part, that is to say on a second part of the modulation period T, illustrated in FIG. 4, the high side switch MAI is closed and the low side switch MA2 is open. . The second operating part has a duration aAT, where aA is the duty cycle applied to the first switch MAI of the first arm A and T the modulation period. In this second part, the voltage at the first connection point PI is equal to the input voltage Ve. The voltage applied to the first primary circuits 101, 10 is equal to the input voltage Ve. This voltage is positive so that the reflected voltage at the secondary 102 is also positive, and blocks the first diode Dl of the first switch Ql of the rectifier circuit R. The first portion L12 of the secondary circuit 102 therefore behaves as an open switch. However, since the diode D2 of the second switch Q2 of the rectifying circuit R is conducting, the voltage across the second portion L22 of the secondary circuit 102 is equal to the output voltage Vo. The voltage across the second portion L21 'of the second primary circuit 10 is therefore NxVo and the voltage across the second portion L21' of the first primary circuit 101 is therefore -NxVo. The energy at the terminals of the second portions L21, L21 'of the primary circuits 101, 10 is transferred to the secondary circuit 102.

The voltage across the first part LU of the first primary circuit 101 is equal to Ve-NxVo and the voltage across the first part LU 'of the second primary circuit 10 is equal to - (Ve-NxVo), which allows a energy storage at the resulting magnetising inductance of the first part of the magnetic component 100.

The voltage VC1 across the first capacitor C1 during this second period of operation is CiA Ve average.

Thus, on the second operating part, the second part of the first primary circuit 101 implemented by the second inductor L21 and the second part of the second primary circuit 10 implemented by the second inductor L21 'transfer energy to the secondary circuit 102, in particular to the the second part of the secondary circuit 102 implemented by the second inductor L22 of the secondary circuit 102. The first part of the first primary circuit 101 implemented by the first inductance LU and the first part of the second primary circuit 10 implemented by the second inductance LU 'store energy.

The voltages at the terminals of the first inductances LU, LU ', L12 give the following relation:

{\ - a _A ) xNxV ₀ = a _A x (V _e - NxV ₀ )

The voltages at the terminals of the second inductances L21, L21 ', L22 give the following relation:

a _A xNxV ₀ = {l - a _A ) (V _e - NxV ₀ )

With a cyclic ratio of the first arm A remaining substantially equal to a nominal value (constant, we can obtain a non-zero average current in the magnetic component 100. This may be interesting as will be explained later. To avoid the appearance of an average current in the magnetic component 100, the voltages at the terminals of the first inductances LU, LU ', L12 and at the terminals of the second inductances L21, L21', L22 can be balanced on the two parts of the operating period.

According to a variant of this first embodiment, the duty cycle A has a constant nominal value equal to 50%. This results in a balancing of the first inductances LU, LU 'and L12 and a balancing of the second inductances L21, L21' and L22, which reduces the losses in the isolated DC / DC converter.

Furthermore, at a duty cycle of 50%, the output current of the isolated DC / DC converter 1, more particularly at the output of the magnetic component 100, has ripples which are weak because the currents of the currents in magnetising inductances of the isolated DC / DC converter, in particular those of the magnetic component 100, are compensated.

In particular, the voltage stresses across the diodes D1, D2 of the switches Q1, Q2 of the secondary circuit 102 are a function of the duty cycle A, and are given by the following expressions:

V (D1) = Vo / (l - a _A ) and V (D2) = Vo / a _A

With a duty cycle aA equal to 50%, the voltage stresses across two diodes D1, D2 are equal, the wear is the same between the diodes.

The following table shows a comparison between a DC / DC converter isolated from the prior art such as that in FIG. 1 and the isolated DC / DC converter illustrated in FIG. 2. Taking a transformation ratio N equal to 2 for the transformer of the converter of FIG. 1 and equal to 4 for the converter of FIG. 2, for an input voltage Ve of 200V, an output voltage Vo of 25V with an output current Io, and a duty cycle aA equal to 50%, we have the following characteristics:

Figure 1 Figure 2

Voltage V at V = 200V V = Ve + VCl = 400V

terminals of the ^1st or

^2nd switch

Voltage V at V = a _A xVo = 40V V = a _A xVo = 40V

secondary 102

Voltage at terminals VC '= a _A xVe = 100V VC1 = Ve = 200

C abilities,

Cl

Total current It to ^the j _ o _ o _ ^l _ ^l o ^l o ^f the primary 2N 2N 4 ^f 8 Component

magnetic

Peak current

circulating in the; ^c -! s 4- ^{/ ci "} 16

C, Cl capacity Note that for Figure 2, the total current It to the primary corresponds to the sum of the currents flowing in the first 101 and the second 10 primary circuit.

Thus, in the isolated DC / DC converter of the prior art, the capacitor C in series with the transformers T, T sees a current greater than the first capacitance C1 in the isolated DC / DC converter 1 according to the invention. The current flowing through capacitor C1 in the converter of FIG. 2 is twice as small as the current flowing through capacitor C in the converter of FIG. 1, since the transformation ratio is 4 in the converter of FIG. instead of 2 in the converter of FIG. 1. More generally, the currents flowing in the primary circuits 101, 10 of the magnetic component 100 in the isolated DC / DC converter 1 according to the invention are lower than in the prior art. . In particular, the capacitor C1 of the converter 1 of FIG. 2 only sees the current of a single primary circuit at a time, which divides the current by 4 with respect to the circuit of FIG. 1. The converter 1 according to FIG. The invention thus makes it possible to reduce the losses due to current with respect to the prior art.

According to a second embodiment illustrated in FIGS. 5 to 7, the converter 1 comprises an isolated circuit 3 as represented in FIG. 2 and a circuit 2 for regulating the input voltage U delivered to the circuit 3. The regulation circuit 2 is connected to the first extremal terminal of the first arm A.

The regulation circuit 2 controls the output voltage Vo of the isolated DC / DC converter 1 by modifying the voltage U delivered to the first arm A. Thus, the output voltage Vo of the isolated DC / DC converter 1 can be modified even if the ratio cyclic CIA of the first arm A remains constant and equal to the nominal value ON. Thus, the switches M21, M22, MA1, MA2, circuits 2, 3 have successions of openings and closures which make it possible to control the output signal of the isolated DC / DC converter 1.

In the example illustrated in FIG. 5, the regulation circuit 2 is a step-down DC / DC converter, however it could be of another type of DC / DC converter as illustrated in FIGS. 6 and 7. The regulation circuit 2 comprises in particular two switches M21, M22 in series. In particular, the switch M21, called the high-side switch, is connected to the upper terminal of a voltage source (not shown) delivering an input voltage Ve; and the switch M22, said down-side switch, is connected to the lower terminal of the voltage source. This lower terminal corresponds in particular to the first ground GND1 of the converter 1. Each switch M21,

M22 may include a transistor in parallel with a freewheeling diode.

Each switch M21, M22 may comprise a capacity C21, C22 in parallel. These capabilities C21, C22 are used in particular to make a zero voltage switching or ZVS (for "Zero Voltage Switching" in English) when opening switches. During the opening of a switch M21, M22 recovers the energy stored in an inductor to discharge and recharge the capacitor C21, C22 which is across the switch. Once the voltage is close to 0V The switch is controlled and thus a zero-voltage switching is performed, which greatly reduces switching losses.

In particular, an inductor L2 has a first terminal connected to the midpoint of the two switches M21, M22, and a second terminal connected to the input of the isolated circuit 3.

A second capacitor C2 may be connected between the first extremal terminal of the first arm A and the second extremal terminal of the first arm A. This second capacitor C2 is therefore also connected between the second terminal of the inductor L2 and the first ground GND1 of the converter. This second capacitor C2 makes it possible, for example, to interface circuits 2, 3.

In this embodiment, the switches MA1, MA2 of the first arm A also operate with a cyclic ratio CIA which does not vary, that is to say which remains constant over time and equal to a nominal value ON. During operation of the converter 1, the output voltage Vo of the isolated circuit 3, that is to say the output voltage of the isolated DC / DC converter 1, is controlled by the voltage delivered by the control circuit 2 at the input isolated circuit 3.

For this purpose, the converter 1 may comprise a control unit 5 of the regulation circuit 2. The control unit 5 delivers a signal S2 pulse width modulation or PWM (for "pulse width modulation" in English) which controls the opening and closing of the switches M21, M22 of the regulation circuit 2 to control the electrical signal delivered by the regulation circuit 2. The switches M21, M22 are controlled so that the voltage U delivered at the input of the isolated circuit 3 , that is to say at the output of the regulation circuit 2, makes it possible to obtain a desired voltage value Vo at the output of the isolated DC / DC converter 1. Thus, it is not necessary to vary the duty cycle. CIA of the isolated circuit 3 to achieve a desired output voltage Vo. The isolated circuit 3 can therefore operate at its most advantageous duty cycle, especially at 50%. The control unit 5 may use an I2mes measurement of the current delivered by the control circuit 2 to improve the accuracy of the pulse width modulation signal S2.

In particular, when the input voltage Ve of the voltage converter 1 varies, the control circuit 2 ensures that the input voltage U of the isolated circuit 3 keeps a value which makes it possible to obtain the output voltage Vo. desired. Thus, if the input voltage Ve of the converter 1 changes value, the control unit 5 correspondingly modifies the control of the duty cycles of the switches M21, M22 of the control circuit 2 to maintain the voltage U at the output of the circuit 2. This is particularly advantageous in an electric vehicle where the charge level of a battery can vary over time.

At a duty cycle of 50% in the first arm A, the average current in the magnetic component 100 is zero and allows a decrease of the current ripple at the output of the isolated DC / DC converter as explained previously for the first embodiment. The control unit 5 can furthermore provide protection for the isolated circuit 3. For example, in the event of a short-circuit at the output load of the isolated DCDC converter 1, the control unit 5 can protect the isolated circuit. 3 by acting on the controls S2 of the control circuit 2 so as to cancel the voltage U at the input of the isolated circuit 3 in order to protect it.

The converter 1 can be designed to cover a range of operation. The operating range corresponds to an input voltage Ve of the converter 1 between a minimum value Ve _m in and a maximum value Ve _ma x; and at an output voltage Vo between a minimum value Vo _m in and a maximum value Vomax. For example, the input voltage Ve is between 170 and 450V; and the target voltage Vo at the output of the isolated circuit 1 is between 12 and 16V. For example, the minimum value Vo _m in of the output voltage is between 8 and 14V and the maximum value Vo _ma x of the output voltage is between 15 and 16V.

In the example of FIG. 5, the regulation circuit 2 is a step-down DC / DC converter. The converter 1, in particular the regulation circuit 2, is then configured to be able to deliver the maximum output voltage Vo _ma x with the minimum voltage Ve _m in. The examples of converters illustrated in FIGS. 6 and 7 are similar to the example of FIG. 5 but differ in regulation circuit 2. FIG. 6 illustrates an example of converter 1 in which the regulation circuit 2 is a known boosting circuit in itself. The converter 1, in particular the regulation circuit 2, is then configured to be able to deliver the minimum output voltage Vomin with the maximum input voltage Ve _ma x. FIG. 7 illustrates another example of a converter in which the regulation circuit 2 is a step-up SEPIC circuit known per se. In this example, the regulation circuit 2 can lower or raise the voltage, which facilitates the use of the regulation circuit 2.

According to a third embodiment illustrated in FIG. 8, the isolated DC / DC converter 1 comprises a second arm B of switches in series. The second arm B comprises two switches MB1, MB2 which are directly in series. A first switch MBl, said switch high side, is connected to the upper terminal of a voltage source (not shown) delivering an input voltage Ve. A second switch MB2, called low side switch, is connected to the second extremal terminal of the first arm A. The second switch MB2 is further connected to the lower terminal of the voltage source. This lower terminal therefore corresponds to the first ground GND1 of the isolated DC / DC converter 1. Each switch MB1, MB2 may comprise a transistor in parallel with a freewheeling diode.

A third inductor L3 has a first terminal connected to the midpoint of the second arm B, and a second terminal connected to the second connection point P2. A second capacitor C2 is connected between the extremal terminals of the first arm A. The second arm B could also include capacities for a smooth switching of its switches MB1, MB2. However, this would impose current ripples in the third inductance L3 likely to cause losses. As a result, the advantage of gentle switching of switches MB1, MB2 of second arm B could be lost. A succession of openings and closings of the switches MAI, MA2, MB1, MB2 of the first A and the second B arm make it possible to control the output of the isolated DC / DC converter 1. In the example illustrated in FIG. energy through the magnetic component 100 is controlled by the switches MA1, MA2 of the first arm A. In the isolated DC / DC converter 1 according to this embodiment, the second arm B also controls this energy transmission. Indeed, in the example illustrated in FIG. 2, the voltage between the extremal terminals of the first arm A is equal to the input voltage Ve of the isolated DC / DC converter 1. While in the isolated DC / DC converter 1 illustrated in FIG. 8, the voltage U at the terminals of the first arm A, that is to say at the terminals of the second capacitor C2, is given by the expression:

_{U =} ^ _{xVe ^}

Where A is the duty ratio of the first arm A and (is the duty ratio of the second arm B.

Thus, in the isolated DC / DC converter 1 illustrated in FIG. 8, the duty ratio (of the second arm B constitutes, with respect to the example illustrated in FIG. 2, an additional parameter in the control of the transfer of energy through the magnetic component 100. The control of the isolated DC / DC converter 1 is thus refined in this third embodiment.

In addition, the value range accessible by the voltage U across the first arm A is greater than the value range accessible by the voltage across the first arm A in the converter illustrated in FIG. 2. Indeed, if the ratio ( is greater than 1, then the voltage U at the terminals of the first branch A is greater than the input voltage Ve, In particular, the voltage U may be greater than a maximum value Ve _ma x of the input voltage Ve. The voltage U at the terminals of the first branch A may therefore be higher than the input voltage Ve of the isolated DC / DC converter 1, unlike the case of the converter illustrated in FIG. 2. Similarly, if the ratio (is less than 1, then the voltage U across the first arm A is lower than the input voltage Ve, in particular the voltage U may be less than a minimum value Ve _m in of the input voltage Ve. terminals of the first arm A can therefore be more than the input voltage Ve of the isolated DC / DC converter 1, unlike the case of the converter illustrated in FIG.

It may be noted that this property of lowering or raising the input voltage Ve can be realized in an isolated DC / DC converter 1 according to the second embodiment, by using a step-down converter as a control circuit. 2. The converter 1 obtained therefore comprise two additional switch arms relative to the first arm A. The total number of switch arms would therefore be three on the primary side of the converter 1. While in the converter according to this mode of realization, the property of lowering or raising the input voltage is obtained with two arms A, B of switches MA1, MA2, MB1, MB2 on the primary side of the converter 1.

According to a first variant of this third embodiment, the switches MA1, MA2 of the first arm A operate with a duty cycle that does not vary, that is to say that remains constant over time. The duty cycle remains substantially equal to a nominal value ON. During operation of the isolated DC / DC converter 1, the output voltage Vo is controlled by the current flowing in the third inductor L3. This current is controlled by the second arm B. For this purpose, the isolated DC / DC converter 1 may comprise a control unit 5 of the second arm B. The control unit 5 delivers a pulse width modulation signal S2. which controls the opening and closing of the switches MB1, MB2 of the second arm B to control the current flowing in the third inductance L3. The switches MB1, MB2 of the second arm B are controlled so that the current flowing in the third inductance L3 makes it possible to obtain a desired voltage value Vo at the output of the isolated DC / DC converter.

1. Thus, it is not necessary to vary the duty cycle of the switches MAI, MA2 of the first arm A. The first arm A can therefore operate at its most advantageous duty cycle for the transmission of energy by the magnetic component 100, especially 50%.

At a duty cycle of 50% in the first arm A, the average current in the magnetic component 100 is zero and allows a decrease of the current ripple at the output of the isolated DC / DC converter as explained previously for the first embodiment.

The voltage U across the first branch A is then equal to 2aBVe. With the duty ratio of the second arm B, it is possible to vary the voltage U across the first arm A. If the duty ratio of the second arm B is less than 50%, the voltage U across the first arm A is less than 2Ve. . If the duty ratio of the second arm B is greater than 50%, the voltage U across the first arm A is greater than 2Ve. A cyclic ratio of 50% for the first arm A thus allows a simple control of the isolated DC / DC converter 1.

In particular, when the input voltage Ve of the voltage converter 1 varies, the second arm B ensures that the output voltage Vo keeps a desired value. Thus, if the input voltage Ve of the isolated DC / DC converter 1 changes value, the control unit 5 correspondingly modifies the control of the cyclic ratios of the switches MB1, MB2 of the second arm B to maintain the current flowing through the third inductance L3 to a desired value. This is particularly advantageous in an electric vehicle where the charge level of a battery can vary over time.

More particularly, the control unit 5 carries out a first current control loop traversing the third inductance L3 connected between the first A and second B arms to a difference between the value Vo_mes of the output voltage of the isolated DC / DC converter. 1 and a desired voltage Vo at the output of the isolated DC / DC converter 1. For this purpose, the control unit 5 receives the voltage Vo_mes measured at the output of the isolated DC / DC converter 1, possibly multiplied by a gain K1. The control unit 5 then compares a voltage setpoint V * with the voltage Vo_mes measured. The voltage setpoint V * corresponds to the desired voltage Vo at the output of the isolated DC / DC converter 1. Depending on the result of the comparison, a controller 51 supplies the second arm B with a current setpoint.

Dcons having to go through the third inductance L3.

The current setpoint Dcons can be transmitted directly to a controller 52 which supplies the second arm B with the PWM signal S2 from the current setpoint Dcons. However, the control unit 5 can produce a second loop which slaves the current flowing through the third inductance L3 to a difference between the value Dmes of the current flowing through the third inductance L3 and the current setpoint Dcons. In particular, the control unit 5 compares the current setpoint Dcons resulting from the first loop with the current Dmes measured on the third inductance L3. The current Dcons is possibly multiplied by a gain K2 before the comparison. Depending on the result of this comparison, the controller 52 determines the control signal S2 of the duty cycle (switches MB1, MB2 of the second arm B, so as to adjust the current flowing through the third inductance L3. However, the current loop is easier to implement because, in a small signal, the current loop makes it possible to have a first-order transfer function while the voltage loop is of the second order. isolated DC / DC converter 1 could implement the first loop without using the second loop.

As in the second embodiment, the isolated DC / DC converter 1 according to the third embodiment may be designed to cover a range of operation. The operating range corresponds to an input voltage Ve of the isolated DC / DC converter 1 between a minimum value Ve _m in and a maximum value Ve _ma x; and at an output voltage Vo between a minimum value Vo _m in and a maximum value Vo _mas . For example, the input voltage Ve is between 170 and 450V; and the target voltage Vo at the output of the isolated DC / DC converter 1 is between 12 and 16V. For example, the minimum value Vomin of the output voltage is between 8 and 14V and the maximum value Vo _mas of the output voltage is between 15 and 16V.

In a second variant of the third embodiment, the duty ratio of the first arm A varies around the nominal value (as a function of an electrical parameter Γ of the signal traveling through the third inductance L3) .The advantage of this variant will be understood with this following.

In a first part of the operating period T close to that illustrated in FIG. 3, the second switch MA2 of the first arm A is closed and the first switch MA1 of the first arm A is open. The second switch MA2 is then traversed by a current from the third inductance L3 and a current It from the magnetic component 100. These currents add up because they flow in the same direction. In a second part of the operating period T close to that illustrated in FIG. 4, the second switch MA2 first arm A is open and the first MAI switch of the first arm A is closed. The first switch MAI is then traversed by a current from the third inductance L3 and a current It from the magnetic component 100. These currents are withdrawn because they do not flow in the same direction.

Thus, the first switch MAI and the second switch MA2 do not see the same current during operation of the isolated DC / DC converter 1. The second switch MA2 is traversed by a current higher than the first switch MAI, which creates a imbalance between the losses when the first switch MAI is closed and losses when the second switch MA2 is closed. The second switch MA2 wears faster than the first switch MAI because it receives a higher current.

One solution would be to double the second switch MA2, that is to say to replace the second switch MA2 by two switches in parallel. But this complicates the circuit and does not always guarantee that the same current flows between the two switches in parallel.

One way of balancing the losses between the two switches MAI, MA2 of the first arm A is to use an electrical parameter of the magnetic component 100, such as its average current Γτ, to rebalance the currents flowing in the first switch MAI and the second switch. MA2.

Figure 9 shows an equivalent diagram of the isolated circuit 3 in steady state. The average current in the first capacitance C1 is zero. It is observed that the average current I ' _MAI flowing in the first switch MAI is equal to the average current IV 2 flowing in the first primary circuit 101, where Γτ is the total average current flowing in the two primary circuits 101, 101'. It is further observed that the average current I ' _MA2 flowing in the second switch MA2 is equal to the average current I'L3 flowing in the third inductance L3 minus the average current Γτ 11 flowing in the second primary circuit 101'. The average currents I'MAI, I'MA2 flowing in the first MAI and the second switch MA2 are equal if the average current I ' _L 3 flowing in the third inductance L3 is equal to the total average current Γτ flowing in the two primary circuits 101 , 10 Γ.

FIG. 10 shows an equivalent diagram of the isolated circuit 3 on the first part of the operating period T. FIG. 11 shows an equivalent diagram of the isolated circuit 3 on the second operating period T. The following relationship is deduced:

Where Γ _Α is the equivalent resistance of each switch MAI, MA2, assuming that it is the same for each switch; rr is the equivalent resistance of the magnetic component 100 obtained from the equivalent resistances r _w of the primary circuits 101, 101 ', in particular r _T = ^; U is the voltage at the first extremal terminal of the first arm A. Thus, by acting on the duty ratio A of the first arm A, the value of the average current Γτ flowing in the magnetic component 100 can be modified so that it is equal to the average current I'L3 delivered by the third inductor L3 to the second point P2 connection. In particular, by increasing the duty cycle A of the first arm A, the average current Γτ flowing in the magnetic component 100 is increased; by decreasing the cyclic ratio aA of the first arm A, the average current Γτ flowing in the magnetic component 100 is decreased.

Just small variations around the nominal value aN cyclic ratio aA of the first arm A to adjust the average current Γτ flowing in the magnetic component 100. Notably, the duty cycle varies around this nominal value aN to plus or minus 2% compared to the nominal value aN. This nominal value aN is for example equal to 50% because of the advantages mentioned above.

The adjustment of the average current Γτ flowing in the magnetic component 100 can be obtained by a control loop of the duty ratio aA of the first arm A as a function of a difference between the mean current Γτ flowing in the magnetic component 100 and the current means I'L3 delivered by the third inductor L3 at the second connection point P2. For example, for a switching frequency of 300 kHz, the servo loop operates at a frequency between 2 and 3 kHz. The measurements of the current flowing in the magnetic component 100 and in the third inductance L3 are carried out at a frequency of

20kHz.

In particular, the average current Γτ flowing in the magnetic component 100 is measured over contiguous cutting periods of the first arm A, and the average current I'L3 delivered by the third inductance L3 is measured over contiguous switching periods of the second arm B .

Figure 12 illustrates an isolated DC / DC converter 1 according to a fourth embodiment. The converter 1 illustrated in FIG. 12 is similar to that illustrated in FIG. 8, except that it comprises a third capacitor C3 and a fourth inductor L4. The third capacitor C3 is connected between the first switch MB1 of the second arm B and the second switch MB2 of the second arm B. Thus, the third capacitor C3 is in series between the first switch MB1 and the second switch MB2 of the second arm B. The third inductor L3 is connected to the connection point P3 between the third capacitor C3 and the second switch MB2. The fourth inductor L4 is connected between the first connection point PI and a fourth connection point P4 between the first switch MB 1 and the third capacitor C3.

By adding the third capacitor C3 and the fourth inductor L4, the voltage range achievable by the isolated DC / DC converter 1 is increased with respect to the converter illustrated in FIG. 8. The isolated DC / DC converter 1 according to this fourth embodiment forms an up / down DC / DC converter.

This will be better understood from the following.

In the converter, the average voltage of an inductor is zero. As a result, the average voltage at the first connection point PI is equal to the average voltage at the fourth connection point P4; and the average voltage at the third connection point P3 is equal to the average voltage at the second connection point P2. The average voltage across the third capacitor C3 is therefore equal to the average voltage across the first capacitor C1.

In addition, it also results that the average voltage at the first connection point PI is zero. The average voltage at the second connection point P2 is equal to the average voltage VC2 'across the second capacitor C2. And therefore the average voltage VC2 'across the second capacitor C2 is equal to the average voltage VC1' of the first capacitor C1.

By controlling the switches MB1, MB2 of the second arm B with a duty ratio B, the average voltage Vp ₄ 'at the fourth connection point P4 is given by the relation

Vp4 '= a x Ve - (1 - a) x VC3'

Therefore

Vc3 '= Vc2 = - ^ - x Ve

1 - a

This relationship shows that the voltage VC2 across the capacitor C2 can be controlled by the duty cycle (XB of the second arm B. Thus, when the duty cycle (XB of the second arm B is less than 1 the converter 1 operates as a step-down voltage and when the duty cycle (XB is greater than 1, the converter 1 operates as a voltage booster.

The converter according to this fourth embodiment can operate similarly to the converter according to the third embodiment. The converter according to this fourth embodiment achieves a larger operating range than the converter according to the third embodiment. Indeed, in the third embodiment, the minimum allowable input voltage of the isolated DC / DC converter 1 is limited by the voltage of the second capacitor C2, the voltage of the second capacitor C2 being a function of the output voltage Vo. While in the fourth embodiment, the minimum voltage is not limited by the voltage across the second capacitor C2.

In the converter according to the invention, the magnetic component 100 may comprise a first T1 and a second T2 transformers in series. Each transformer T1, T2 has two primaries. The primers of the first transformer T1 form respectively the first portion LU of the first primary circuit 101 and the first portion LU 'of the second primary circuit 10; and the secondary of the first transformer T1 forms the first portion L12 of the secondary circuit 102. The primary of the second transformer T2 respectively form the second portion L21 of the first primary circuit 101 and the second portion L21 'of the second primary circuit 10; and the secondary of the second transformer T2 forms the second portion L22 of the secondary circuit 102. The magnetic component 100 can be made otherwise. For example, the first primary circuit 101 can be made with a single first primary winding and the second primary circuit 10 can also be realized with a single second primary winding. The secondary circuit 102 may be made with two secondary windings. These windings are in particular wound around a common magnetic core. The two secondary windings are magnetically coupled to the primary windings but are not magnetically coupled to each other. In particular, the first LU and second L21 parts of the first primary circuit 101 are respectively formed with a first and a second portion of the first primary winding. In particular, the first LU 'and second L21' parts of the second primary circuit 10 are respectively formed with a first and a second portion of the second primary winding. Such a way of producing the magnetic component 100 not only reduces the cost of the converter 1 by reducing the number of components comprising ferrite, but also reduces the size of the converter 1 to obtain a more compact converter.

In the embodiments, the second switch MB2 of the second arm B may be replaced by a diode DB (illustrated in FIG. 14) whose cathode is connected to the third connection point P3. This produces a unidirectional converter instead of a bidirectional converter as is the case when the second arm B includes a second switch MB2.

Fig. 13 shows an exemplary converter according to a fifth embodiment. The converter 1 of FIG. 13 is obtained from the converter of FIG. 2 by adding a third switch arm E and two primary circuits 101 E, 10 Ε similar to the first arm A and to the two primary circuits 101, 10 of the In particular, the third arm E comprises a first switch ME1 in series with a capacitor CE and a second switch ME2. A first extremal terminal of the third arm E corresponds to the terminal of the first switch ME1 which is not connected to the capacitor CE; a second extremal terminal of the third arm E corresponds to the terminal of the second switch ME2 which is not connected to the capacitor CE. The first end terminal of the third arm E is connected to the first end terminal of the first arm A and the second end terminal of the third arm E is connected to the second end terminal of the first arm A. Add a third arm E and two primary circuits 101E , 10 Ε to the converter of FIG. 2 makes it possible to double the voltage range accessible by the isolated DC / DC converter 1. The converter 1 can comprise as many arms E and primary circuits 101E, 10Ε additional 101E, 10Ε as necessary . This embodiment is compatible with all other embodiments.

The examples of isolated DC / DC converter 1 according to the invention are particularly suitable for applications embedded in a vehicle, in particular an electric or hybrid vehicle, for the voltage conversion between a first and a second edge network of different voltages. In particular, the isolated DC / DC converter 1 may be included in a system comprising an AC / DC converter configured to power an electrical machine of the vehicle from the first electrical network. A capacitor can be connected to the input terminals of the AC / DC converter to interface between the first power grid and the AC / DC converter. The isolated DC / DC converter 1 can then be connected to the terminals of this capacitor so as to perform precharge or capacitance discharge operations. Such a system is for example described in the European patent application publication EP2012338 A1. The converter according to the fourth embodiment illustrated in FIG. 12 is particularly adapted to these precharge or discharge operations, since it makes it possible to preload the capacity since zero initial voltage across the capacitance, and discharge the capacitance to zero final voltage across the capacitance.

The invention is not limited to the examples described. In particular, the voltage loops can be replaced by current loops. The isolated DC / DC converter can also be used in an AC-DC converter configured to convert an AC voltage into a DC voltage or vice versa, or into an AC-AC converter. Advantageously, the isolated DC / DC converter is then completed by an AC-DC converter upstream of the first arm A in the first or the fifth embodiment, or upstream of the regulation circuit 2 in the second embodiment, or upstream of the second arm B for the third or fourth embodiment; and / or a DC-AC converter downstream of the isolated DC / DC converter.

In particular, the switches may be transistors, such as MOSFET, IGBT or other transistors. The circuits may be made from a semiconductor material such as silicon (Si), gallium nitride (GaN), silicon carbide (SiC), or any other semiconductor material.

Claims

An isolated DC / DC converter (1) comprising an isolated circuit (3) having:

a first arm (A) comprising a first switch (MAI), in series with a second switch (MA2);

a magnetic component (100) comprising two primary circuits (101, 101 ') and a secondary circuit (102) separated by at least one electrical insulation barrier, said magnetic component (100) being configured for, during the conversion of an input voltage (Ve) of the isolated DC / DC converter into an output voltage (Vo), function as a transformer of the primary circuits (101,

101 ') to the secondary circuit (102) and as an impedance which stores energy at the primary circuits (101, 10),

and wherein:

the first arm (A) comprises a first capacitance (Cl) in series with the two switches (MAI, MA2) and situated between the two switches (MAI, MA2),

one of said primary circuits, said second primary circuit (10), is connected between a first extremal terminal of the first arm (A) and the connection point, said second connection point (P2), between the second switch (MA2) of first arm (A) and the first capacitance (C1), the first extremal terminal of the first arm (A) corresponding to the terminal of the first switch (MAI) which is not connected to the first capacitance (C1); and

the other primary circuit, said first primary circuit (101), is connected between a second extremal terminal of the first arm (A) and the connection point, said first connection point (PI), between the first switch (MAI) and the first capacitance (C1), the second extremal terminal of the first arm (A) corresponding to the terminal of the second switch (MA2) which is not connected to the first capacitance (C1).

The converter of claim 1, wherein the magnetic component (100) is configured so that:

in a first part of a period of operation of the converter, respective first portions (LU, LU ') of the primary circuits (101, 101') transfer energy to a first portion (L12) of the secondary circuit (102), and respective second portions (L21, L21 ') of the primary circuits (101, 101') provide inductances for storing energy;

on a second part of the operating period of the converter, the respective second portions (L21, L21 ') of the primary circuits (101, 10 Γ) transfer energy to a second portion (L22) of the secondary circuit (102), and the respective first portions (LU, LU ') of the primary circuits (101, 10) produce inductances that store energy.

3. Converter according to claim 1 or 2, wherein the input of the isolated circuit (3) is at the first terminal extremal of the first arm (A).

4. Converter according to one of claims 1 to 3, comprising a control circuit (2) connected to the first end terminal of the first arm (A) and for regulating a voltage (U) delivered to the first arm (A), the control circuit (2) being configured to control the output voltage (Vo) of the isolated DC / DC converter by modifying the voltage (U) delivered to the first arm (A), the duty cycle (OIA) of the first arm (A ) remaining substantially constant.

5. Converter according to the preceding claim, wherein a second capacitor (C2) is connected between the first end terminal of the first arm (A) and the second end terminal of the first arm (A).

Converter according to claim 1 or 2, comprising:

a second arm (B) comprising a first switch (MB1) and a second electronic element (MB2, DB) in series, the free terminal of the second electronic element (MB2, DB) being connected to the second extremal terminal of the first arm ( AT),

an inductor (L3) connected between the second connection point (P2) and a third connection point (P3), the third connection point (P3) corresponding to the terminal of the second electronic element (MB2, DB) which is on the side of the first switch of the second arm (B),

a second capacitance (C2) connected between the first extremal terminal of the first arm (A) and the second extremal terminal of the first arm (A),

the second electronic element being a second switch (MB 2) or a diode (DB) having its cathode connected to the third connection point (P3), and in which successions of opening and closing of the switch or switches of the second arm ( B) convert an input voltage (Ve) into an output voltage (Vo) via the magnetic component (100).

7. Converter (1) according to the preceding claim, wherein the second arm (B) is configured to control the output voltage (Vo) of the isolated DC / DC converter (1) by modifying an electrical parameter (Γ) of a signal traversing the inductance (L3).

8. Converter according to claim 7, wherein the electrical parameter is an average current (Γ).

The converter (1) according to claim 7 or 8, wherein the first arm (A) is configured so that its duty cycle has a nominal value ((XN) and varies around this nominal value ((XN) depending of a difference between a value (I'L3) of the electrical parameter of the signal traversing the inductance (L3) and a value (Γτ) of the electrical parameter of the signal traveling through the magnetic component (100).

Converter (1) according to claim 9, wherein the first arm

(A) is configured so that its duty cycle has a nominal value ((ΧΝ) and varies around this nominal value ((ΧΝ) so that the value (Γυ) of the electrical parameter of the signal traversing the inductance (L3) and the value (Γτ) of the electrical parameter of the signal traveling through the magnetic component (100) is equal.

11. Converter (1) according to one of claims 6 to 8, wherein the duty cycle of the first arm (A) remains substantially constant at a nominal value ((ΧΝ).

Converter according to one of claims 6 to 11, further comprising:

a third capacitance (C3) in series between the first switch (MB1) of the second arm (B) and the second electronic element (MB1, DB) of the second arm (B), the third capacitor (C3) being connected between the third connection point (P3) and a fourth connection point (P4) corresponding to the terminal of the first switch (MDB1) which is on the side of the second electronic element (MB1, DB) of the second arm (B),

another inductor (L4) connected between the first connection point (PI) and the fourth connection point (P4).

13. Converter according to one of claims 1 to 12, wherein the isolated circuit (3) further comprises at least a third arm (E) comprising a first switch (ME1), a second switch (ME2), and a fourth capacitance (CE) in series with the two switches (ME1, ME2) and located between the two switches (ME1, ME2); and wherein the magnetic component

(100) comprises at least two additional primary circuits (101 E, 10 Ε) separated from each other and with the secondary circuit (102) by at least one electrical insulation barrier,

one of said additional primary circuits (101E, 10 Ε), said first additional primary circuit (101E), is connected between a first end terminal of the third arm (E) and the connection point between the second switch (ME2) of the third arm ( E) and the fourth capacitor (CE), the first end terminal of the third arm (E) corresponding to the terminal of the first switch (ME1) of the third arm (E) which is not connected to the fourth capacitance (CE); and

the other of said additional primary circuits (101E, 10 Ε), said second additional primary circuit (101 Έ), is connected between a second extremal terminal of the third arm (A) and the connection point between the first switch (ME1) of the third arm (E) and the fourth capacitor (CE), the second end terminal of the third arm (E) corresponding to the terminal of the second switch (ME2) of the third arm (E) which is not connected to the fourth capacitance (CE), the extremal terminals of the first (A) and the third (E) arm being respectively connected to each other.

A voltage conversion method using an isolated DC / DC converter according to one of claims 6 to 10, wherein the control of the output voltage (Vo) of the isolated DC / DC converter (1) comprises the steps of :

modifying an electrical parameter of a signal traversing the inductance (L3) by varying the duty ratio ((XB) of the second arm (B),

- vary the duty cycle (or) of the first arm (A) around a nominal value ((XN) as a function of a difference between a value (I 'L ₃ ) of the electrical parameter of the signal traversing the inductance ( L3) and a value (Γτ) of the electrical parameter of the signal traveling through the magnetic component (100).