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EP0675422A1 - Regelschaltung zur Erzeugung einer temperatur- und versorgungsspannungsunabhängigen Referenzspannung - Google Patents

Regelschaltung zur Erzeugung einer temperatur- und versorgungsspannungsunabhängigen Referenzspannung Download PDF

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Publication number
EP0675422A1
EP0675422A1 EP95200704A EP95200704A EP0675422A1 EP 0675422 A1 EP0675422 A1 EP 0675422A1 EP 95200704 A EP95200704 A EP 95200704A EP 95200704 A EP95200704 A EP 95200704A EP 0675422 A1 EP0675422 A1 EP 0675422A1
Authority
EP
European Patent Office
Prior art keywords
transistor
emitter
collector
regulator circuit
resistor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
EP95200704A
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English (en)
French (fr)
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EP0675422B1 (de
Inventor
Timothy Ridgers
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Koninklijke Philips NV
Original Assignee
Photonis SAS
Koninklijke Philips Electronics NV
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Publication of EP0675422A1 publication Critical patent/EP0675422A1/de
Application granted granted Critical
Publication of EP0675422B1 publication Critical patent/EP0675422B1/de
Anticipated expiration legal-status Critical
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    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F3/00—Non-retroactive systems for regulating electric variables by using an uncontrolled element, or an uncontrolled combination of elements, such element or such combination having self-regulating properties
    • G05F3/02—Regulating voltage or current
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F3/00—Non-retroactive systems for regulating electric variables by using an uncontrolled element, or an uncontrolled combination of elements, such element or such combination having self-regulating properties
    • G05F3/02—Regulating voltage or current
    • G05F3/08—Regulating voltage or current wherein the variable is DC
    • G05F3/10—Regulating voltage or current wherein the variable is DC using uncontrolled devices with non-linear characteristics
    • G05F3/16—Regulating voltage or current wherein the variable is DC using uncontrolled devices with non-linear characteristics being semiconductor devices
    • G05F3/20—Regulating voltage or current wherein the variable is DC using uncontrolled devices with non-linear characteristics being semiconductor devices using diode- transistor combinations
    • G05F3/26—Current mirrors
    • G05F3/265—Current mirrors using bipolar transistors only
    • G—PHYSICS
    • G05—CONTROLLING; REGULATING
    • G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
    • G05F3/00—Non-retroactive systems for regulating electric variables by using an uncontrolled element, or an uncontrolled combination of elements, such element or such combination having self-regulating properties
    • G05F3/02—Regulating voltage or current
    • G05F3/08—Regulating voltage or current wherein the variable is DC
    • G05F3/10—Regulating voltage or current wherein the variable is DC using uncontrolled devices with non-linear characteristics
    • G05F3/16—Regulating voltage or current wherein the variable is DC using uncontrolled devices with non-linear characteristics being semiconductor devices
    • G05F3/20—Regulating voltage or current wherein the variable is DC using uncontrolled devices with non-linear characteristics being semiconductor devices using diode- transistor combinations
    • G05F3/30—Regulators using the difference between the base-emitter voltages of two bipolar transistors operating at different current densities

Definitions

  • the present invention relates to a regulator circuit providing a stabilized voltage, a circuit which is connected between a supply terminal and a reference terminal and comprises in particular four transistors of the same polarity each having an emitter, a base and a collector, a first transistor, the l the emitter is coupled to the reference terminal through a first resistor, a second transistor whose emitter is connected to the reference terminal, the bases and the collectors of the first and second transistors being connected in cross-coupling, a third transistor of which the emitter is connected to the collector of the first transistor, its base and its collector connected together at one end of a second resistor, and a fourth transistor whose emitter is connected to the collector of the second transistor, and the base connected to the base and collector of the third transistor, circuit in which the surface emits ur of the first transistor is larger than that of the third transistor.
  • Such a regulator circuit based on a cell with four transistors of the same polarity is known from document EP-A-0329232.
  • this basic cell with four transistors can supply either a plurality of stabilized current sources or even a voltage source independent of the supply voltage and the temperature.
  • stabilized sources of current or voltage can be produced using bipolar transistors only of the NPN type. It follows that such a circuit can react quickly to variations in supply voltage or to variations in the current consumed at the output.
  • the known regulator circuit does not take into account the base currents of the transistors so that the accuracy of the stabilized voltage obtained remains affected by errors qualified as second order errors.
  • the invention proposes to provide an improvement to a regulator providing a stabilized voltage which is even less sensitive to the value of the supply voltage on either side of a nominal voltage, which exhibits a high rejection of the noise originating of the supply voltage and which remains stable with respect to variations in temperature.
  • a regulator circuit of the type indicated in the introductory paragraph is characterized in that the circuit further comprises a fifth bipolar transistor of the same polarity as the transistors previously mentioned, having an emitter connected to the collector of the fourth transistor , a base coupled to its collector through a base resistance of value at least equal to twice the value of the second resistance, and in that the node connecting this base resistance to the collector of this fifth transistor is on the one hand coupled to the other end of the second resistor and on the other hand, coupled to the supply terminal through a current source.
  • the presence of the fifth transistor provides compensation for certain basic currents, compensation which had been neglected in the known circuit.
  • the basic resistance of the fifth transistor is chosen by a value which is related to the value of the second resistance.
  • connection between the emitter of the fifth transistor and the collector of the fourth transistor constitutes an output of the stabilized voltage.
  • This stabilized voltage is particularly independent of the supply voltage and has a high rate of rejection of the noise contained in the supply voltage.
  • the second, fourth and fifth transistors have an identical emitter surface.
  • the third transistor it is known that its emitter surface must be provided as being a submultiple of the emitter surface of the first transistor, the latter being, in practice, constituted by the association of a plurality of identical transistors, connected in parallel, each of which is of equivalent construction and paired with the third transistor.
  • the third transistor can also have an emitter surface equal to that of the second, fourth or fifth transistors.
  • the regulator circuit is characterized in that it further comprises a sixth transistor and a seventh transistor, of the same polarity as the preceding transistors, the sixth transistor, connected as a diode being inserted in the direct direction between the other end of the second resistor and the source current while the seventh transistor has its base connected to the emitter of the fourth transistor, its collector coupled to the supply terminal, and its emitter, which provides an output of the stabilized voltage, is coupled to the reference terminal at across an emitter resistor.
  • This implementation mode has a lower stabilized voltage output impedance and therefore allows higher current consumption at the output, compared with the previous implementation mode.
  • the collector of the seventh transistor can also constitute another output of the regulator circuit providing a reference current stabilized with respect to the supply voltage and the temperature.
  • the regulator circuit according to the invention can be produced only using NPN type bipolar transistors, it is capable of reacting at high frequency, in particular to reject as output the fluctuations in the supply voltage, at high frequency. To further increase this rejection power, with respect to the noise of the supply voltage, the regulator circuit according to the invention is advantageously supplemented with a capacitor connected in parallel between the bases of the fifth transistor and of the second transistor.
  • the capacitance in question may be of low value (a few pF for example) to be integrated with the regulator circuit, its effect being multiplied by the gain of the second transistor. It is noted that the power of rejection with respect to the noise of the supply voltage as a function of the frequency of this noise, increases with the frequency from a certain frequency value, of the order of 1 MHz. This property contrasts with the behavior of regulating circuits of the prior art using a high gain error amplifier which must be frequency stabilized. On the contrary, such regulating circuits have a noise rejection power which decreases beyond a limit frequency, corresponding in fact to the frequency from which the error amplifier is voluntarily limited in gain.
  • the current source supplying the regulator circuit from the supply terminal is reduced to a resistance.
  • a resistance for reasons of economy of the supply current, in particular in battery-powered applications, it may be advantageous to be able to completely deactivate the regulator circuit, which can be achieved when the current source is produced using a resistor in series with a MOS field effect type switching transistor.
  • the regulator circuit of FIG. 1 is supplied between a positive supply voltage terminal 1 having a voltage Vcc and a reference terminal 2 carrying a voltage VEE (ground).
  • This circuit includes a first transistor T1 whose emitter is coupled to the reference terminal 2 through an emitter resistor R1, a second transistor T2 whose emitter is also connected to the reference terminal 2, the transistors T1 and T2 have their bases and their collectors interconnected in cross coupling.
  • a third transistor T3 has its emitter connected to the collector of the first transistor T1, its base and its collector joined together to form a diode configuration are connected on the one hand, to a first end of a second resistor R2, as well as to the base of a fourth transistor T4 whose emitter is connected to the collector of the second transistor T2.
  • the four transistors T1 to T4 have the same polarity, here of NPN type, and the emitter surface of the first transitor T1 is n times larger than that of the third transistor T3.
  • the transistors T2 and T4 preferably have an identical emitter surface which can also be equal to that of the transistor T3.
  • the other end of the second resistor R2 is coupled to the positive supply terminal 1 through a current source 11 which here is simply constituted by a resistor, in this example.
  • the connection between the current source 11 and the resistor R2 forms a line 12 to which is connected a resistor R5 supplying the base of a fifth transistor T5, which has its collector connected to the league 12 and its emitter connected to the collector of the fourth transistor T4.
  • the current source 11 constitutes a very imperfect current source in which a current flows which varies with the supply voltage Vcc.
  • the voltage of the line 12 being practically fixed by the sum of the base / emitter voltages of the transistors T2 and T3 increased by the voltage drop in the resistor R2 due to the current I1, the current I2 simply results from the difference between the current supplied by the current source 11 and the current I1.
  • the transistor T5 presents to its emitter a voltage deduced from the voltage Vx by subtracting a base / emitter voltage from this transistor which outputs the current I2.
  • the transistor T5 is chosen as having an emitter surface equal to the emitter surfaces of the transistors T2 or T4 so that the base / emitter voltage drop in the transistor T5 compensates for the voltage drop in the transistor T2.
  • the output voltage Vref of the circuit is substantially equal to the sum of a voltage drop I1.R2 having a positive temperature coefficient and a base / emitter voltage of transistor T3 traversed by a current I1, which base / emitter voltage has a negative temperature coefficient.
  • the value of the resistance R2 is chosen so that the two components of the sum of the voltages have temperature coefficients that cancel each other out. In practice it is usual to use a voltage drop I1.R2 whose value is of the order of 500mV.
  • the base current of transistor T5 being, as a first approximation, substantially equal to the base current of transistor T4 or of the base current of transistor T2, compensation for the aforementioned effect on the voltage Vx of line 12 should be obtained when the resistor R5 inserted in the base of the transistor T5 is equal to twice the value of the resistor R2. Thus the increase in voltage Vx should be compensated at the output of the regulator circuit.
  • a value of the current source 11 is chosen such that for a nominal supply voltage Vcc, the currents I1 and I2 are substantially equal.
  • the current I2 varies, but as we have seen previously, the stabilized voltage obtained Vref is only very slightly disturbed .
  • the regulator circuit is capable of reacting to fluctuations in supply voltages even when these fluctuations are at high frequencies.
  • the rejection of the noise contained in the supply voltage Vcc can be further improved in a preferred embodiment according to which the base of the transistor T5 is coupled to the base of the transistor T2 using a capacitor C.
  • This capacity can be easily integrated since a low value is sufficient. Its effect, as a first approximation, is multiplied by the gain of transistor T2.
  • the noise rejection rate R at the output of the regulator circuit from the noise presented by the supply voltage Vcc is represented in FIG. 2 curve A, as a function of the frequency F of this noise .
  • the rejection rate increases beyond a certain limit frequency. This remarkable property is particularly advantageous when the regulator circuit is used in applications where it is integrated in conjunction with circuits switched at high frequencies, for example frequency dividers which provide interference at high frequencies on the supply voltage.
  • Figure 3 shows very schematically the principle underlying many known regulator circuits. It comprises on the one hand a cell 30 with two transistors whose emitter surfaces are uneven, intended to deliver a current proportional to the temperature on a compensation resistor R. The collectors of the transistors flow on paired loads, symbolically represented by an assembly 31.
  • the circuit further comprises a differential amplifier 32, with high gain, the output of which supplies the combined bases of the two transistors, the whole arranged so that the collector currents of the transistors are equal.
  • the amplifier 32 is therefore an error amplifier and thus, the reference voltage Vref at the output of this amplifier is all the more precise the higher the gain of the amplifier. It is also well known that such an amplifier needs to be stabilized in frequency and therefore has a gain curve G, the shape of which is shown in FIG. 4.
  • the power of rejection R of the noise of the supply voltage for a regulator circuit of this type, has a shape inverse to that of the gain, such as that indicated by the curve B in dashes, of FIG. 2. It is clear that from the point of view of the noise rejection, the circuit according to the invention is very advantageous in applications where is exhibits high frequency noise.
  • FIG. 5 represents the diagram of a second embodiment of the invention.
  • the circuit of FIG. 5 shows all the elements of the circuit of FIG. 1 to which are added a sixth transistor T6 and a seventh transistor T7 of the same polarity as the transistors T1 to T5.
  • the transistor T6 is connected as a diode, its emitter-collector path is inserted between the resistor R2 and the line 12.
  • the voltage Vx of the line 12 is thus increased by the value of a V BE compared to the example previously described .
  • the transistor T7 has its base connected to the node joining the emitter of the transistor T5 to the collector of the transistor T4. Its transmitter is coupled to reference terminal 2 through an R7 transmitter load resistor.
  • the transistor T7 is therefore arranged as a follower emitter and supplies its stabilized voltage Vref on its emitter.
  • the base / emitter voltage drop of T7 compensates, as a first approximation, the voltage drop in the transistor T6 so that the voltage Vref is again practically identical to that obtained previously with the circuit of FIG. 1.
  • the output impedance of the circuit is lower than previously and a larger current can be taken at the output.
  • the collector of the transistor is shown as being supplied by a terminal 17. This can be connected directly to line 12 or even to the supply terminal 1. However, the circuit shown can also supply a stabilized reference current Io, absorbed by the collector of transistor T7. Terminal 17 then constitutes such an output of the regulator circuit.
  • the current source 11 presented as a so-called limiting resistor in FIG. 1 is only a simplified example and one could also use any other current source provided with means ensuring, for example, even pre-regulation. rough current supplying the two branches of the regulator circuit. In applications where the voltage regulator circuit is not used continuously, it is desirable to be able to deactivate the regulator circuit when its use is not required, so as to save current consumption.
  • FIG. 6 presents an example of substitution of the current source 11 of FIG. 1 by a resistor 21 and MOS field effect transistor 22 assembly.
  • a switchable current source which has a resistance equal to the sum of the value of the resistance 21 and the internal resistance of the transistor 22 when it is conductive.
  • FIG. 7 represents another example of current source 11, provided with means ensuring a pre-regulation of the current supplying the whole of the regulator circuit.
  • Two resistors 31 and 32 are connected in series between the supply terminal 1 and the line 12.
  • the common point between these resistors has its voltage V D regulated by the effect of four diodes D1 to D4, connected in series between this point and the reference terminal 2.
  • FIG. 8 represents yet another example of a current source 11 using at least one transistor T8 of PNP type, ensuring by all known means, a pre-regulation of the current supplied by its emitter / collector path.
  • a PNP type transistor has the drawback that the stray capacitance of such a transistor is generally large, which is unfavorable from the point of view of the rejection of noise from the supply voltage.
  • a resistor 41 is inserted between the collector of the transistor T8 and the line 12 so as to reduce the effect of the stray capacitance of the transistor T8.

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  • Engineering & Computer Science (AREA)
  • Physics & Mathematics (AREA)
  • Microelectronics & Electronic Packaging (AREA)
  • Automation & Control Theory (AREA)
  • Electromagnetism (AREA)
  • General Physics & Mathematics (AREA)
  • Radar, Positioning & Navigation (AREA)
  • Nonlinear Science (AREA)
  • Power Engineering (AREA)
  • Control Of Electrical Variables (AREA)
  • Continuous-Control Power Sources That Use Transistors (AREA)
  • Amplifiers (AREA)
  • Logic Circuits (AREA)
EP95200704A 1994-03-30 1995-03-22 Regelschaltung zur Erzeugung einer temperatur- und versorgungsspannungsunabhängigen Referenzspannung Expired - Lifetime EP0675422B1 (de)

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
FR9403775A FR2718259A1 (fr) 1994-03-30 1994-03-30 Circuit régulateur fournissant une tension indépendante de l'alimentation et de la température.
FR9403775 1994-03-30

Publications (2)

Publication Number Publication Date
EP0675422A1 true EP0675422A1 (de) 1995-10-04
EP0675422B1 EP0675422B1 (de) 1999-09-08

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EP95200704A Expired - Lifetime EP0675422B1 (de) 1994-03-30 1995-03-22 Regelschaltung zur Erzeugung einer temperatur- und versorgungsspannungsunabhängigen Referenzspannung

Country Status (8)

Country Link
US (1) US5576616A (de)
EP (1) EP0675422B1 (de)
JP (1) JPH07271461A (de)
KR (1) KR950033755A (de)
CN (1) CN1118461A (de)
DE (1) DE69511923T2 (de)
FR (1) FR2718259A1 (de)
TW (1) TW255073B (de)

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2310737A (en) * 1996-03-01 1997-09-03 Nec Corp Voltage reference circuit
FR2757964A1 (fr) * 1996-12-31 1998-07-03 Sgs Thomson Microelectronics Regulateur de tension serie

Families Citing this family (14)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
DE19530737A1 (de) * 1995-08-22 1997-02-27 Philips Patentverwaltung Schaltungsanordnung zum Liefern eines konstanten Stromes
US6002293A (en) * 1998-03-24 1999-12-14 Analog Devices, Inc. High transconductance voltage reference cell
DE19821906C1 (de) * 1998-05-15 2000-03-02 Siemens Ag Klemmschaltung
CN1154032C (zh) * 1999-09-02 2004-06-16 深圳赛意法微电子有限公司 预调节器、产生参考电压的电路和方法
US6285244B1 (en) * 1999-10-02 2001-09-04 Texas Instruments Incorporated Low voltage, VCC incentive, low temperature co-efficient, stable cross-coupled bandgap circuit
FR2806489B1 (fr) * 2000-03-15 2002-06-28 St Microelectronics Sa Circuit de fourniture de tension de reference
US7259626B2 (en) * 2004-12-28 2007-08-21 Broadcom Corporation Apparatus and method for biasing cascode devices in a differential pair using the input, output, or other nodes in the circuit
CN1896900B (zh) * 2005-07-13 2010-10-06 辉达公司 能阶参考电路
TW200810231A (en) 2006-08-11 2008-02-16 Hon Hai Prec Ind Co Ltd Antenna device
TWI355772B (en) 2006-12-29 2012-01-01 Advanced Semiconductor Eng Carrier with solid antenna structure and manufactu
US8669754B2 (en) * 2011-04-06 2014-03-11 Icera Inc. Low supply regulator having a high power supply rejection ratio
CN103163935B (zh) * 2011-12-19 2015-04-01 中国科学院微电子研究所 一种cmos集成电路中基准电流源产生电路
US9921596B2 (en) * 2013-12-23 2018-03-20 Marvell Israel (M.I.S.L) Ltd Power supply noise reduction circuit and power supply noise reduction method
CN115268551B (zh) * 2021-04-30 2024-04-09 炬芯科技股份有限公司 基准电压生成电路、集成芯片和方法

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3930172A (en) * 1974-11-06 1975-12-30 Nat Semiconductor Corp Input supply independent circuit
US4491780A (en) * 1983-08-15 1985-01-01 Motorola, Inc. Temperature compensated voltage reference circuit
EP0329232A1 (de) * 1988-02-16 1989-08-23 Koninklijke Philips Electronics N.V. Stabilisierte Strom- und Spannungsquellen
US5015942A (en) * 1990-06-07 1991-05-14 Cherry Semiconductor Corporation Positive temperature coefficient current source with low power dissipation
US5049807A (en) * 1991-01-03 1991-09-17 Bell Communications Research, Inc. All-NPN-transistor voltage regulator

Family Cites Families (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
NL8501882A (nl) * 1985-07-01 1987-02-02 Philips Nv Signaalspanning-stroom omzetter.
US4958122A (en) * 1989-12-18 1990-09-18 Motorola, Inc. Current source regulator
GB2264573B (en) * 1992-02-05 1996-08-21 Nec Corp Reference voltage generating circuit
US5446409A (en) * 1992-11-30 1995-08-29 Sony Corporation Cross coupled symmetrical current source unit
US5367249A (en) * 1993-04-21 1994-11-22 Delco Electronics Corporation Circuit including bandgap reference
US5399914A (en) * 1993-10-18 1995-03-21 Allegro Microsystems, Inc. High ratio current source

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US3930172A (en) * 1974-11-06 1975-12-30 Nat Semiconductor Corp Input supply independent circuit
US4491780A (en) * 1983-08-15 1985-01-01 Motorola, Inc. Temperature compensated voltage reference circuit
EP0329232A1 (de) * 1988-02-16 1989-08-23 Koninklijke Philips Electronics N.V. Stabilisierte Strom- und Spannungsquellen
US5015942A (en) * 1990-06-07 1991-05-14 Cherry Semiconductor Corporation Positive temperature coefficient current source with low power dissipation
US5049807A (en) * 1991-01-03 1991-09-17 Bell Communications Research, Inc. All-NPN-transistor voltage regulator

Non-Patent Citations (2)

* Cited by examiner, † Cited by third party
Title
"Temperature Compensation Current Reference", RESEARCH DISCLOSURE, no. 337, EMSWORTH, pages 419 - 420 *
BROKAW: "A Monolithic Conditioner for Thermocouple Signals", IEEE JOURNAL OF SOLID STATE CIRCUITS, vol. sc18, no. 6, pages 707 - 716, XP001411105 *

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
GB2310737A (en) * 1996-03-01 1997-09-03 Nec Corp Voltage reference circuit
GB2310737B (en) * 1996-03-01 1999-11-10 Nec Corp Voltage reference circuit
FR2757964A1 (fr) * 1996-12-31 1998-07-03 Sgs Thomson Microelectronics Regulateur de tension serie

Also Published As

Publication number Publication date
CN1118461A (zh) 1996-03-13
JPH07271461A (ja) 1995-10-20
TW255073B (en) 1995-08-21
FR2718259A1 (fr) 1995-10-06
US5576616A (en) 1996-11-19
DE69511923D1 (de) 1999-10-14
KR950033755A (ko) 1995-12-26
DE69511923T2 (de) 2000-03-30
EP0675422B1 (de) 1999-09-08

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