CN117118257B - Coupling inductance dual-mode high-efficiency photovoltaic micro inverter - Google Patents
Coupling inductance dual-mode high-efficiency photovoltaic micro inverter Download PDFInfo
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- CN117118257B CN117118257B CN202311273624.6A CN202311273624A CN117118257B CN 117118257 B CN117118257 B CN 117118257B CN 202311273624 A CN202311273624 A CN 202311273624A CN 117118257 B CN117118257 B CN 117118257B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J3/00—Circuit arrangements for ac mains or ac distribution networks
- H02J3/38—Arrangements for parallely feeding a single network by two or more generators, converters or transformers
- H02J3/381—Dispersed generators
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/01—Resonant DC/DC converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J2300/00—Systems for supplying or distributing electric power characterised by decentralized, dispersed, or local generation
- H02J2300/20—The dispersed energy generation being of renewable origin
- H02J2300/22—The renewable source being solar energy
- H02J2300/24—The renewable source being solar energy of photovoltaic origin
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E10/00—Energy generation through renewable energy sources
- Y02E10/50—Photovoltaic [PV] energy
- Y02E10/56—Power conversion systems, e.g. maximum power point trackers
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- Engineering & Computer Science (AREA)
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Abstract
The invention relates to the technical field of power electronics and renewable energy grid-connected power generation, in particular to a coupling inductance dual-mode high-efficiency photovoltaic micro inverter, which comprises the following components: a main circuit and a control circuit; the power frequency conversion circuit comprises n direct current converter units and a power frequency conversion circuit, wherein the n direct current converter units comprise n photovoltaic modules, n decoupling capacitors, n high-frequency transformers, 5n power switching tubes, n resonance capacitors and 2n filter capacitors; the boost inductor is coupled with the flyback primary side inductor, so that the gain of the converter is improved, and the turn ratio and leakage inductance of the transformer are reduced; the boost output and the flyback output are stacked in series, so that a lossless absorption circuit is provided, the voltage stress is reduced, and leakage inductance energy is recovered; the inverter is alternately operated in a critical boost-flyback mode and an intermittent flyback mode in a half power frequency period, so that the inverter also has zero-voltage switching, zero-current switching, voltage reduction and low-switching frequency characteristics, and the conversion efficiency is improved and the high efficiency in a wide load range is realized.
Description
Technical Field
The invention relates to the technical field of power electronics and renewable energy grid-connected power generation, in particular to a coupling inductance dual-mode high-efficiency photovoltaic micro inverter.
Background
The miniature inverter type power generation system can realize maximum power point tracking at a component level, greatly improve the overall efficiency and the generated energy of a photovoltaic system, and simultaneously avoid the problems of wooden barrel effect and the like of the traditional inverter; the state of the component can be detected in real time, and the maintenance of the component and the system is convenient. Therefore, the method is widely applied to the field of distributed photovoltaic grid-connected power generation.
The existing flyback micro inverter is simple in topological structure and control strategy, but the inverter efficiency is difficult to further improve due to the fact that the turn ratio of a transformer is large and leakage inductance is high. The staggered parallel flyback inversion topological structure is adopted, so that current ripple is reduced, power density is improved, and leakage inductance is reduced on the premise of not reducing the turn ratio of the transformer, so that voltage stress of a switching tube is reduced, efficiency is improved to a certain extent, and obvious defects of excessive components, complex control and the like exist.
By adopting the voltage doubling rectification technology, the turn ratio of the flyback transformer is reduced on the premise of meeting the high-gain characteristic, and meanwhile, the leakage inductance is also reduced, however, the problem that the efficiency of the inverter still needs to be improved still exists.
Disclosure of Invention
The invention provides a coupling inductance double-mode high-efficiency photovoltaic micro-inverter, which aims to solve the problems that the voltage doubling rectification technology is not eliminated but only leakage inductance is reduced in the prior art, and the efficiency of the inverter still needs to be improved.
The aim of the invention can be achieved by the following technical scheme:
the coupling inductance dual-mode high-efficiency photovoltaic micro inverter comprises a main circuit and a control circuit, wherein the main circuit is connected with the control circuit and comprises n direct current converter units and a power frequency phase-change circuit; the n direct current converter units comprise n photovoltaic modules, n decoupling capacitors, n high-frequency transformers, 5n power switch tubes, n resonance capacitors and 2n filter capacitors, wherein n is a positive integer greater than or equal to 1.
The first end of the ith decoupling capacitor is connected with the first end of the ith photovoltaic module and the first input end of the primary winding of the ith transformer, the second end of the ith decoupling capacitor is connected with the second end of the ith photovoltaic module, the source of the ith 1 switch tube, the source of the ith 4 switch tube, the second end of the ith resonant capacitor and the second end of the ith 2 filter capacitor, so as to form the ith 2 output end of the ith direct current converter unit, the second input end of the primary winding of the ith transformer is connected with the drain of the ith 1 switch tube, the drain of the ith 5 switch tube and the drain of the ith 3 switch tube, the first end of the ith resonant capacitor is connected with the source of the ith 5 switch tube, the first output end of the ith transformer secondary winding is connected with the drain of the ith 2 switch tube, the first end of the ith transformer secondary winding is connected with the source of the ith 2 switch tube, the first end of the ith 1 filter capacitor is connected with the source of the ith 2 switch tube, so as to form the integral number of the ith output end of the ith direct current converter unit, and the ith output end of the ith filter tube is connected with the ith capacitor 1, the ith output end of the ith filter tube is connected with the ith filter tube, and the ith filter tube is connected with the first end of the ith filter tube.
The power frequency phase-change circuit comprises 4 power switching tubes, 1 filter capacitor and 1 filter inductor; sixth switch tube (S) 1 ) Is connected with the drain electrode of the fifth switch tube (S 2 ) Is connected to the drain of the power frequency commutation circuit to form a first input terminal, a sixth switching tube (S 1 ) Source and ninth switching tube (S) 4 ) A drain electrode of (C) and a third filter capacitor (C) f ) And a first filter inductance (L) f ) Is connected to the input of the first filter inductance (L f ) Is connected to the first end of the power network, a seventh switching tube (S 2 ) Source of (S) and eighth switch tube (S) 3 ) A drain electrode of (C) and a third filter capacitor (C) f ) Is connected with the second end of the power grid to form a second input end of the power frequency phase-change circuit.
Preferably, when the n dc converter units are connected in parallel, the 11 th output end is connected with the 21 st output end, and the n1 st output end of the same, and then is connected with the first input end of the power frequency phase-change circuit; the 12 th output end is connected with the 22 nd output end, the 32 nd output end and the n2 nd output end in the similar way, and is further connected with the second input end of the power frequency phase-change circuit, wherein n is a positive integer greater than or equal to 1.
Preferably, when the n dc converter units are connected in series, the 11 th output end is connected to the first input end of the power frequency commutation circuit, the 12 th output end is connected to the 21 st output end, the 22 nd output end is connected to the 31 st output end, the 32 nd output end is connected to the 41 st output end, and the (n-1) 2 nd output end is connected to the n1 st output end, the n2 nd output end is connected to the second input end of the power frequency commutation circuit, and n is a positive integer greater than or equal to 1.
Preferably, when n is equal to 1, the main circuit comprises a photovoltaic module (pv), a decoupling capacitor (C i ) A high-frequency transformer (T), nine power switching tubes (Q) 1 、Q 2 、Q 3 、Q 4 、Q 5 、S 1 、S 2 、S 3 And S is 4 ) A resonant capacitor (C s ) Three filter capacitors (C 1 、C 2 And C f ) And a filter inductance (L f )。
Preferably, the control circuit comprises a sampling circuit, a power frequency commutation drive circuit, a drive circuit and a digital controller, wherein the digital controller is respectively connected with the sampling circuit, the drive circuit and the power frequency commutation drive circuit.
Preferably, the sampling circuit needs to be added with (n-1) photovoltaic module (pv) voltage sampling circuits and (n-1) photovoltaic module (pv) current sampling circuits respectively, the driving circuit needs to be added with 5 (n-1) driving circuits of corresponding power switch tubes, the digital controller needs to be added with driving signals for generating 5 (n-1) corresponding power switch tubes, and n is a positive integer greater than or equal to 1.
Preferably, the coupling inductance dual-mode high-efficiency photovoltaic micro inverter alternately works in a temporary reverse lifting mode and a temporary reverse breaking mode in a half power frequency period; the temporary rising reverse mode and the breaking reverse mode realize smooth transition through the comparison of peak currents in the two modes; peak current in the two modes, namely current I obtained by a maximum power point tracking algorithm based on voltage and current sampling values of a photovoltaic module, voltage sampling value vi of the photovoltaic module and sampling absolute value v of grid voltage 0 And the phase angle theta of the grid voltage generated by the phase-locked loop is obtained by respective peak current algorithms.
Preferably, the coupling inductance dual-mode high-efficiency photovoltaic micro inverter adopts a composite control strategy of combining an OTC feedforward controller with a self-adaptive iterative learning controller; the OTC feedforward controller consists of a dieMaximum peak current i generated by the discrimination module p.max Voltage sampling value v of photovoltaic module i Obtained by means of a turn-on time algorithm.
Preferably, the sampled values of the network voltage are processed by a phase-locked loop, each producing a sixth switching tube (S 1 ) Seventh switch tube (S) 2 ) Eighth switching tube (S) 3 ) And a ninth switching tube (S 4 ) A power frequency driving signal of (2); the synchronous rectification controller acquires the information of the conduction of the diode body of the switching tube and the zero crossing of the secondary side current by sampling the drain-source voltage signal to respectively generate a second switching tube (Q) 2 ) And a third switching tube (Q) 3 ) Is provided.
Preferably, based on the generated high-frequency driving signal, the working state in the half power frequency period is as follows: when the inverter is operated in the temporary reverse mode, the fifth switching tube (Q 5 ) Long-pass, fourth switch tube (Q) 4 ) Long break, first switch tube (Q 1 ) Second switch tube (Q) 2 ) And a third switching tube (Q3) both operating in a high frequency state; when the inverter is operated in the off-mode, the fifth switching tube (Q 5 ) And a third switching tube (Q) 3 ) Are all long and are broken, a fourth switching tube (Q 4 ) Long-pass, first switch tube (Q 1 ) And a second switching tube (Q) 2 ) Operate at high frequency.
The beneficial effects of the invention are as follows: the boost inductor is coupled with the flyback primary side inductor, so that the gain of the converter is improved, the turn ratio and leakage inductance of the transformer are reduced, and the efficiency of the converter is improved; the two converters output a stack, inherently providing a lossless snubber circuit, reducing voltage stress, recovering leakage inductance energy; the boost output and the flyback output are stacked in series, so that a lossless absorption circuit is inherently provided, the voltage stress is reduced, and leakage inductance energy is recovered; the inverter is alternately operated in a critical boost-flyback (critical boost flyback) mode and an intermittent flyback (intermittent flyback) mode in a half power frequency period, so that the inverter also has the characteristics of zero voltage switch, zero current switch, buck, low switching frequency and the like, and the inverter is expected to realize high conversion efficiency and high efficiency in a wide load range.
Drawings
The present invention is further described below with reference to the accompanying drawings for the convenience of understanding by those skilled in the art.
Fig. 1-2 are main circuit diagrams and digital controller structural diagrams of the coupling inductance dual-mode high-efficiency photovoltaic micro inverter provided by the invention;
FIG. 3 is a block diagram of a composite controller of a coupled inductor dual mode high efficiency photovoltaic micro-inverter;
FIG. 4 is a diagram of the main operating waveforms in the half power frequency cycle of a coupled inductor dual mode high efficiency photovoltaic micro inverter;
FIG. 5 is a diagram of a reverse-mode, high-frequency operation waveform of a coupled inductor dual-mode high-efficiency photovoltaic micro-inverter;
FIGS. 6-10 are five mode diagrams of a coupled inductor dual mode high efficiency photovoltaic micro-inverter during a switching cycle when operating in a temporary reverse mode;
FIG. 11 is a topology of a one-ton parallel coupled inductive dual-mode high efficiency photovoltaic micro-inverter;
fig. 12 is a topology diagram of a one ton series coupled inductive dual mode high efficiency photovoltaic micro inverter.
Detailed Description
In order to further describe the technical means and effects adopted by the invention for achieving the preset aim, the following detailed description is given below of the specific implementation, structure, characteristics and effects according to the invention with reference to the attached drawings and the preferred embodiment.
Referring to fig. 1 and 2, the invention provides a coupled inductor dual-mode high-efficiency photovoltaic micro-inverter based on a virtual direct current bus structure, which is characterized in that a boost inductor and a flyback primary side inductor are coupled, a boost output and a flyback output are stacked in series, a working mode transition network is added, a composite control strategy of an OTC feedforward controller and a self-adaptive iterative learning controller and a synchronous rectification control strategy are adopted, and the coupled inductor dual-mode high-efficiency photovoltaic micro-inverter comprises a main circuit and a control circuit, wherein the main circuit comprises a photovoltaic component, a decoupling capacitor, a high-frequency transformer, nine power switching tubes, a resonant capacitor, three filter capacitors and a filter inductor. Decoupling capacitor C i Is connected with light at the first end ofA first end of the photovoltaic module pv, a first input end of a primary winding of the transformer T, an output end of the photovoltaic module pv, a second end of the photovoltaic module pv and a first switching tube Q 1 Source of fourth switch tube Q 4 Source electrode of (S) eighth switching tube 3 Source electrode of (S) and ninth switch tube S 4 Source, resonance capacitance C of (2) s A second end of (C), a second filter capacitor C 2 A second input end of the primary winding of the transformer T is connected with a fifth switch tube Q 5 Drain electrode of (a) first switch tube Q 1 And a third switching tube Q 3 The first end of the resonant capacitor Cs is connected with the fifth switch tube Q 5 A first output end of the secondary winding of the transformer T and a second input end of the primary winding of the transformer T form a homonymous end which is connected with a second switch tube Q 2 A first filter capacitor C connected to the drain electrode of the transistor 1 First and second switch tube Q 2 Source electrode of (S) sixth switching tube 1 Drain electrode of (d) and seventh switching tube S 2 Drain electrode connection of the third switch tube Q 3 Source electrode of (C) and fourth switch tube Q 4 Drain electrode of (C), first filter capacitor (C) 1 A second end of (C), a second filter capacitor C 2 A sixth switching tube S connected with the second output end of the secondary winding of the transformer T 1 Source electrode of (d) and ninth switch tube S 4 Drain electrode of (C), third filter capacitor (C) f And a filter inductance L f Is connected with the input end of the filter inductance L f The output end of the (c) is connected with the first end of the power grid, and a seventh switch tube S 2 Source electrode of (d) and eighth switching tube S 3 Drain electrode of (C), third filter capacitor (C) f Is connected to the second end of the power grid. The coupling inductance technology is adopted, so that the gain of the converter is improved, the turn ratio and leakage inductance of the transformer are reduced, and the efficiency of the converter is improved.
The control circuit of the coupling inductance dual-mode high-efficiency photovoltaic micro inverter comprises a sampling circuit, a power frequency phase-change driving circuit, a driving circuit and a digital controller: the sampling circuit comprises a power grid voltage sampling circuit, a power grid current sampling circuit, a photovoltaic module voltage sampling circuit and a photovoltaic module current sampling circuit; the power frequency phase-change driving circuit comprises a sixth switching tube S 1 Drive circuit of (d) and seventh switching tube S 2 Driving circuit of (a) eighth switching tube S 3 Drive circuit of (d) and ninth switching tube S 4 Is provided; the driving circuit comprises a first switch tube Q 1 Driving circuit of (a) second switching tube Q 2 Driving circuit of (d), third switching tube Q 3 Drive circuit of (a) fourth switching tube Q 4 Driving circuit of (d) and fifth switching tube Q 5 Is provided; the digital controller comprises a power grid voltage and current sampling module, a photovoltaic module voltage and current sampling module, a self-adaptive iterative learning controller module, an OTC feedforward controller module, a mode discrimination (critical inversion/broken inversion) module, a dual-mode peak current calculation module, a critical/intermittent mode controller module, a maximum power point tracking algorithm module, a synchronous rectification controller module, a power frequency commutation PWM module, an absolute value module and a phase-locked loop module.
For better understanding of the technical solution of the present invention, the working principle of the coupling inductance dual-mode high-efficiency photovoltaic micro-inverter will be clearly and completely described with reference to fig. 1 to 12, and it is obvious that the described embodiments are some, but not all, embodiments of the present invention. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
Referring to fig. 2, the coupling inductance dual-mode high-efficiency photovoltaic micro inverter alternately works in a temporary rising and reversing mode and a breaking and reversing mode in a half power frequency period, and smooth transition between the temporary rising and reversing mode and the breaking and reversing mode is realized by comparing peak currents in the two modes, wherein the peak current expression of the temporary rising and reversing mode is as follows
The peak current expression of the off-mode is
When i Temporary lifting and reversing ＞i Breaking and reversing When generating the fifth switch tube Q 5 Long-pass driving signal of (a), fourth switching tube Q 4 Long-break driving signal of (2) and release of third switching tube Q 3 The inverter works in the temporary reverse mode, otherwise, a fifth switch tube Q is generated 5 Long-break driving signal of fourth switching tube Q 4 Long-pass drive signal of (2) and third switching tube Q 3 And the long-break driving signal of (2) is operated in the break-make mode. Sampling values of the grid voltage are processed through a phase-locked loop to respectively generate sixth switching tubes S 1 Seventh switching tube S 2 Eighth switching tube S 3 And a ninth switching tube S 4 Is a power frequency drive signal. The synchronous rectification controller acquires the information of the conduction of the diode body of the switching tube and the zero crossing of the secondary side current by sampling the drain-source voltage signal to respectively generate a second switching tube Q 2 And a third switching tube Q 3 Is provided. Through peak current comparison of the two modes, transition between the temporary rising and breaking modes is smoothly realized, and high grid-connected current quality is ensured. Referring to fig. 3, the coupling inductance dual-mode high-efficiency photovoltaic micro inverter adopts a composite control strategy of an OTC feedforward controller and a self-adaptive iterative learning controller: the OTC feedforward controller pre-adjusts the on time, so that the anti-interference capability of the system is enhanced, and the control pressure of the self-adaptive iterative learning controller is relieved; the self-adaptive iterative learning controller works in the iterative learning control or the proportional resonance control in time according to the steady state or the dynamic state of the load, corrects the on time in real time, improves the control precision of the system and ensures the dynamic characteristic of the system. The adaptive iterative learning controller samples the grid current y(s) from the output and performs compensation with the compensated reference current i ref (s) comparing, and sending the obtained error value e(s) into an adaptive iterative learning controller to generate an output value u with the OTC feedforward controller f (s) adding, and feeding the obtained x(s) into the control object, i.e. generating the first switching tube Q by the critical/intermittent mode controller 1 Is provided. The reference current i ref The expression of(s) is
i ref (s)＝I·sinθ
In view of the filter capacitance C f The phase of the grid-connected current is delayed from the phase of the grid voltage, and the compensation current is introduced as
i c (s)＝V o ·ωC f ·cosθ
The compensated reference current i ref (s) is
i * ref (s)＝I·sinθ+V o ·ωC f ·cosθ
The expression of the OTC feedforward controller is
The self-adaptive iterative learning controller consists of an iterative learning controller and a proportional resonance controller, wherein the discrete expression of the iterative learning controller is as follows
u i+1 (k)＝u i (k)+k l e i (k+λ n )
Wherein k is l Is the gain of the learning controller lambda n Representing the phase advance order, and introducing a low-pass filter and a forgetting factor in practical application to improve the anti-interference performance and stability of the controller; the transfer function expression of the proportional resonance controller is
Wherein K is p Is a proportionality coefficient, K r Is the fundamental resonance coefficient omega 0 For fundamental angular frequency, omega i To take into account the bandwidth required by-3 dB, i.e. at ω 0 +ω i The gain of the resonance term was 0.707Kr. The OTC feedforward controller and the self-adaptive learning controller are adopted, so that the anti-interference capability and the dynamic response capability of the system are enhanced, and meanwhile, the stability of the system is ensured.
Referring to fig. 4, based on the driving signal generated as described above, the operating state of the coupling inductance dual-mode high-efficiency photovoltaic micro-inverter in the half power frequency period is described as follows:
when the inverter is operating in the temporary reverse mode, the fifth switching tube Q 5 Long-pass fourth switch tube Q 4 Long break, first switch tube Q 1 Second switch tube Q 2 And a third switching tube Q 3 All operate in a high frequency state; when the inverter works in the turn-off mode, the fifth switching tube Q 5 And a third switching tube Q 3 All are long and are broken, the fourth switch tube Q 4 Long-pass, first switch tube Q 1 And a second switching tube Q 2 Operate at high frequency. Depending on the positive or negative of the half power frequency period of the AC power grid, a sixth switching tube S 1 And a ninth switching tube S 4 Long on or long off, seventh switching tube S 2 And an eighth switching tube S 3 Long break or long pass. With the change of power, the interval of working in two modes is not fixed, and when full load, the inverter is mostly operated in the temporary reverse lifting mode, and only a small part of time is operated in the temporary reverse lifting mode, and with the reduction of power, the time of working in the temporary reverse lifting mode is gradually reduced, and the time of working in the temporary reverse lifting mode is gradually increased until the time of reducing to a certain critical power, and the temporary reverse lifting mode disappears, and the inverter is operated in the temporary reverse lifting mode in a half power frequency period.
Referring to fig. 5, when the coupled inductor dual-mode high-efficiency photovoltaic micro-inverter operates in the reverse-boost mode, one complete switching cycle includes five operating modes:
for simplicity of description and in accordance with the usual expressions in the art, reference numerals or letter designations of the elements referred to in the following description have the same meaning as those previously described, and unless otherwise indicated, the individual places are designated by numerals only without giving full cognizance to the elements, without affecting the understanding of the person skilled in the art; in addition, referring to fig. 6 to 10, for convenience of description of the working principle, the power frequency commutation circuit and the power grid in fig. 1 are equivalent to a direct current sinusoidal full wave (steamed bread wave) source.
t 0 ～t 1 ：t 0 At the moment, the main switch tube Q 1 In the on state, the input power starts to supply power to the exciting inductance L m And leakage inductance L s Charging, primary current i 1 With slope v i /(L m +L s ) From zero up to t 1 Time Q 1 The corresponding mode diagram is shown in fig. 6.
t 1 ～t 2 ：t 1 At the moment, the main switch tube Q 1 Switch off, exciting inductance L m Leakage inductance L s And a resonance capacitor C s The three are resonated, and the primary current i 1 Almost unchanged, main switch tube Q 1 The drain-source voltage gradually and linearly rises, the corresponding mode diagram is shown in FIG. 7, and the resonant frequency is
C s Slow down the switch tube Q 1 The rising slope of the drain-source voltage is
From the above, it can be seen that the resonant capacitor C s Is introduced to reduce Q 1 Drain-source voltage v ds To make Q 1 The zero-voltage turn-off characteristic is achieved, and turn-off loss is effectively reduced.
t 2 ～t 3 ：t 2 Time of day, switch tube Q 3 And Q 2 On, stored in the exciting inductance L m And leakage inductance L s Is released to the output. If neglecting leakage inductance L s Through a switching tube Q 3 And Q 2 At the same time with the same slope v c1 /(N 2 L m ) From i Temporary lifting and reversing /(n+1) decreases linearly until t 3 At the moment, pass through the switching tube Q 3 And Q 2 Is reduced to 0, Q 3 And Q 2 Turning off; as shown by the high frequency oscillation waveform in fig. 5, in fact, there isAt the beginning of the time interval, leakage inductance Ls and resonance capacitance C s And output capacitance C 2 High-frequency resonance can occur, leakage inductance energy is recycled to the output end, as shown in fig. 8, and v ds The spike voltage of (a) is also effectively suppressed.
t 3 ～t 4 ：t 3 At a time similar to mode 2, as shown in FIG. 9, the resonance capacitance C s And excitation inductance L m And leakage inductance L s Resonance occurs, main switch tube Q 1 Drain-source voltage v ds Gradually attenuate, if v 0 And v i Satisfy the following requirements
v 0 >(N+2)v i
v ds Can be at t 4 Time decay is 0, the time interval, t 34 Can be expressed as
To ensure zero voltage soft switching, the delay time should be greater than t 34 。
t 4 ～t 5 ：t 4 After the moment, as shown in fig. 10, the primary current i 1 Reverse flow through main switching tube Q 1 V of the body diode ds Is clamped to 0, and then a driving signal is added to realize Q 1 Zero voltage on, t 5 At that point, the inverter enters the next switching cycle.
The one-ton parallel-type coupled inductor dual-mode high-efficiency photovoltaic micro-inverter shown in fig. 11, and the one-ton serial-type coupled inductor dual-mode high-efficiency photovoltaic micro-inverter shown in fig. 12 adopt a control strategy and basic working principle similar to the processes of the embodiments shown in fig. 1-2-6-10.
The coupling inductance technology is adopted, so that the gain of the converter is improved, the turn ratio and leakage inductance of the transformer are reduced, and the efficiency of the converter is improved; the two converters output a stack, inherently providing a lossless snubber circuit, reducing voltage stress, recovering leakage inductance energy; the temporary lifting reverse mode is adopted, so that a zero-voltage soft switch and a zero-current soft switch are provided, and the switching loss of the inverter is reduced; the switching frequency is fixed to a certain low constant frequency when the (instantaneous) power is low, the extremely high switching frequency caused by the temporary lifting reverse mode is eliminated, and the high efficiency of a wide load range is optimized. Through peak current comparison of the two modes, transition between the temporary rising and breaking modes is smoothly realized, and high grid-connected current quality is ensured. The critical/intermittent mode controller is realized based on the on-time control, a high-frequency current transformer inherent to peak current control is eliminated, the signal-to-noise ratio of a control signal is reduced, and the cost is saved. The OTC feedforward controller and the self-adaptive learning controller are adopted, so that the anti-interference capability and the dynamic response capability of the system are enhanced, and meanwhile, the stability of the system is ensured. And the synchronous rectification technology is adopted, so that the bidirectional flow of energy is realized, and the development requirement of a future intelligent power grid is met. The adopted one-support-n parallel or series topological structure breaks through the technical bottleneck of the traditional virtual direct current bus, realizes the free expansion of the power of the inverter, further improves the efficiency of the inverter and reduces the manufacturing cost of unit power.
The present invention is not limited to the above embodiments, but is capable of modification and variation in detail, and other modifications and variations can be made by those skilled in the art without departing from the scope of the present invention.
Claims (5)
1. The coupling inductance dual-mode high-efficiency photovoltaic micro inverter is characterized by comprising a main circuit and a control circuit, wherein the main circuit is connected with the control circuit and comprises n direct current converter units and a power frequency phase-change circuit; the n direct current converter units comprise n photovoltaic modules, n decoupling capacitors, n high-frequency transformers, 5n power switch tubes, n resonance capacitors and 2n filter capacitors, wherein n is a positive integer greater than or equal to 1; the first end of the ith decoupling capacitor is connected with the first end of the ith photovoltaic module and the first input end of the primary winding of the ith transformer, the second end of the ith decoupling capacitor is connected with the second end of the ith photovoltaic module, the source electrode of the ith 1 switch tube, the source electrode of the ith 4 switch tube, the second end of the ith resonant capacitor and the second end of the ith 2 filter capacitor to form the ith 2 output end of the ith direct current converter unit, the second input end of the primary winding of the ith transformer is connected with the drain electrode of the ith 1 switch tube, the drain electrode of the ith 5 switch tube and the drain electrode of the ith 3 switch tube, the first end of the ith resonant capacitor is connected with the source electrode of the ith 5 switch tube, the first output end of the ith transformer secondary winding and the second input end of the ith transformer primary winding form the same name end, the first output end of the ith transformer secondary winding is connected with the drain electrode of the ith 2 switch tube, the first end of the ith 1 filter capacitor is connected with the source electrode of the ith 2 switch tube to form the ith direct current converter unit, and the first end of the ith filter capacitor is connected with the ith output end of the ith capacitor 1, the ith filter tube is connected with the first end of the ith filter tube, and the ith capacitor is connected with the first end of the ith capacitor 1 and the ith capacitor to the positive end of the ith capacitor and the ith capacitor is connected with the first end of the capacitor and is connected to the first end of the capacitor is connected to the capacitor to the ith capacitor;
the power frequency phase-change circuit comprises 4 power switching tubes, 1 filter capacitor and 1 filter inductor; sixth switch tube (S) 1 ) Is connected with the drain electrode of the fifth switch tube (S 2 ) Is connected to the drain of the power frequency commutation circuit to form a first input terminal, a sixth switching tube (S 1 ) Source and ninth switching tube (S) 4 ) A drain electrode of (C) and a third filter capacitor (C) f ) And a first filter inductance (L) f ) Is connected to the input of the first filter inductance (L f ) Is connected to the first end of the power network, a seventh switching tube (S 2 ) Source of (S) and eighth switch tube (S) 3 ) A drain electrode of (C) and a third filter capacitor (C) f ) Is connected with the second end of the power grid to form a second input end of the power frequency phase-change circuit;
wherein,
when the n direct current converter units are connected in parallel, the 11 th output end is connected with the 21 st output end and the n1 st output end in the similar way, and then is connected with the first input end of the power frequency phase-change circuit; the 12 th output end is connected with the 22 nd output end, the 32 nd output end and the n2 nd output end of the same type, and is further connected with the second input end of the power frequency phase-change circuit;
when the n direct current converter units are connected in series, an 11 th output end is connected with a first input end of the power frequency phase-change circuit, a 12 th output end is connected with a 21 st output end, a 22 nd output end is connected with a 31 st output end, a 32 nd output end is connected with a 41 st output end, and the like, (n-1) 2 is connected with an n1 st output end, and an n2 nd output end is connected with a second input end of the power frequency phase-change circuit;
the coupling inductance dual-mode high-efficiency photovoltaic micro inverter alternately works in a temporary reverse lifting mode and a temporary reverse breaking mode in a half power frequency period; the temporary rising reverse mode and the breaking reverse mode realize smooth transition through the comparison of peak currents in the two modes; peak current in the two modes, namely current I obtained by a maximum power point tracking algorithm based on voltage and current sampling values of a photovoltaic module, voltage sampling value vi of the photovoltaic module and sampling absolute value v of grid voltage 0 And the phase angle theta of the grid voltage generated by the phase-locked loop is obtained by respective peak current algorithms;
the sampled values of the network voltage are processed by a phase-locked loop to generate a sixth switching tube (S 1 ) Seventh switch tube (S) 2 ) Eighth switching tube (S) 3 ) And a ninth switching tube (S 4 ) A power frequency driving signal of (2); the synchronous rectification controller acquires the information of the conduction of the diode body of the switching tube and the zero crossing of the secondary side current by sampling the drain-source voltage signal to respectively generate a second switching tube (Q) 2 ) And a third switching tube (Q) 3 ) Is a high frequency drive signal of (a);
based on the generated high-frequency driving signal, the working state in the half power frequency period is as follows: when the inverter is operated in the temporary reverse mode, the fifth switching tube (Q 5 ) Long-pass, fourth switch tube (Q) 4 ) Long break, first switch tube (Q 1 ) Second switch tube (Q) 2 ) And a third switching tube (Q3) both operating in a high frequency state; when the inverter is operated in the off-mode, the fifth switching tube (Q 5 ) And a third switching tube (Q) 3 ) Are all long and are broken, a fourth switching tube (Q 4 ) Long-pass, first switch tube (Q 1 ) And a second switching tube (Q) 2 ) All operate in a high frequency state;
wherein,
the control circuit of the coupling inductance dual-mode high-efficiency photovoltaic micro inverter comprises a sampling circuit, a power frequency phase-change driving circuit, a driving circuit and a digital controller: the sampling circuit comprises a power grid voltage sampling circuit, a power grid current sampling circuit, a photovoltaic module voltage sampling circuit and a photovoltaic module current sampling circuit; the power frequency phase-change driving circuit comprises a sixth switching tube S 1 Drive circuit of (d) and seventh switching tube S 2 Driving circuit of (a) eighth switching tube S 3 Drive circuit of (d) and ninth switching tube S 4 Is provided; the driving circuit comprises a first switch tube Q 1 Driving circuit of (a) second switching tube Q 2 Driving circuit of (d), third switching tube Q 3 Drive circuit of (a) fourth switching tube Q 4 Driving circuit of (d) and fifth switching tube Q 5 Is provided; the digital controller comprises a power grid voltage and current sampling module, a photovoltaic module voltage and current sampling module, a self-adaptive iterative learning controller module, an OTC feedforward controller module, a mode judging module, a dual-mode peak current calculating module, a critical/intermittent mode controller module, a maximum power point tracking algorithm module, a synchronous rectification controller module, a power frequency commutation PWM module, an absolute value module and a phase-locked loop module.
2. The coupled inductor dual-mode high efficiency photovoltaic micro-inverter of claim 1, wherein when n is equal to 1, the main circuit comprises a photovoltaic module (pv), a decoupling capacitor (C i ) A high-frequency transformer (T), nine power switching tubes (Q) 1 、Q 2 、Q 3 、Q 4 、Q 5 、S 1 、S 2 、S 3 And S is 4 ) A resonant capacitor (C s ) Three filter capacitors (C 1 、C 2 And C f ) And a filter inductance (L f )。
3. The coupled inductor dual-mode high-efficiency photovoltaic micro-inverter according to claim 1, wherein the control circuit comprises a sampling circuit, a power frequency commutation drive circuit, a drive circuit and a digital controller, and the digital controller is respectively connected with the sampling circuit, the drive circuit and the power frequency commutation drive circuit.
4. The coupling inductance dual-mode high-efficiency photovoltaic micro-inverter according to claim 3, wherein the sampling circuits are added with (n-1) photovoltaic module (pv) voltage sampling circuits and (n-1) photovoltaic module (pv) current sampling circuits respectively, the driving circuits are added with 5 (n-1) driving circuits of corresponding power switching tubes, and the digital controller is added with driving signals for generating 5 (n-1) corresponding power switching tubes.
5. The coupled inductor dual-mode high-efficiency photovoltaic micro-inverter of claim 1, wherein the coupled inductor dual-mode high-efficiency photovoltaic micro-inverter adopts a composite control strategy of combining an OTC feedforward controller with an adaptive iterative learning controller; the OTC feedforward controller generates maximum peak current i by a mode discrimination module p.max Voltage sampling value v of photovoltaic module i Obtained by means of a turn-on time algorithm.
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