CN116805882A - Processing method for signal amplitude exceeding AD range of receiver - Google Patents
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Abstract
The application discloses a processing method for a receiver with signal amplitude exceeding an AD range, which solves the problems of the over-range and signal distortion. The method comprises the following steps: setting a digital control attenuator at the front end of an AD sampling module, setting the attenuation of the digital control attenuator to zero, collecting a single-carrier analog signal, converting the analog signal into a digital signal through AD sampling, and converting the digital signal from a real number domain to a complex number domain by adopting Hilbert transformation in a digital signal processor to obtain a complex number domain signal; obtaining an amplitude value corresponding to the complex domain signal by adopting a rotation vector method; if the amplitude value exceeds a preset amplitude region in the digital processor, carrying out attenuation control until the amplitude value is in the preset amplitude region or reaches the maximum attenuation. The application has the advantages of simple logic, less calculation workload, accuracy, reliability and the like, and has high practical value and popularization value in the technical field of ADC sampling processing.
Description
Technical Field
The application relates to the technical field of ADC sampling processing, in particular to a processing method for a receiver with signal amplitude exceeding an AD range.
Background
In receiver AD sampling, a low noise amplifier is typically added to the system in order to provide the system with a greater signal-to-noise ratio when the signal amplitude processed by the system varies with time and geographic location. The method also increases the risk that the signal of the system exceeds the ADC range, so that the sampled signal is in a distortion state. In order to make a large signal in the ADC range, a digital control attenuator is usually added, then the signal is coupled and detected, and the attenuator is controlled to attenuate the signal properly according to the detected state, so that the method needs to increase extra hardware cost.
In the application of China, with the patent publication number of CN113114245A, named as an over-range input and incoherent sampling signal recovery method in ADC parameter test, the method comprises the following steps: firstly, the frequency domain information of the output signal of the tested ADC is utilized to estimate the measurement period, amplitude, initial phase and direct current component of the tested ADC, then the truncated output signal is subjected to first reconstruction and truncated processing to obtain a reconstructed truncated output signal, the truncated output signal of the first reconstruction is subtracted from the output signal of the tested ADC, the amplitude error is estimated based on the residual signal, then the truncated output signal is subjected to second reconstruction and truncated processing to obtain a second reconstructed truncated output signal, and the truncated output signal of the second reconstruction in the output signal of the tested ADC is replaced by an incoherent sampling output signal, so that the incoherent sampling signal can be recovered to obtain a coherent sampling signal. The technology adopts discrete Fourier transform and estimates the sampling period of the ADC to be tested, and utilizes a three-parameter sine fitting method to jointly estimate the amplitude, the initial phase and the direct current component of the output signal.
Therefore, it is urgently needed to provide a single carrier signal amplitude out-of-AD range processing method which is simple in logic, small in calculation workload, accurate and reliable.
Disclosure of Invention
In view of the above problems, the present application aims to provide a processing method for a receiver with signal amplitude exceeding an AD range, and the technical scheme adopted by the present application is as follows:
the processing method for the signal amplitude of the receiver exceeding the AD range adopts a numerical control attenuator, an AD sampling module and a digital signal processor which are connected in sequence; the digital signal processor is in feedback connection with the numerical control attenuator, and the method comprises the following steps:
setting the attenuation of the numerical control attenuator to zero;
acquiring a single-carrier analog signal, and converting the single-carrier analog signal into a digital signal through an AD sampling module; converting the digital signal from the real number domain to the complex number domain by using Hilbert transform in the digital signal processor to obtain a complex number domain signal;
obtaining an amplitude value corresponding to the complex domain signal by adopting a rotation vector method;
if the amplitude value exceeds a preset amplitude region in the digital signal processor, carrying out attenuation control until the amplitude value is in the preset amplitude region or reaches the maximum attenuation.
Further, the single carrier analog signal is a cosine wave function expressed as:
wherein K represents an overscan coefficient; a represents the signal amplitude value of ADC at full scale; f represents frequency; t represents time;representing the input single carrier time domain signal.
Further, when the absolute value of the overscan coefficient K is larger than 1, the single carrier signal exceeds the ADC range; when the absolute value of the overscan coefficient K is smaller than 1, the carrier signal is in the ADC range; and when the absolute value of the overscan coefficient K is equal to 1, the single carrier signal is ADC full-scale.
Further, the processing method for the signal amplitude exceeding the AD range of the receiver further comprises the following steps:
presetting an initial value larger than 1 for an overscan coefficient K, and sampling a single carrier signal by using an AD sampling module to obtain a time domain signal;
conversion of a time domain signal from the real domain to the complex domain in the digital domain using a Hilbert transformThe expression of (2) is:
wherein e represents the base of natural logarithms; omega represents an angular frequency;representing imaginary units.
Further, the Hilbert transform is adopted to convert the time domain signal from the real number domain to the complex number domain, and the converted expression is:
wherein,,a frequency domain signal representing an input single carrier; />Representing frequency domain signals of an input single carrierThe frequency domain signal after Hilbert transform.
Further, the processing method for the signal amplitude exceeding the AD range of the receiver further comprises the following steps:
let the time domain signal of the input time domain signal of the single carrier signal after Hilbert transform be:
；
forming a complex domain signal according to the time domain signal after the input time domain signal is subjected to Hilbert transformation and the input time domain signal, and analyzing the complex domain signal; the expression of the complex domain signal is:
。
further, the method for obtaining the amplitude value corresponding to the complex domain signal by adopting the rotation vector method comprises the following steps:
iterative calculation is carried out by adopting a rotation coordinate method to obtain an amplitude value and an angle value of the signal; the expression of the rotation coordinate method is as follows:
wherein,,indicating that the complex domain signal is at +.>Real part value of time; />Indicating that the complex domain signal is at +.>An imaginary value of the time; />Indicating that the complex domain signal is at +.>Real part value after time rotation; />Indicating that the complex domain signal is at +.>The imaginary value after the moment rotation; />Indicating the angle of rotation.
Compared with the prior art, the application has the following beneficial effects:
(1) According to the application, the front end of the AD sampling module is provided with the numerical control attenuator, the numerical control attenuator is utilized to obtain the single carrier signal, the conversion from the real number domain to the complex number domain is adopted in the digital domain by adopting the Hilbert conversion to obtain the complex number domain signal, the real number signal only needs to pass through one Hilbert FIR filter, the system is simple, and the occupied amount of hardware resources is small.
(2) The application adopts a rotation vector method to obtain the amplitude value corresponding to the complex domain signal, compares the amplitude value with a preset amplitude region, continuously adjusts the attenuation quantity of the numerical control attenuator, repeatedly carries out Hilbert transformation on the sampled time domain signal to obtain a complex domain analysis signal, and adopts the rotation vector method to obtain the amplitude value of the complex domain analysis signal so that the calculated amplitude value is lower than the full-scale state of the ADC, and completes the amplitude control of the signal. The advantage is that a particular rotation angle can be chosen such that the tangent of the angle is such thatWherein i is a positive integer from 0 to 15, and comprises 0 and 15. Thus, the trigonometric function calculation which is needed to be performed originally is changed into simple shift operation. The whole rotation vector calculation only comprises the operation of shift addition and the multiplication operation of the last amplitude compensation factor, thereby greatly reducing the calculation complexity. Furthermore, the application can obtain a high-precision calculated value by only 16 times of rotation, and finally obtain +.>The sum of the 16 rotation angles is the angle value, which is the required amplitude value.
In conclusion, the method has the advantages of simple logic, less calculation workload, accuracy, reliability and the like, and has high practical value and popularization value in the technical field of ADC sampling processing.
Drawings
For a clearer description of the technical solutions of the embodiments of the present application, the drawings to be used in the embodiments will be briefly described below, it being understood that the following drawings only illustrate some embodiments of the present application and should not be considered as limiting the scope of protection, and other related drawings may be obtained according to these drawings without the need of inventive effort for a person skilled in the art.
FIG. 1 is a logic flow diagram of the present application.
Fig. 2 is a schematic diagram of the present application.
FIG. 3 is a schematic diagram of overscan sampling in the present application.
FIG. 4 is a diagram of a complex domain analysis signal according to the present application.
Fig. 5 is a graph comparing the signal modulation before and after the signal modulation in the present application.
Description of the embodiments
For the purpose of making the objects, technical solutions and advantages of the present application more apparent, the present application will be further described with reference to the accompanying drawings and examples, which include, but are not limited to, the following examples. All other embodiments, which can be made by those skilled in the art based on the embodiments of the application without making any inventive effort, are intended to be within the scope of the application.
In this embodiment, the term "and/or" is merely an association relationship describing the association object, and indicates that three relationships may exist, for example, a and/or B may indicate: a exists alone, A and B exist together, and B exists alone.
The terms first and second and the like in the description and in the claims of the present embodiment are used for distinguishing between different objects and not for describing a particular sequential order of objects. For example, the first target object and the second target object, etc., are used to distinguish between different target objects, and are not used to describe a particular order of target objects.
In embodiments of the application, words such as "exemplary" or "such as" are used to mean serving as an example, instance, or illustration. Any embodiment or design described herein as "exemplary" or "e.g." in an embodiment should not be taken as preferred or advantageous over other embodiments or designs. Rather, the use of words such as "exemplary" or "such as" is intended to present related concepts in a concrete fashion.
In the description of the embodiments of the present application, unless otherwise indicated, the meaning of "a plurality" means two or more. For example, the plurality of processing units refers to two or more processing units; the plurality of systems means two or more systems.
As shown in fig. 1 to 5, the present embodiment provides a processing method for a receiver with a signal amplitude exceeding the AD range, which requires only one digital attenuator. The system adopts a numerical control attenuator, an AD sampling module and a digital signal processor which are sequentially connected, and the digital signal processor is connected with the numerical control attenuator in a feedback way. When the ADC samples an input signal, the conversion of the signal from a real number domain to a complex number domain is realized by using Hilbert transformation in a digital domain, and the amplitude value of the signal is obtained by a rotation vector method through the complex number signal. And if the amplitude value exceeds the set amplitude region, performing attenuation control until the amplitude requirement is met or the maximum attenuation is reached. In addition, it should be noted that, in this embodiment, the same time domain signal and frequency domain signal of a single carrier are in a corresponding relationship, and their conversion between each other belongs to a conventional technical means in the art, and the conversion process thereof will not be described herein.
Specifically:
first, the attenuation of the numerical control attenuator is set to zero in the initial stage.
Step two, acquiring a single-carrier analog signal, and converting the single-carrier analog signal into a digital signal through an AD sampling module; the digital signal is converted from real number domain to complex number domain by Hilbert transform in the digital signal processor to obtain complex number domain signal.
Wherein, take single carrier analog signal as the input signal, let the input signal be cosine wave function, it expresses as:
wherein K represents an overscan coefficient; a represents the signal amplitude value of ADC at full scale; f represents frequency; t represents time.
In this embodiment, when the absolute value of the overscan coefficient K is greater than 1, the single carrier signal exceeds the ADC range, when the absolute value of the overscan coefficient K is less than 1, the carrier signal is in the ADC range, and when the absolute value of the overscan coefficient K is equal to 1, the single carrier signal is the ADC full range.
At the beginning, an initial value larger than 1 is preset for the overscan coefficient K, and an AD sampling module is utilized to sample the single carrier signal, so that a time domain signal is obtained. In this embodiment, the overscan coefficient K is set to 1.3.
Third, the conversion of the time domain signal from the real domain to the complex domain is performed in the digital domain using a Hilbert transform, said Hilbert transformThe expression of (2) is:
wherein e represents the base of natural logarithms; omega represents an angular frequency;representing imaginary units.
Let the time domain signal of the input time domain signal of the single carrier signal after Hilbert transform be:
；
forming a complex domain signal according to the time domain signal after the input time domain signal is subjected to Hilbert transformation and the input time domain signal, and analyzing the complex domain signal; the expression of the complex domain signal is:
。
in this embodiment, the analysis result is shown in fig. 4.
And fourthly, calculating the amplitude value of the complex domain analysis signal by using a rotation vector method, and calculating the amplitude value and the angle value of the signal by using the rotation vector method through a rotation coordinate method with limited times. The rotation vector method can reduce the calculation amount by performing specific value on the rotation angle, so that only a small amount of addition and subtraction and shift operations are needed to replace complex trigonometric function operations.
And fifthly, judging through the calculated amplitude of the rotation vector, continuously adjusting the attenuation quantity (the overscan coefficient K (variable) in the first step) of the numerical control attenuator, repeating the third step and the fourth step, so that the calculated amplitude value is lower than the full-scale state of the ADC, and finishing the amplitude control of the signal, wherein the signals before and after adjustment are shown in figure 5.
By the technical scheme, the problems of overrange and signal distortion can be solved by adding only one digital control attenuator, and compared with the prior art, the application has outstanding substantive characteristics and remarkable progress, and has high practical value and popularization value in the technical field of ADC sampling processing.
The above embodiments are only preferred embodiments of the present application and are not intended to limit the scope of the present application, but all changes made by adopting the design principle of the present application and performing non-creative work on the basis thereof shall fall within the scope of the present application.
Claims (7)
1. The processing method for the signal amplitude exceeding the AD range of the receiver is characterized by adopting a numerical control attenuator, an AD sampling module and a digital signal processor which are connected in sequence; the digital signal processor is in feedback connection with the numerical control attenuator, and the method comprises the following steps:
setting the attenuation of the numerical control attenuator to zero;
acquiring a single-carrier analog signal, and converting the single-carrier analog signal into a digital signal through an AD sampling module; converting the digital signal from the real number domain to the complex number domain by using Hilbert transform in the digital signal processor to obtain a complex number domain signal;
obtaining an amplitude value corresponding to the complex domain signal by adopting a rotation vector method;
if the amplitude value exceeds a preset amplitude region in the digital signal processor, carrying out attenuation control until the amplitude value is in the preset amplitude region or reaches the maximum attenuation.
2. The method for processing the signal amplitude exceeding the AD range of the receiver according to claim 1, wherein the single carrier analog signal is a cosine wave function expressed as:
the method comprises the steps of carrying out a first treatment on the surface of the Wherein K represents an overscan coefficient; a represents the signal amplitude value of ADC at full scale; f represents frequency; t represents time; />Representing the input single carrier time domain signal.
3. The method for processing the signal amplitude exceeding the AD range of the receiver according to claim 2, wherein when the absolute value of the overscan coefficient K is greater than 1, the single carrier signal exceeds the ADC range; when the absolute value of the overscan coefficient K is smaller than 1, the carrier signal is in the ADC range; and when the absolute value of the overscan coefficient K is equal to 1, the single carrier signal is ADC full-scale.
4. The method for processing the signal amplitude exceeding the AD range for the receiver according to claim 2, further comprising:
presetting an initial value larger than 1 for an overscan coefficient K, and sampling a single carrier signal by using an AD sampling module to obtain a time domain signal;
conversion of a time domain signal from the real domain to the complex domain in the digital domain using a Hilbert transformThe expression of (2) is:
the method comprises the steps of carrying out a first treatment on the surface of the Wherein e represents the base of natural logarithms; omega represents an angular frequency; />Representing imaginary units.
5. The method for processing the signal amplitude exceeding the AD range for a receiver according to claim 4, wherein the conversion of the time domain signal from the real domain to the complex domain by using Hilbert transform is performed by the following expression:
the method comprises the steps of carrying out a first treatment on the surface of the Wherein (1)>A frequency domain signal representing an input single carrier; />Frequency domain signal representing input single carrier>The frequency domain signal after Hilbert transform.
6. The method for processing the signal amplitude exceeding the AD range for the receiver as claimed in claim 5, further comprising:
let the time domain signal of the input time domain signal of the single carrier signal after Hilbert transform be:
；
forming a complex domain signal according to the time domain signal after the input time domain signal is subjected to Hilbert transformation and the input time domain signal, and analyzing the complex domain signal; the expression of the complex domain signal is:
。
7. the method for processing the signal amplitude exceeding the AD range for a receiver according to claim 6, wherein obtaining the amplitude value corresponding to the complex domain signal by using a rotation vector method comprises:
iterative calculation is carried out by adopting a rotation coordinate method to obtain an amplitude value and an angle value of the signal; the expression of the rotation coordinate method is as follows:
the method comprises the steps of carrying out a first treatment on the surface of the Wherein (1)>Indicating that the complex domain signal is at +.>Real part value of time; />Indicating that the complex domain signal is at +.>An imaginary value of the time; />Indicating that the complex domain signal is at +.>Real part value after time rotation; />Indicating that the complex domain signal is at +.>The imaginary value after the moment rotation; />Indicating the angle of rotation.
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|---|---|---|---|---|
| CN117674752A (en) * | 2023-10-19 | 2024-03-08 | 四川鸿创电子科技有限公司 | Automatic gain control method, device and equipment for frequency agile chip |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20060066290A1 (en) * | 2004-09-27 | 2006-03-30 | Reiner Hausdorf | Method and apparatus for zero-mixing spectrum analysis with Hilbert transform |
| CN112235055A (en) * | 2020-03-27 | 2021-01-15 | 中国人民解放军海军工程大学 | Heterodyne self-adaptive interference cancellation device based on digital Hilbert transform |
| CN112564816A (en) * | 2020-11-04 | 2021-03-26 | 中山大学 | Single sideband signal recovery algorithm based on time domain iteration |
| CN115913231A (en) * | 2023-01-06 | 2023-04-04 | 上海芯炽科技集团有限公司 | Digital estimation method for sampling time error of TIADC |
| CN116346148A (en) * | 2023-03-14 | 2023-06-27 | 电子科技大学 | Multi-mode automatic gain control method and system based on SoC |
-
2023
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Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20060066290A1 (en) * | 2004-09-27 | 2006-03-30 | Reiner Hausdorf | Method and apparatus for zero-mixing spectrum analysis with Hilbert transform |
| CN112235055A (en) * | 2020-03-27 | 2021-01-15 | 中国人民解放军海军工程大学 | Heterodyne self-adaptive interference cancellation device based on digital Hilbert transform |
| CN112564816A (en) * | 2020-11-04 | 2021-03-26 | 中山大学 | Single sideband signal recovery algorithm based on time domain iteration |
| CN115913231A (en) * | 2023-01-06 | 2023-04-04 | 上海芯炽科技集团有限公司 | Digital estimation method for sampling time error of TIADC |
| CN116346148A (en) * | 2023-03-14 | 2023-06-27 | 电子科技大学 | Multi-mode automatic gain control method and system based on SoC |
Non-Patent Citations (7)
| Title |
|---|
| CSDN博客园作者ZD0303: "希尔伯特变换简介", Retrieved from the Internet <URL:https://blog.csdn.net/zd0303/article/details/82996134> * |
| CSDN博客园作者碎碎思: "CORDIC算法详解(一)-CORDIC 算法之圆周系统之旋转模式", Retrieved from the Internet <URL:https://blog.csdn.net/Pieces_thinking/article/details/83512820> * |
| LAM ANH BUI; ARNAN MITCHELL: "All optical instantaneous frequency measurement incorporating optical Hilbert transformer", 《2012 IEEE INTERNATIONAL TOPICAL MEETING ON MICROWAVE PHOTONICS》, pages 323 - 326 * |
| 史永彬; 于蒙: "VM-7衰减校准系统的量程拓展方法研究", 《仪器仪表标准化与计量》, pages 39 - 41 * |
| 知乎网友HSUTY: "希尔伯特变换详解 (the Hilbert transform)", Retrieved from the Internet <URL:https://zhuanlan.zhihu.com/p/609586133> * |
| 知乎网友纸上谈芯: "老生常谈CORDIC算法", Retrieved from the Internet <URL:https://zhuanlan.zhihu.com/p/433076197> * |
| 美信集成产品公司: "如何在宽带通信接收机中合理选择ADC", 《电子技术应用》, no. 1, pages 141 - 142 * |
Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN117674752A (en) * | 2023-10-19 | 2024-03-08 | 四川鸿创电子科技有限公司 | Automatic gain control method, device and equipment for frequency agile chip |
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