CN114614839B - Multichannel Ka wave band front end subassembly - Google Patents
Multichannel Ka wave band front end subassembly Download PDFInfo
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- CN114614839B CN114614839B CN202210212639.0A CN202210212639A CN114614839B CN 114614839 B CN114614839 B CN 114614839B CN 202210212639 A CN202210212639 A CN 202210212639A CN 114614839 B CN114614839 B CN 114614839B
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/005—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission adapting radio receivers, transmitters andtransceivers for operation on two or more bands, i.e. frequency ranges
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
- H04B1/40—Circuits
- H04B1/403—Circuits using the same oscillator for generating both the transmitter frequency and the receiver local oscillator frequency
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04B—TRANSMISSION
- H04B1/00—Details of transmission systems, not covered by a single one of groups H04B3/00 - H04B13/00; Details of transmission systems not characterised by the medium used for transmission
- H04B1/38—Transceivers, i.e. devices in which transmitter and receiver form a structural unit and in which at least one part is used for functions of transmitting and receiving
- H04B1/40—Circuits
- H04B1/50—Circuits using different frequencies for the two directions of communication
- H04B1/52—Hybrid arrangements, i.e. arrangements for transition from single-path two-direction transmission to single-direction transmission on each of two paths or vice versa
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02D—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN INFORMATION AND COMMUNICATION TECHNOLOGIES [ICT], I.E. INFORMATION AND COMMUNICATION TECHNOLOGIES AIMING AT THE REDUCTION OF THEIR OWN ENERGY USE
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- Y02D30/70—Reducing energy consumption in communication networks in wireless communication networks
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Abstract
The invention discloses a multichannel Ka waveband front end component, which specifically comprises: the radio frequency circuit comprises four radio frequency circuits which are the same, and four intermediate frequency circuits which are the same and are formed by four intermediate frequency circuits, wherein the radio frequency circuits and the intermediate frequency circuits are connected in series in a one-to-one correspondence manner; the self-checking one-to-four power distribution network is respectively connected to the coupling ends of the couplers in the four-path radio frequency circuit, so that the self-checking function of the component is realized; the local oscillator one-to-four power distribution network is respectively connected to local oscillator ends of the frequency mixers in the four-path radio frequency circuit to provide local oscillator signals required by component frequency mixing. According to the Ka-band front-end component, a millimeter-wave broadband frequency mixing technology is adopted, millimeter-wave band signals are mixed to a low-frequency band, a noise baseline is more stable by adopting an SDLVA technology, a temperature compensation attenuator and a baseline compensation unit are added, and the influence of temperature on the performance of the component is reduced; the interior of the component adopts the micro-assembly and electric fitting mixed assembly process, and the component has the characteristics of high sensitivity, large dynamic, stable full-temperature characteristic, small volume, low assembly requirement and the like.
Description
Technical Field
The invention belongs to the technical field of microwave and millimeter waves, and particularly relates to a multichannel Ka-band front-end component.
Background
With the application of modern radar technology, electronic countermeasure faces more complicated and changeable electromagnetic environment, and millimeter waves are widely applied to systems such as precise guided weapons and various aircrafts due to the frequency band characteristics of the millimeter waves. In a complex electromagnetic environment, external radiation is sorted out for analysis and identification, and an alarm can be given out accurately without error, which is a very complex and difficult task. Compared with one of the direction-finding technologies based on the amplitude direction-finding technology, the direction-finding technology has higher interception probability in the azimuth dimension than the phase direction-finding technology. Meanwhile, wide opening can be carried out in a frequency domain, the instantaneous bandwidth is very wide, the equipment is relatively simple, various platforms are easy to transplant, and the method is widely applied to modern reconnaissance alarm equipment. As the front end of a millimeter wave amplitude-comparison direction-finding system, a traditional Ka-band front end component usually uses a coaxial detector, has large volume, is not beneficial to integration, has small linear dynamic range of only about 35dB, and cannot be expanded.
Disclosure of Invention
The invention aims to provide a multi-channel Ka-band front-end component with high integration, high sensitivity and wide linear dynamic range.
The specific technical scheme of the invention is as follows: the utility model provides a multichannel Ka wave band front end subassembly, includes that four ways radio frequency circuit, four ways intermediate frequency circuit, self-checking divide the network by one minute four merit and the local oscillator divides the network by one minute four merits, wherein:
the four radio frequency circuits are composed of four identical radio frequency circuits, the four intermediate frequency circuits are composed of four identical intermediate frequency circuits, and the radio frequency circuits and the intermediate frequency circuits are connected in series in a one-to-one correspondence manner;
the self-checking one-to-four power distribution network is respectively connected to the coupling ends of the couplers in the four-path radio frequency circuit, so that the self-checking function of the component is realized;
the local oscillator one-to-four power distribution network is respectively connected to local oscillator ends of the frequency mixers in the four-path radio frequency circuit to provide local oscillator signals required by component frequency mixing.
The invention has the beneficial effects that: (1) The Ka-band signal is mixed to a low-frequency band and then is subjected to continuous logarithmic detection amplification, so that the integration is facilitated; (2) The method has extremely high sensitivity, simultaneously has extremely wide instantaneous linear dynamic range, and the linear dynamic range can be expanded; (3) A temperature compensation attenuator and a baseline compensation unit are arranged in the temperature compensation device, and indexes are stable under the full-temperature condition; (4) The interior of the component adopts a micro-assembly and electric fitting mixed assembly process, so that the occupied space is reduced by more than 50%, the integration level is high, and the requirement on assembly is low.
Drawings
Fig. 1 is a schematic diagram of a multi-channel Ka-band front-end component according to an embodiment of the present invention.
Fig. 2 is a schematic diagram of the temperature compensation attenuator according to the embodiment of the present invention.
Fig. 3 is a schematic diagram illustrating a principle of a self-test one-to-four power division network according to an embodiment of the present invention.
Fig. 4 is a schematic diagram of a local oscillation one-to-four power division network principle according to an embodiment of the present invention.
Fig. 5 is an assembly diagram of a multi-channel Ka-band front-end component according to an embodiment of the invention.
Detailed Description
In order to make the objects, technical solutions and advantages of the present invention more apparent, the present invention will be further described with reference to the accompanying drawings and specific embodiments. It should be understood that the specific embodiments described herein are merely illustrative of the invention and do not limit the invention.
As shown in fig. 1, the multichannel Ka band front end module of the present invention includes a four-way radio frequency circuit, a four-way intermediate frequency circuit, a self-checking one-to-four power distribution network, and a local oscillator one-to-four power distribution network, where:
the four radio frequency circuits are composed of four identical radio frequency circuits, the four intermediate frequency circuits are composed of four identical intermediate frequency circuits, and the radio frequency circuits and the intermediate frequency circuits are connected in series in a one-to-one correspondence manner;
the self-checking one-to-four power distribution network is respectively connected to the coupling ends of the couplers in the four-path radio frequency circuit, so that the self-checking function of the component is realized;
the local oscillator one-to-four power distribution network is respectively connected to local oscillator ends of the frequency mixers in the four-path radio frequency circuit to provide local oscillator signals required by component frequency mixing.
The parts are specifically explained as follows:
(1) The four radio frequency circuits are composed of four same radio frequency circuits, each radio frequency circuit is formed by cascading a coupler CP1, a single-pole double-throw switch SW1, an amplifier AM1, a fixed attenuator AT1, a single-pole double-throw switch SW2, a radio frequency band-pass filter BP1, a numerical control attenuator AT2 and a mixer MX1, and the working frequency is 30-40 GHz.
In this embodiment, the coupler CP1 adopts a microstrip parallel coupling structure, the coupling port is connected to the self-checking one-to-four power division network, the coupling degree is usually about 20dB, and the insertion loss is within 0.3dB, so as to realize the self-checking function of the component (checking whether the channel works normally).
The single-pole double-throw switch SW1 and the single-pole double-throw switch SW2 belong to MMIC devices of the same model, are composed of PIN tubes based on an AlGaAs process, and have smaller insertion loss (not more than 0.6 dB) in the whole Ka wave band so as to ensure the sensitivity of the component; the input P-1 is higher, so that the dynamic range of the component is ensured; the smaller rising and falling edges, within 15 ns.
In this embodiment, the amplifier AM1 is formed by cascading a GaAs MMIC low noise amplifier and a three-level self-biased wideband low noise amplifier, +4.5V for power supply, has a whole Ka band noise figure within 3dB and a gain of about 20dB, and has a low noise figure and a high gain to improve the receiving sensitivity of the front end module, which is helpful to improve the detection distance of the amplitude-versus-direction system.
The fixed attenuator AT1 is an MMIC fixed attenuator based on a GaAs process, consists of a thin film resistor, and has extremely flat attenuation and smaller input/output return loss in the whole working bandwidth.
In this embodiment, the single-pole double-throw switches SW1 and SW2, the amplifier AM1 and the fixed attenuator AT1 form a simple linear dynamic expansion circuit, and when a small signal smaller than a set threshold enters a channel, the small signal is output after passing through the single-pole double-throw switch SW1, the amplifier AM1 and the single-pole double-throw switch SW2 by controlling the single-pole double-throw switch SW1 and the single-pole double-throw switch SW 2; when a large signal larger than a set threshold value enters a channel, the single-pole double-throw switch SW1 and the single-pole double-throw switch SW2 are controlled and controlled, so that the large signal is output after passing through the single-pole double-throw switch SW1, the fixed attenuator AT1 and the single-pole double-throw switch SW2, the component always works in a linear working state, the purpose of linear dynamic expansion is achieved, and the attenuation value of the fixed attenuator AT1 is determined by the gain of the amplifier AM1 and the linear dynamic expansion requirement.
In the embodiment, the radio frequency band-pass filter BP1 adopts a three-line microstrip structure and is integrated with a microstrip signal transmission line in an integrated manner, a plate Rogers 5580 is selected, the near-end inhibition is higher, the insertion loss at the passband of 30-40GHz is less than 1dB, the standing wave is not more than 1.6, the inhibition on DC-24GHz reaches more than 65dBc, and the inhibition on 42 GHz-48 GHz reaches more than 40 dBc; the suppression of possible interfering signals outside the radio frequency operating bandwidth (30-40 GHz) is mainly carried out, in particular at the image frequency and at a frequency division of one half of the radio frequency operating frequency.
In the embodiment, the numerical control attenuator AT2 adopts a 2-digit numerical control attenuator integrally driven by GaAs MMIC, the frequency range covers 30-40GHz, the insertion loss is less than or equal to 4dB, the step is 10dB, the TTL logic control is adopted, the switching speed of the switch is less than 20ns, the better input and output standing wave is realized, and the internode matching between the mixer MX1 and the radio frequency link is improved.
The numerical control attenuator AT2 performs graded attenuation according to requirements, and when small signals smaller than a set threshold value enter a channel, the numerical control attenuator AT2 does not perform attenuation; when a large signal larger than a set threshold value enters a channel, if a subsequent device works in a nonlinear state, the numerical control attenuator AT2 attenuates according to 10dB, 20dB, 30dB and 40dB in sequence, so that the subsequent device always works in a linear working state, and the aim of further expanding a linear dynamic range is fulfilled.
In this embodiment, the mixer MX1 employs a passive double-balanced MMIC mixer, which has very low passband insertion loss, high inter-port isolation, high spurious suppression, and high input P-1; the radio frequency and local oscillator working frequency covers 20-40GHz, the intermediate frequency working frequency covers DC-18GHz, and the three ports have high isolation, particularly the isolation from the local oscillator to the radio frequency port is more than 40 dB; the insertion loss of the passband is not more than 10dB, the fluctuation is not more than 3dB, and the input P-1 is not less than 5dBm.
A local oscillation port of the mixer MX1 is connected with a local oscillation one-to-four power division network to convert the radio frequency signal to an intermediate frequency; each port needs to satisfy a corresponding working frequency band, certain isolation is provided between the ports, and a certain suppression degree can be provided for stray signals generated in the medium frequency bandwidth after frequency mixing.
(2) The four intermediate frequency circuits are composed of four same intermediate frequency circuits, each intermediate frequency circuit has the same circuit structure and comprises an intermediate frequency band-pass filter BP2, a temperature compensation attenuator AT3 and a power divider PW1 which are sequentially connected in series, one output of the power divider PW1 is sequentially connected with a continuous logarithmic detection amplifier (SDLVA) SA1 and a base line compensation circuit BL1, the other output is sequentially connected with a fine step numerical control attenuator AT4 and an amplifier AM2, and the working frequency of the intermediate frequency circuit is 6-16 GHz;
in the embodiment, the intermediate frequency band-pass filter BP2 adopts a microstrip interdigital structure, because the intermediate frequency is 6-16GHz and the radio frequency is lower than that of the medium frequency, a ceramic plate AL2O3 is selected as the plate, the filter has small volume and can be integrated with an external microstrip signal transmission line in a bonding and gold wire bonding mode, the pass band is as narrow as possible, the insertion loss of the pass band is not more than 4dB, and the sideband suppression reaches more than 30dB at the position of 1 GHz; the passband of the intermediate frequency band-pass filter BP2 is as narrow as possible on the premise of meeting the intermediate frequency bandwidth, so that the stray signals entering the SDLVA subsequently are reduced, and the sensitivity of the SDLVA is improved. The if band-pass filter BP2 mainly suppresses spurious signals that may exist outside the if bandwidth, especially at the lo frequency and its half.
As shown in fig. 2, in this embodiment, the temperature-compensated attenuator AT3 is formed by combining an external temperature sensor of the electrically-tuned attenuator, a single chip, and a digital-to-analog converter, and specifically includes the following components:
the electric tuning attenuator adopts a GaAs MMIC electric tuning chip, the frequency range of the electric tuning attenuator covers DC-20GHz, the insertion loss is not more than 3dB, the attenuation range is 0-10dB, and the response speed is less than 20ns.
The temperature sensor works at-40 ℃ to +125 ℃, has extremely low working self-heating value, and converts the environment temperature into a digital signal for output.
The digital-to-analog converter has higher resolution, is not lower than 12 bits, has the stable time not higher than 4.5us, is internally provided with a voltage reference source and comprises a double buffer register.
The temperature sensor collects the ambient temperature and converts the ambient temperature into a digital signal, the digital signal is processed by the singlechip and then converted into an analog signal by the digital-to-analog converter, and the analog signal drives the electrically-controlled attenuator to change the attenuation, so that the purpose of temperature compensation is achieved. The temperature compensation attenuation AT3 can adjust the attenuation of the electrically-controlled attenuator by writing a singlechip program, improve the consistency among Video output (Video Out) channels and contribute to improving the precision of a specific amplitude direction-finding system.
In the embodiment, the power divider PW1 adopts a GaAs MMIC 0-degree two-way power divider, the frequency covers 2-18GHz, the insertion loss is not higher than 4.5dB, and the isolation is superior to 12dB.
In the embodiment, the working frequency band of the continuous logarithmic detection amplifier SA1 covers 0.5-18GHz, the flatness in the band is +/-2 dB, the rising edge of the pulse detection output is 5ns, the falling edge of the pulse detection output is 15ns, the time delay of the pulse detection output is not more than 10ns, the recovery time of the pulse detection output is not more than 40ns, the logarithmic slope of the pulse detection output is 15mV/dB, and the detection dynamic range of the pulse detection output is 67dB.
The continuous logarithmic detection amplifier SA1 converts the microwave rf signal into a video signal for output, the working bandwidth includes a medium frequency bandwidth and has a good frequency flatness, and the pulse detection has a very fast rising edge and falling edge and a recovery time meeting the working requirement of the front-end component, which is usually in the order of nanoseconds.
Due to the detection working principle of the continuous logarithmic detection amplifier SA1, the clutter signal may interfere the final video signal, which is mainly manifested as the jitter of the video signal outputted by the detection, affecting the working sensitivity and linear dynamic range of the amplitude-versus-amplitude direction-finding system, so that the influence of the spurious signal and the harmonic signal within the working bandwidth on the detection needs to be analyzed before the specific frequency conversion scheme (i.e. the local oscillator signal frequency) can be determined.
Specifically, the method comprises the following steps: when the difference between the stray signal and the main signal is more than 100MHz, the influence can be ignored; when the spurious signal is close to the main signal, the effect is negligible when the spurious signal is suppressed to 40 dBc. From this, a mixing scheme can be determined, the local oscillator signal frequency being 24GHz.
The detection range of the continuous logarithmic detection amplifier SA1 is higher than the instantaneous linear dynamic range required by a front-end component by more than 15dB so as to improve the receiving sensitivity of the front-end component and reduce the influence caused by frequency flatness in a working bandwidth; the requirements of the components on the noise coefficient and the gain can be determined according to the detection range of SA 1.
In this embodiment, the baseline compensation circuit BL1 includes a temperature sensor, a voltage bias circuit, and an operational amplifier OA1, the SDLVA outputs a video signal to the + input terminal of OA1, the temperature sensor and the voltage bias circuit are connected to the-input terminal of OA1, the voltage bias circuit is mainly used to cancel baseline drift caused by noise of the SDLVA itself, noise of the radio frequency circuit and the intermediate frequency circuit, and the temperature sensor is mainly used to cancel variation of the circuit noise with temperature variation.
The temperature sensor can work at minus 40 ℃ to plus 125 ℃, has extremely low work self-heating value and can convert the environment temperature into an analog signal for output; the voltage bias circuit is formed by connecting a precision power supply and a resistor in series for voltage division, and the initial voltage value of the voltage bias circuit is selected as the noise level of the continuous logarithmic detection amplifier SA 1; the operational amplifier OA1 is a low-noise high-speed current feedback type amplifier, the 3dB bandwidth reaches 95MHz (under the conditions of power supply +/-5V and gain 1 dB), and the slew rate reaches 820V/us (under the conditions of power supply +/-5V and gain 1 dB).
The baseline compensation circuit BL1 makes the noise baseline of the front-end components have very small fluctuation under the full-temperature working state.
The operational amplifier OA1 has a wide Gain-Bandwidth Product (Gain Bandwidth Product) affecting the peak-to-peak value of the front-end component Video output signal "Video Out" and generally cannot be less than 20MHz, and a high Slew Rate (Slew Rate) affecting the rising and falling edges of the "Video Out" pulse and generally cannot be less than 750V/us.
In the embodiment, the fine step numerical control attenuator AT4 adopts a GaAs MMIC numerical control attenuator, the insertion loss is not more than 3dB, the step is 0.25dB and has two bits in total, the attenuation precision is +/-0.2 dB, the TTL voltage is adopted for control, and the switching time is not more than 20ns; the fine step numerical control attenuator AT4 finely adjusts the gain of each intermediate frequency IF channel, the amplitude consistency between the intermediate frequency IF channels is improved, and the number of bits is not more than 4.
In the embodiment, the amplifier AM2 adopts a GaAs MMIC low-noise amplifier, the gain is not less than 20dB, and the noise coefficient is less than 2dB; to meet the linear dynamic range of the front-end components, it is desirable to have a high output P-1, i.e., the power at the 1dB compression point, of no less than 15dBm.
(3) As shown in fig. 3, the self-checking one-to-four power distribution network is formed by connecting four output ends of a one-to-four power divider SPW1 in series with a fixed attenuator SAT1 and an amplifier SAM1, respectively, wherein the input end, i.e., the common end, of the one-to-four power divider SPW1 is connected with a self-checking signal, and the output end of the amplifier SAM1 is connected with the coupling port of the coupler CP1, so as to implement a self-checking function, and the working frequency of the self-checking one-to-four power distribution network is 36GHz.
The one-to-four power divider SPW1 adopts a GaAs MMIC 0-degree four-way power divider chip, the frequency covers 30-40GHz, the in-band insertion loss is less than 1.5dB, the working bandwidth comprises radio frequency, and the isolation between four ways is more than 18 dB.
The fixed attenuator SAT1 is a GaAs MMIC fixed attenuator, is composed of a thin film resistor, and has an extremely flat attenuation amount of 6dB in the entire operating bandwidth and a small input/output return loss.
The amplifier SAM1 adopts a GaAs MMIC low-noise amplifier, the frequency covers 30-40GHz, the gain is about 10dB, and the reverse isolation degree (more than 35 dB) is high, and the amplifier SAM1 is mainly used for improving the isolation degree between channels.
The isolation between the four paths of radio frequency circuits is improved by fixing the attenuation value of the attenuator SAT1 and the reverse isolation of the amplifier SAM1, and the isolation between the four paths of radio frequency circuits reaches over 65dB (related to the linear dynamic range of a front end component) by combining the coupling degree of the coupler CP 1.
The self-checking signal is power-divided and amplified through a one-to-four power divider SPW1, a four-way fixed attenuator SAT1 and an amplifier SAM1, and then is respectively connected to the coupling ports of a four-way radio frequency circuit coupler CP1, so that the independent self-checking function of each path of the assembly is realized.
(4) As shown in fig. 4, the local oscillator one-to-four power division network includes a phase-locked source (PLS) LS1, a band-pass filter LBP1, and a power divider LPW1, which are connected in series in sequence, and four output ends of the power divider LPW1 are respectively connected to a frequency multiplier LMA1 and a band-pass filter LBP2; the input end of a phase-locked source LS1 is connected with a reference signal of 100MHz and the power of 3dBm, the output end of a band-pass filter LBP2 is connected with a local oscillation port of a mixer MX1, a local oscillation signal required by frequency mixing is provided, and the frequency of the local oscillation signal is 24GHz;
the phase-locked source LS1 is formed by a voltage-controlled oscillator (VCO), a frequency divider chip and a voltage stabilizing chip in combination with a multilayer printed board wiring process, is small in size, simple in circuit and convenient to integrate, and has the output frequency of 6GHz, the power of about 5dBm and the phase noise of about-110 dBc/Hz @1kHz.
The band-pass filter LBP1 adopts a parallel coupling line structure, the intermediate frequency is 6GHz, the sideband suppression position is more than 20dB, a plate is selected as ceramic AL2O3, and the filter is small in size and can be integrated with an external microstrip signal transmission line in a bonding and gold wire bonding mode.
The power divider LPW1 adopts a micro-strip Wilkinson cascade structure, has the frequency of 6-18GHz and the in-band insertion loss of not more than 9dB, adopts ceramic AL2O3 as a plate, has small volume and can be integrated with an external micro-strip signal transmission line in a bonding and gold wire bonding mode.
The frequency multiplier LMA1 adopts a GaAs MMIC active quadrupler, and integrates a quadrupler and an output amplifier inside, so that the fundamental wave suppression reaches more than 30dBc, and the output power is more than 18 dBm.
The band-pass filter LBP2 adopts a parallel coupling line structure, the intermediate frequency is 24GHz, the in-band insertion loss is not more than 2dB, the inhibition on 6GHz, 12GHz, 18GHz and 30-40GHz is more than 60dB, a selected plate is ceramic AL2O3, the filter is small in size, and the filter can be integrated with an external microstrip signal transmission line in a bonding and gold wire bonding mode.
In this embodiment, the phase-locked source LS1 is formed by using a classical phase-locked loop (PLL) circuit, including a Voltage Controlled Oscillator (VCO), a frequency divider chip, and a voltage stabilization chip, and combining a multilayer printed board wiring process, and has the advantages of a small size, a simple circuit, and low phase noise.
In this embodiment, the center frequency of the band-pass filter LBP1 is the output frequency of the phase-locked source LS1, the insertion loss is within 3dB, the half harmonic and the second harmonic of the output frequency are suppressed out-of-band, and the suppression degree is above 50 dB.
In this embodiment, the insertion loss at the output frequency of the power divider LPW1 and the one-to-four power divider LS1 is not greater than 4dB, and the isolation of the four power dividers is greater than 15 dB.
In this embodiment, the frequency multiplier LMA1 and the active quadrupler have input power of about 0dBm, output power of more than 15dBm, and fundamental suppression of more than 25 dB.
In this embodiment, the center frequency of the band-pass filter LBP2 is the local oscillator signal frequency, the insertion loss is within 3dB, the output fundamental wave and the third harmonic of the LMA1 are suppressed out-of-band, and the suppression degree is above 55 dB.
In this embodiment, the local oscillator one-to-four power distribution network may effectively reduce the problem of channel isolation caused by local oscillator leakage by the combination of the four-path frequency multiplier LMA1 and the band-pass filter LBP 2.
It can be seen that, the local oscillation signal frequency can be determined according to the influence of the clutter on the SDLVA video output signal, and then the internal parameters of the local oscillation one-to-four power division network are determined; determining the noise coefficient and the gain range of the whole link according to the SDLVA detection range, and further determining the internal parameters of a radio frequency circuit and an intermediate frequency circuit, the noise coefficient as low as possible and the instantaneous linear dynamic range as high as possible; the linear dynamic of the component can be expanded through a switch and a numerical control attenuator in the radio frequency circuit; the performance of the assembly under the full-temperature condition can be optimized through a temperature compensation attenuator in the intermediate frequency circuit; the consistency among the channels can be improved through the fine step numerical control attenuator in the intermediate frequency circuit; through a baseline compensation circuit in the intermediate frequency circuit, the noise baseline of the component has extremely small fluctuation under the full-temperature condition; through the network is divided into four to one in self-checking, the subassembly possesses the self-checking function.
The multi-channel Ka-band front-end component provided by this embodiment has complex functions and high integration level, and needs to be designed in a reasonable plane, wherein the radio frequency circuit (four paths in total), the intermediate frequency circuit (four paths in total) and part of logic signals and power routing are placed on the front side, and the self-checking one-to-four power division network, the local oscillator one-to-four power division network, the power management circuit and the logic control circuit are placed on the back side. All GaAs MMIC chips must be grounded on the back side and sintered by 80/20 Au-Sn at the sintering temperature not exceeding 300 ℃ and the sintering time as short as possible not exceeding 30 seconds.
The assembly is schematically shown in fig. 5, and the whole cavity is divided into a surface A and a surface B. The four radio frequency circuits and the four intermediate frequency circuits are concentrated on the surface A of the assembly, and a micro-assembly and electric fitting mixed assembly process is adopted, namely, the micro-assembly circuit is arranged on the electric fitting circuit, and the temperature gradient needs to be designed reasonably during assembly, so that the later debugging performance and the maintainability are realized; the self-checking one-to-four power distribution network, the local oscillator one-to-four power distribution network, the power management circuit and the logic control circuit are integrated on the B surface of the component. The A surface and the B surface are communicated through direct current transition and radio frequency vertical transition respectively, the circuit area is reduced by the assembly mode, and the integration level of the assembly is improved.
Specifically, the surface A adopts a micro-assembly and electric-part hybrid assembly process, namely a micro-assembly circuit (flexible substrate) is arranged on an electric circuit (printed circuit board). A proper amount of alpha tin paste LR721H3 (62 Sn36Pb2 Ag) is uniformly coated on the bottom surface of the printed board, and is matched with a small amount of soldering flux and welded on the box body through a 220 ℃ heating table; mounting the partition wall on the surface of the printed board by using screws and coating H20E conductive adhesive on the joints; and finally, coating H20E conductive adhesive on the bottom surface of the soft substrate, adhering the soft substrate to the surface of a printed board, and curing at the temperature of 170 ℃ for 30 minutes, so that micro-assembly and electric device hybrid assembly is completed, and the debugging performance and the maintainability are realized in the later stage.
The performance criteria that can be achieved are as follows: the input radio frequency covers 30-40GHz, and the input signal power is as follows: -65 ~+ 15dBm, instantaneous linear dynamic of Video Out (Video signal) output is not less than 50dB, instantaneous linear dynamic of IF (intermediate frequency signal) output is not less than 40dB, self-checking signal frequency is 36GHz, intermediate frequency signal output frequency is 6-16GHz, full temperature gain is 38 +/-3 dB, output signal stray is not more than-25 dBc, phase noise is not more than-80 dBc/Hz @1kHz; the total temperature of a Video Out (Video signal) noise base line is 0-150 mV, the peak value is less than or equal to 200mV, the logarithmic slope is 60 +/-2.5 mV/dB, the logarithmic linearity is less than or equal to +/-2 dB, the rising edge is less than or equal to 25ns, the falling edge is less than or equal to 100ns, and when a-65 dBm signal is injected, the signal-to-noise ratio is more than or equal to 300mV; the amplitude consistency among all channels of the component is less than or equal to +/-2 dB, and the isolation is more than or equal to 65dBc.
According to the multichannel Ka-band front-end component, millimeter-band signals are mixed to a low-frequency band by adopting a millimeter wave broadband mixing technology, and then a continuous logarithmic detection amplification (SDLVA) technology is adopted, so that the multichannel Ka-band front-end component has a wider dynamic range compared with a traditional millimeter wave detection scheme, and has a smaller volume compared with a traditional DLVA scheme; determining a mixing scheme according to the influence of the stray on the SDLVA video output signal, reasonably distributing link gain, having extremely high sensitivity and simultaneously considering a larger instantaneous linear dynamic range, and the linear dynamic can be expanded; by adopting the SDLVA technology, a noise base line is more stable than that of the traditional DLVA technology, a temperature compensation attenuator and a base line compensation unit are additionally added, the influence of temperature on the performance of the component is reduced, and the stability is higher under the full-temperature condition; the interior of the component adopts the micro-assembly and electric fitting mixed assembly process, and the occupied space is reduced by more than 50%. All technical indexes of the assembly reach the domestic leading level, the integration level is extremely high, the requirement on assembly is low, and the assembly is suitable for a millimeter wave amplitude comparison direction finding system.
The above-mentioned embodiments only express the embodiments of the present invention, and the description thereof is more specific and detailed, but not construed as limiting the scope of the present invention. It should be noted that, for a person skilled in the art, several variations and modifications can be made without departing from the inventive concept, which falls within the scope of the present invention. Therefore, the protection scope of the present invention should be subject to the appended claims.
Claims (2)
1. The utility model provides a multichannel Ka wave band front end subassembly, its characterized in that, front end subassembly operating frequency is 30 ~ 40GHz, divides the network and local oscillator one divides four merit to divide the network including four ways radio frequency circuit, four ways intermediate frequency circuit, self-checking one divide four merit, wherein:
the four radio frequency circuits consist of four identical radio frequency circuits, and each radio frequency circuit is formed by cascading a coupler, a first single-pole double-throw switch, a first amplifier, a fixed attenuator, a second single-pole double-throw switch, a radio frequency band-pass filter, a numerical control attenuator and a frequency mixer; the four intermediate frequency circuits consist of four identical intermediate frequency circuits, each intermediate frequency circuit comprises an intermediate frequency band-pass filter, a temperature compensation attenuator and a first power divider which are sequentially connected in series, one output of the first power divider is sequentially connected with a continuous logarithmic detection amplifier and a base line compensation circuit, and the other output of the first power divider is sequentially connected with a fine step numerical control attenuator and a second amplifier; the radio frequency circuit and the intermediate frequency circuit are connected in series in a one-to-one correspondence manner;
the coupler adopts a microstrip parallel coupling structure, the radio frequency band-pass filter adopts a three-line microstrip structure, the mixer adopts a passive double-balance MMIC mixer, and the intermediate frequency band-pass filter adopts a microstrip interdigital structure; the fine stepping numerical control attenuator adopts a GaAs MMIC numerical control attenuator, the insertion loss is not more than 3dB, the stepping is 0.25dB, the total number of the two positions is two, the attenuation precision is +/-0.2 dB, the TTL voltage is adopted for control, and the switching time is not more than 20ns;
the self-checking one-to-four power distribution network is respectively connected to the coupling ends of the couplers in the four-path radio frequency circuit, so that the self-checking function of the component is realized;
the local oscillator one-to-four power distribution network is respectively accessed to local oscillator ends of frequency mixers in the four-path radio frequency circuit to provide local oscillator signals required by component frequency mixing;
the first single-pole double-throw switch, the second single-pole double-throw switch, the first amplifier and the fixed attenuator form a linear dynamic expansion circuit; when a small signal smaller than a set threshold value enters a channel, the small signal is output after passing through the first single-pole double-throw switch, the first amplifier and the second single-pole double-throw switch by controlling the first single-pole double-throw switch and the second single-pole double-throw switch; when a large signal larger than a set threshold value enters a channel, the large signal is output after passing through the first single-pole double-throw switch, the fixed attenuator and the second single-pole double-throw switch by controlling the first single-pole double-throw switch and the second single-pole double-throw switch, so that the assembly always works in a linear working state;
the temperature compensation attenuator is formed by combining an electrically-controlled attenuator externally connected with a first temperature sensor, a singlechip and a digital-to-analog converter, wherein the first temperature sensor is used for acquiring ambient temperature and converting the ambient temperature into a digital signal, the digital signal is processed by the singlechip and then converted into an analog signal by the digital-to-analog converter, and the analog signal drives the electrically-controlled attenuator to change attenuation so as to achieve the purpose of temperature compensation;
the baseline compensation circuit comprises a second temperature sensor, a voltage bias circuit and an operational amplifier, wherein the second temperature sensor converts the ambient temperature into an analog signal and outputs the analog signal; the initial voltage value of the voltage bias circuit is selected as the noise level of the continuous logarithmic detection amplifier; the operational amplifier adopts a low-noise and high-speed current feedback type amplifier;
the self-checking one-to-four power distribution network is formed by respectively connecting four output ends of a one-to-four power divider in series with a fixed attenuator and a third amplifier, wherein the input end, namely the common end, of the one-to-four power divider is connected with a self-checking signal, and the output end of the third amplifier is connected with a coupling port of a coupler;
the local oscillator one-to-four power distribution network comprises a phase-locked source, a band-pass filter and a second power divider which are sequentially connected in series, wherein four output ends of the second power divider are respectively connected with a frequency multiplier and a band-pass filter; the input end of the phase-locked source is accessed with a reference signal of 100MHz and the power of 3dBm, and the output end of the band-pass filter is connected with a local oscillator port of the frequency mixer to provide a local oscillator signal required by frequency mixing;
the numerical control attenuator adopts a 2-digit numerical control attenuator integrally driven by GaAs MMIC, the frequency range covers 30-40GHz, the insertion loss is less than or equal to 4dB, the step is 10dB, the TTL logic control is adopted, and the switching speed of a switch is less than 20ns; when the small signal smaller than the set threshold enters the channel, the numerical control attenuator does not attenuate; when a large signal larger than a set threshold value enters a channel, if a subsequent device works in a nonlinear state, the numerical control attenuator attenuates according to 10dB, 20dB, 30dB and 40dB in sequence, so that the subsequent device always works in a linear working state, and the linear dynamic range expansion is realized.
2. The multi-channel Ka-band front-end module of claim 1, wherein the four RF circuits and four IF circuits are integrated on a first side of the module by a micro-assembly and electrical-device hybrid assembly process, i.e., the micro-assembly circuit is mounted on the electrical-device circuit; the self-checking one-to-four power distribution network and the local oscillator one-to-four power distribution network are centralized on the second surface of the component, and the first surface and the second surface are communicated through direct current transition and radio frequency vertical transition respectively.
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| CN115022148B (en) * | 2022-06-20 | 2024-06-25 | 成都富元辰科技有限公司 | Four-channel single-bit frequency measurement system and method |
| CN115458886A (en) * | 2022-09-07 | 2022-12-09 | 太仓市同维电子有限公司 | Method for improving out-of-band rejection capability of WiFi full-band filter |
| CN115343679A (en) * | 2022-10-13 | 2022-11-15 | 南京冉思电子科技有限公司 | Multi-band receiver |
| CN116938277B (en) * | 2023-09-15 | 2023-12-15 | 中科海高(成都)电子技术有限公司 | Multichannel radio frequency front end and composite substrate |
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