CN114024129B - Balanced type microstrip series-feed array antenna - Google Patents
Balanced type microstrip series-feed array antenna Download PDFInfo
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- CN114024129B CN114024129B CN202111186172.9A CN202111186172A CN114024129B CN 114024129 B CN114024129 B CN 114024129B CN 202111186172 A CN202111186172 A CN 202111186172A CN 114024129 B CN114024129 B CN 114024129B
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01P—WAVEGUIDES; RESONATORS, LINES, OR OTHER DEVICES OF THE WAVEGUIDE TYPE
- H01P1/00—Auxiliary devices
- H01P1/02—Bends; Corners; Twists
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q1/00—Details of, or arrangements associated with, antennas
- H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q21/00—Antenna arrays or systems
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/01—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the shape of the antenna or antenna system
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q3/00—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system
- H01Q3/26—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture
- H01Q3/28—Arrangements for changing or varying the orientation or the shape of the directional pattern of the waves radiated from an antenna or antenna system varying the relative phase or relative amplitude of energisation between two or more active radiating elements; varying the distribution of energy across a radiating aperture varying the amplitude
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- H—ELECTRICITY
- H01—ELECTRIC ELEMENTS
- H01Q—ANTENNAS, i.e. RADIO AERIALS
- H01Q9/00—Electrically-short antennas having dimensions not more than twice the operating wavelength and consisting of conductive active radiating elements
- H01Q9/04—Resonant antennas
- H01Q9/0407—Substantially flat resonant element parallel to ground plane, e.g. patch antenna
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Abstract
The invention discloses a balanced type microstrip series-fed array antenna, which comprises an antenna radiation layer, an antenna coupling layer and an antenna feed layer which are sequentially connected, wherein the antenna radiation layer comprises two substrate integrated waveguide sub-power sub-networks connected with the antenna coupling layer and a plurality of balanced type microstrip radiation patch sub-arrays arranged between the two substrate integrated waveguide sub-power sub-networks, and the two substrate integrated waveguide sub-power sub-networks are symmetrical about the central line of the balanced type microstrip radiation patch sub-arrays. The invention solves the problems that the radiation performance is influenced by the deviation and asymmetry of the feed directional diagram along with the central frequency in the prior art.
Description
Technical Field
The invention relates to the technical field of radar system antennas, in particular to a balanced microstrip series-fed array antenna.
Background
High gain, low sidelobes are generally required for radar system antennas. The radar antenna mainly adopts the forms of a reflector antenna, a panel antenna, a phased array antenna and the like. The reflector antenna is largely used in the conventional radar system due to the advantages of simple design, high reliability, low cost and the like, but has a high section and a large volume, is not beneficial to the integration of the whole system and is not suitable for a small-sized radar system. The phased array antenna can scan beams without a servo system, is short in beam switching time, is very suitable for a carrier platform moving at a high speed, but is high in design difficulty and manufacturing and maintenance cost, and cannot be borne by a common civil system. The panel antenna has the advantages of low profile, high efficiency and the like, and is widely applied to radar systems.
However, the prior art has the following defects:
references [1] and [2] propose a waveguide slot panel array antenna, which performs directional diagram shaping by controlling the size of radiation energy of each slot, and reduces the side lobe level. The whole antenna is made of metal and is produced in a machining mode, layers are connected in a brazing vacuum welding mode, the overall cost is high, the consistency is poor, and the yield is difficult to guarantee in batch production.
References [3] and [4] propose a planar slot array antenna based on a Substrate Integrated Waveguide (SIW), which adopts the substrate integrated waveguide to replace a metal waveguide and is processed by a PCB process with low cost. However, in the millimeter wave and even higher frequency band, the size of the radiation gap energy is very sensitive to the size, and the radiation performance can be ensured only by improving the processing precision. And in reference [3], the whole feed network and the radiation surface are in the same layer, so that the radiation aperture utilization rate is reduced.
References [5] and [6] propose a flat array antenna based on a series-fed microstrip. The control of radiation energy is realized by controlling the length and the width of the patch, and the side lobe level is reduced. The whole antenna is processed through a PCB process, the processing difficulty is small, and the cost is low. However, the feed port is arranged on one side of the series-fed microstrip line, the directional diagram deviates from the normal direction along with the frequency deviation, and the directional diagram is asymmetric. The feed network in reference [5] is a microstrip power dividing network, and generates a certain radiation, thereby affecting the overall pattern and reducing the radiation efficiency.
Reference:
[1]S.S.Oh,J.W.Lee,M.S.Song and Y.S.Kim.Two-layer slotted-waveguide antenna array with broad reflection/gain bandwidth at millimetre-wave frequencies[J].IEEE Proc.-Microw.Antennas Propag,Vol.151,No.5,October 2004
[2]X.P.Li,S.H.Zhang,Y.B.Yang and Z.Y.Li.Design and Thermal-analysis of A Slotted Waveguide Antenna Array for W-band Applications[C].2012Iternational Conference on Microwave and Millimeter Wave Technology(ICMMT).
[3]Y.J.Chen,W.Hong,K.Wu.94GHz Substrate Integrated Monopulse Antenna Array[J].IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION,VOL.60,NO.1,JANUARY 2012.
[4]J.Wang,Y.J.Chen.W-Band High Gain Slot Array Antenna with Low Sidelobe Level[C].2016IEEE 5th Asia-Pacific Conference on Antennas and Propagation(APCAP).
[5]Y.I.Chong,W.B.Dou.Microstrip Series Fed Antenna Array for Millimeter Wave Automotive Radar Applications[C].2012IEEE MTT-S International Microwave Workshop Series on Millimeter Wave Wireless Technology and Applications.
[6]J.J.Yan,H.M.Wang,J.X.Yin and W.Hong.Planar Series-Fed Antenna Array for 77GHz Automotive Radar[C].2017Sixth Asia-Pacific Conference on Antennas and Propagation(APCAP).
disclosure of Invention
In order to overcome the defects of the prior art, the invention provides a balanced microstrip series-fed array antenna, which solves the problems that the radiation performance is influenced by the deviation and asymmetry of a feed directional diagram along with the central frequency in the prior art.
The technical scheme adopted by the invention for solving the problems is as follows:
a balanced type microstrip series feed array antenna comprises an antenna radiation layer, an antenna coupling layer and an antenna feed layer which are sequentially connected, wherein the antenna radiation layer comprises two substrate integrated waveguide sub-power division networks connected with the antenna coupling layer and a plurality of balanced type microstrip radiation patch sub-arrays arranged between the two substrate integrated waveguide sub-power division networks, and the two substrate integrated waveguide sub-power division networks are symmetrical about the central line of the balanced type microstrip radiation patch sub-arrays.
The two substrate integrated waveguide sub-power division networks are symmetrical about the center line of the balanced type microstrip radiation patch sub-array, so that the problems that a single-direction feed directional diagram deviates along with the center frequency and is asymmetrical and the like are solved, and the radiation performance is improved.
As a preferred technical scheme, a plurality of balanced type microstrip radiating patch sub-arrays are distributed in a centrosymmetric manner about the central point of the whole structure formed by the balanced type microstrip radiating patch sub-arrays.
This further solves the problems of single direction feed pattern offset and asymmetry with the center frequency.
As a preferred technical solution, the balanced microstrip radiation patch sub-array includes a plurality of microstrip radiation patches.
The radiation energy can be effectively controlled by adjusting the width of the microstrip radiation patch, so that the side lobe level of the pitching surface is suppressed; the microstrip radiating patch has larger tolerance for processing errors of the radiating gap and can be better applied to millimeter waves and higher frequency bands.
As a preferred technical solution, the plurality of microstrip radiation patches are distributed in central symmetry with respect to a central point of the balanced microstrip radiation patch sub-array.
This further solves the problems of single direction feed pattern offset and asymmetry with the center frequency.
As a preferred technical scheme, the balanced microstrip radiation patch sub-array further includes a plurality of phase modulation microstrip lines, and the plurality of microstrip radiation patches are connected through the phase modulation microstrip lines.
The phase modulation microstrip line connects the microstrip radiating patches.
As a preferred technical scheme, the power distribution system further comprises a width-gradually-changing transition microstrip line, and a plurality of microstrip radiation patches are connected through a phase modulation microstrip line and then connected with the substrate integrated waveguide sub-power distribution network through the width-gradually-changing transition microstrip line.
The width gradually-changing transition microstrip line enables the microstrip radiation patch to be connected with the substrate integrated waveguide sub power division network, and impedance matching is carried out on the balanced type microstrip radiation patch sub array and the substrate integrated waveguide sub power division network.
As a preferred technical solution, the antenna coupling layer includes a rectangular coupling port, the substrate integrated waveguide sub-power division network includes a substrate integrated waveguide network output port, and a substrate integrated waveguide peripheral metal post, a substrate integrated waveguide power adjustment metal post and/or a substrate integrated waveguide matching adjustment metal post are/is disposed between the rectangular coupling port and the substrate integrated waveguide network output port.
The metal column on the periphery of the substrate integrated waveguide is used for limiting the propagation area of electromagnetic energy. The substrate integrated waveguide power adjusting metal column is used for adjusting the energy output to the output port of the substrate integrated waveguide network, and can distribute the energy uniformly or non-uniformly; and then, impedance matching adjustment is carried out through the substrate integrated waveguide matching adjustment metal column, so that the substrate integrated waveguide network impedance is matched with the radiation impedance of each row of the microstrip radiation patches. The impedance change can be effectively controlled by adjusting the size of the rectangular coupling port, and the effect of impedance matching is achieved.
As a preferred technical solution, the antenna feed layer includes a plurality of waveguide networks, and the plurality of waveguide networks are distributed in a central symmetry manner with respect to the center of the waveguide network as a whole.
This further solves the problems of single direction feed pattern offset and asymmetry with the center frequency.
As a preferred technical solution, each waveguide network includes 4 first feed network sub-arrays, and 1 second feed network sub-array connected to the 4 first feed network sub-arrays respectively.
As a preferred technical solution, the first feed network sub-array includes 4H-plane waveguides, 10E-plane waveguides, and 3E-plane T-type power dividers connected in sequence, and the second feed network sub-array includes 2E-plane T-type power dividers and 1H-plane T-type power divider connected to each other.
The H-face curved waveguide is transited through step transformation, and the E-face curved waveguide is transited through corner cut transformation, so that impedance matching is facilitated. The energy reaching each coupling port can be controlled by controlling the power division ratio of the E-surface T-shaped power divider, so that the side lobe level of the azimuth plane of the array antenna is controlled.
Compared with the prior art, the invention has the following beneficial effects:
(1) The invention solves the problems that the feed directional diagram in a single direction deviates along with the center frequency and is asymmetric, thereby improving the radiation performance;
(2) The radiation energy can be effectively controlled by adjusting the width of the microstrip radiation patch, so that the side lobe level of the pitching surface is suppressed; the micro-strip radiation patch has higher tolerance for processing errors of the radiation gap, and can be better applied to millimeter waves and higher frequency bands;
(3) The width gradually-changing transition microstrip line enables the microstrip radiation patch to be connected with the substrate integrated waveguide sub power division network, and impedance matching is carried out on the balanced type microstrip radiation patch sub array and the substrate integrated waveguide sub power division network;
(4) The metal column at the periphery of the substrate integrated waveguide is used for limiting the propagation area of electromagnetic energy. The substrate integrated waveguide power adjusting metal column is used for adjusting the energy output to the output port of the substrate integrated waveguide network, and can distribute the energy uniformly or non-uniformly; then, impedance matching adjustment is carried out through the substrate integrated waveguide matching adjustment metal column, so that the substrate integrated waveguide network impedance is matched with the radiation impedance of each row of microstrip radiation patches; the impedance change can be effectively controlled by adjusting the size of the rectangular coupling port, so that the impedance matching effect is achieved;
(5) The H-face curved waveguide is transited through step transformation, and the E-face curved waveguide is transited through corner cutting transformation, so that impedance matching is facilitated. The energy reaching each coupling port can be controlled by controlling the power division ratio of the E-surface T-shaped power divider, so that the side lobe level of the azimuth plane of the array antenna is controlled.
Drawings
FIG. 1 is a schematic view of the overall structure of the present invention;
FIG. 2 is a schematic diagram of the structure of the antenna radiation layer according to the present invention
FIG. 3 is a schematic structural diagram of a sub-power division network of a substrate integrated waveguide according to the present invention;
FIG. 4 is a schematic structural diagram of the balanced microstrip radiation patch sub-array according to the present invention;
fig. 5 is a schematic structural diagram of the antenna coupling layer according to the present invention;
FIG. 6 is a schematic structural diagram of a waveguide network of the antenna feed layer according to the present invention;
FIG. 7 is a top view of the present invention from FIG. 6;
fig. 8 is a schematic structural diagram of the first feed network subarray according to the present invention;
fig. 9 is a schematic structural diagram of an E-plane T-type power distribution network according to the present invention;
fig. 10 is a schematic structural diagram of a second feed network subarray according to the present invention;
fig. 11 is a standing wave curve diagram of the balanced microstrip series fed array antenna according to the present invention;
fig. 12 is an azimuth plane radiation pattern curve of a balanced microstrip series-fed array antenna according to the present invention;
fig. 13 is a pitching radiation pattern curve of the balanced microstrip series-fed array antenna according to the present invention.
Reference numbers in the drawings and corresponding part names: 1. an antenna radiation layer, 2, an antenna coupling layer, 3, an antenna feed layer, 11, a substrate integrated waveguide sub-power division network, 12, a balanced type microstrip radiation patch subarray, 111, a substrate integrated waveguide network output port, 112, a substrate integrated waveguide peripheral metal column, 113, a substrate integrated waveguide power regulation metal column, 114, a substrate integrated waveguide matching regulation metal column, 121, a width-gradient type transition microstrip line, 122, a microstrip radiation patch, 123, a phase modulation microstrip line, 201, a rectangular coupling port, 31, a first feed network subarray, 32, a second feed network subarray, 311, an H-plane curved waveguide, 312, an E-plane curved waveguide, 313, narrow-side step transition, 314, a first power division tuning diaphragm, 315, a signal input port, 316, a signal output port, 321, a second power division tuning diaphragm, 322, a third power division tuning diaphragm, 323 and wide-side step transition.
Detailed Description
The present invention will be described in further detail with reference to examples and drawings, but the embodiments of the present invention are not limited thereto.
Example 1
As shown in fig. 1 to 13, a balanced microstrip series-fed array antenna includes an antenna radiation layer 1, an antenna coupling layer 2, and an antenna feed layer 3, which are sequentially connected, where the antenna radiation layer 1 includes two substrate integrated waveguide sub power splitting networks 11 connected to the antenna coupling layer 2, and a plurality of balanced microstrip radiation patch sub-arrays 12 disposed between the two substrate integrated waveguide sub-power splitting networks 11, and the two substrate integrated waveguide sub-power splitting networks 11 are symmetric with respect to a central line of the balanced microstrip radiation patch sub-array 12.
The two substrate integrated waveguide sub-power distribution networks 11 are symmetrical about the central line of the balanced type microstrip radiation patch sub-array 12, so that the problems that a single-direction feed directional diagram deviates along with the central frequency and is asymmetrical are solved, and the radiation performance is improved.
As a preferred technical solution, the plurality of balanced microstrip radiation patch sub-arrays 12 are distributed in a centrosymmetric manner with respect to a central point of an overall structure formed by the balanced microstrip radiation patch sub-arrays 12.
This further solves the problems of single direction feed pattern offset and asymmetry with the center frequency.
As a preferred technical solution, the balanced microstrip radiating patch sub-array 12 includes a plurality of microstrip radiating patches 122.
The radiation energy can be effectively controlled by adjusting the width of the microstrip radiation patch 122, so that the pitching side lobe level is inhibited; the microstrip radiating patch 122 has a larger tolerance for processing errors for radiating slots, and can be better applied to millimeter waves and higher frequency bands.
As a preferred technical solution, the plurality of microstrip radiating patches 122 are distributed in a central symmetry manner with respect to the central point of the balanced microstrip radiating patch sub-array 12.
This further solves the problems of single direction feed pattern offset and asymmetry with the center frequency.
As a preferred technical solution, the balanced microstrip radiation patch sub-array 12 further includes a plurality of phase modulation microstrip lines 123, and the plurality of microstrip radiation patches 122 are connected by the phase modulation microstrip lines 123.
A phase modulated microstrip line 123 connects the microstrip radiating patches 122.
As a preferred technical solution, the waveguide power dividing device further includes a width-gradually-changing transition microstrip line 121, and a plurality of microstrip radiation patches 122 are connected by a phase modulation microstrip line 123 and then connected with the substrate integrated waveguide sub-power dividing network 11 by the width-gradually-changing transition microstrip line 121.
The transition microstrip line 121 with gradually changing width connects the microstrip radiation patch 122 with the substrate integrated waveguide sub-power division network 11, and performs impedance matching between the balanced microstrip radiation patch sub-array 12 and the substrate integrated waveguide sub-power division network 11.
As a preferred technical solution, the antenna coupling layer 2 includes a rectangular coupling port 201, the substrate integrated waveguide sub-power distribution network 11 includes a substrate integrated waveguide network output port 111, and a substrate integrated waveguide peripheral metal pillar 112, a substrate integrated waveguide power adjusting metal pillar 113, and/or a substrate integrated waveguide matching adjusting metal pillar 114 are/is disposed between the rectangular coupling port 201 and the substrate integrated waveguide network output port 111.
The substrate integrated waveguide peripheral metal posts 112 serve to limit the propagation area of electromagnetic energy. The substrate integrated waveguide power adjusting metal column 113 is used for adjusting the energy output to the substrate integrated waveguide network output port 111, and can distribute the energy equally or unequally; and then the impedance matching adjustment is performed through the substrate integrated waveguide matching adjustment metal column 114, so that the substrate integrated waveguide network impedance is matched with the radiation impedance of each row of microstrip radiation patches 122. The impedance change can be effectively controlled by adjusting the size of the rectangular coupling port 201, so that the effect of impedance matching is achieved.
Example 2
As shown in fig. 1 to 13, as a further optimization of embodiment 1, this embodiment includes all the technical features of embodiment 1, and in addition, this embodiment further includes the following technical features:
as a preferred technical solution, the antenna feed layer 3 includes a plurality of waveguide networks, and the plurality of waveguide networks are distributed in a central symmetry manner with respect to the center of the waveguide network as a whole.
This further solves the problem that the unidirectional feed pattern is shifted and asymmetric with the center frequency.
As a preferred technical solution, each waveguide network includes 4 first feed network sub-arrays 31, and 1 second feed network sub-array 32 connected to the 4 first feed network sub-arrays 31, respectively.
As a preferred technical solution, the first feed network sub-array 31 includes 4H-plane curved waveguides 311, 10E-plane curved waveguides 312, and 3E-plane T-type power dividers connected in sequence, and the second feed network sub-array 32 includes 2E-plane T-type power dividers and 1H-plane T-type power divider connected to each other.
The H-plane curved waveguide 311 is transitioned by step transformation, and the E-plane curved waveguide 312 is transitioned by corner cut transformation, which is favorable for impedance matching. The energy reaching each coupling port can be controlled by controlling the power division ratio of the E-surface T-shaped power divider, so that the side lobe level of the azimuth plane of the array antenna is controlled.
Example 3
As shown in fig. 1 to 13, this embodiment includes all the technical features of embodiment 1 and embodiment 2, and this embodiment provides a more detailed implementation manner on the basis of embodiment 1 and embodiment 2.
In order to meet the requirement of a radar system on a high-gain low-sidelobe antenna and further reduce the cost and the process complexity, the invention provides a balanced type microstrip series-fed array antenna. The antenna has the advantages of low cost, easy processing, low profile, low side lobe, strong expansion capability and the like, and can be widely applied to the fields of millimeter wave and submillimeter wave radar detection, communication and the like.
The invention provides a balanced microstrip series-fed array antenna, which comprises a first layer, an antenna radiation layer 1, a second layer, an antenna coupling layer 2 and a third layer, an antenna feed layer 3. The antenna radiation layer 1 is used for performing energy distribution on the energy transmitted by the antenna coupling layer 2 through each patch and then radiating the energy, so that the side lobe level meets the design requirement. The role of the antenna coupling layer 2 is to couple the energy of the antenna feed layer 3 to the antenna radiation layer 1. The antenna feed layer 3 is used for transferring and distributing energy, and transmitting the energy to each coupling port in an equalizing or unbalanced manner. The array antenna has the characteristics of low cost, easiness in processing, low side lobe, low profile and the like.
The balanced microstrip series-fed array antenna is composed of an antenna radiation layer 1, an antenna coupling layer 2 and an antenna feed layer 3 from top to bottom in sequence. The antenna feed layer 3 distributes energy to the antenna coupling layer 2, and the antenna coupling layer 2 couples the energy of the antenna feed layer 3 to the antenna radiation layer 1 for radiation.
The antenna radiation layer 1 further comprises an upper metal microstrip radiation patch layer and a middle medium substrate layer.
The metal microstrip radiation patch layer comprises M rows and N columns of rectangular microstrip radiation patches 122, wherein the size of each row of microstrip radiation patches 122 is the same, the length and the width of each column of microstrip radiation patches 122 can be the same or different, and the control of the side lobe level of the pitching surface is realized by adjusting the width and the length of each column of microstrip radiation patches 122. The final microstrip radiation patches 122 at the upper and lower ends are connected with the upper and lower rectangular metal plates through microstrip lines with gradually changed widths, and the whole microstrip radiation patch layer is distributed in an up-and-down symmetrical manner. Wherein the value of M is generally between 10 and 30, and N is more than or equal to 2.
The medium substrate layer is mainly used for bearing the upper surface microstrip radiation patches 122 and the antenna coupling layer 2 on the lower surface, a series of metalized through holes are formed in the middle of the medium substrate layer, and the medium substrate layer and the metal on the upper surface and the lower surface of the medium substrate form a substrate integrated waveguide power distribution network which is used for transmitting the energy of the antenna coupling layer 2 to each row of microstrip radiation patches 122 through the power distribution network for radiation.
The substrate integrated waveguide power distribution network is distributed in an up-down symmetrical manner, and energy obtained by the antenna coupling layer 2 is transmitted to each row of rectangular microstrip radiation patches 122 in an up-down balanced manner through the network. The substrate integrated waveguide network is symmetrically distributed up, down, left and right and consists of 2 × N/X1-division X-substrate integrated waveguide sub-power division networks 11, and the energy transmitted to each row of microstrip radiation patch 122 antennas can be controlled by adjusting the arrangement of metal through holes of the substrate integrated waveguide sub-power division networks 11, so that the control of azimuth plane side lobe level is realized.
The antenna coupling layer 2 is located on the lower surface of the dielectric substrate, the antenna coupling layer 2 is 2 rows of N/X-column rectangular grooves, the size of each rectangular groove is the same, and the rectangular grooves are symmetrically distributed up and down, left and right.
The antenna feed layer 3 is composed of a series of E-plane and H-plane T-shaped power dividers and L-shaped bent waveguides, and the whole antenna feed layer is distributed in a central symmetry mode.
The E-surface T-shaped power divider can be replaced by a 4-port waveguide bridge, signals are input at the input end, output at the straight-through end and the coupling end, and the isolation end is connected with a matched load.
The E-surface T-shaped power divider is a three-port waveguide device and comprises an input waveguide and two output waveguides, wherein the input waveguide and the output waveguides are in a vertical relation. The middle of the waveguide is inserted with a square or triangular diaphragm, the input waveguide is in a step transition structure, and the matching of power is realized by the change of the value of the narrow side and the change of the length and the width of the diaphragm. The power dividers may be equally or unequally power divided. The equipower distribution structure is symmetrical, and the diaphragm is located the power divider center. The lengths of the two output waveguides of the unequal power divider and the positions of the middle diaphragm from the center are different.
The E-surface L-shaped turning waveguide is of a 90-degree bent waveguide structure, and a chamfer structure is arranged at the bent outer corner of the waveguide.
The H-surface L-shaped curved waveguide is a 90-degree curved waveguide, a step blending block is arranged at the bent outer angle of the waveguide, and the number of steps is more than or equal to 1.
The working frequency band of the antenna has universality and comprises any frequency band from 2GHz to 200 GHz.
Compared with the prior art, the invention has the advantages that:
the adopted balanced type microstrip series feed mode is used for carrying out balanced feed on each row of microstrip radiating patches 122 through the upper coupling port, the lower coupling port and the power dividing network, the defects that a single-direction feed directional diagram deviates along with the central frequency and is asymmetric and the like can be avoided, the substrate integrated waveguide and the microstrip lines are transited in a mode of gradually changing the width, the impedance matching can be effectively adjusted, and the bandwidth is expanded.
Low sidelobes of the azimuth and pitch planes are achieved. The sidelobe level value of the pitching surface can be adjusted by controlling the size of each row of patches, and the sidelobe level value of the azimuth surface can be adjusted by controlling the energy distribution of the substrate integrated waveguide network and the feed network. The microstrip radiating patch 122 has a larger tolerance for processing errors for radiating slots, and can be better applied to millimeter waves and higher frequency bands.
The antenna radiation layer 1 and the antenna coupling layer 2 are processed by adopting a PCB process, the antenna feed layer 3 can be processed by adopting a metal machine, and the processing is simple, the cost is low and the batch production is easy.
The antenna radiation layer 1 and the antenna feed layer 3 are processed in a layered mode by adopting a layered structure, and the layers are connected through screw threads. All the layers have no inclined planes, all the chamfers are in the vertical direction, the processing difficulty is low, and the method is suitable for large-scale production.
Examples of the implementation
In order to solve the defects of the prior art, the invention provides a balanced type microstrip series feed array antenna, which solves the problem that a series feed microstrip line directional diagram deviates the normal direction along with the central frequency by carrying out balanced feed on a microstrip array through an upper feed network and a lower feed network. The side lobe level value of the antenna is controlled by adjusting the surface radiation current by controlling the width of the radiation microstrip radiation patch 122 and the power division ratio of the power division network.
The main parameters of the antenna are as follows:
the array of radiating microstrip radiating patches 122 is: 16 rows and 32 columns;
cell pitch: 2.2mm × 2.5mm;
area of antenna array: 80mm multiplied by 40mm;
cross-sectional height of the array: 10mm.
Specific examples of the present invention are described in detail with reference to the accompanying drawings 1-13 of the specification.
Fig. 1 is an overall structural view of a preferred embodiment of the present invention. The antenna is divided into an antenna radiation layer 1, an antenna coupling layer 2 and an antenna feed layer 3 from top to bottom. The antenna radiation layer 1 shown in fig. 2 includes a dielectric substrate and a microstrip radiation patch 122 on the upper surface of the substrate. Signals firstly enter from an input port of an antenna feed layer 3, energy is transmitted to each antenna coupling layer 2 through a 1-16-branch waveguide power division network, then the energy is transmitted to a substrate integrated waveguide sub-power division network 11 of an antenna radiation layer 1 through the antenna coupling layer 2, the signals are fed to 8 balanced microstrip radiation patches 122 sub-arrays 12 in a vertical balanced mode through an output port 111 of the substrate integrated waveguide network, and energy radiation is carried out through rectangular microstrip radiation patches 122 in the sub-arrays.
In the antenna radiation layer 1 of fig. 2, the whole array can be regarded as 8 identical sub-arrays, each sub-array is composed of 16 rows and 4 columns of balanced microstrip radiation patches 122 sub-arrays 12 and upper and lower substrate integrated waveguide sub-power division networks 11. The subarrays are distributed in a centrosymmetric mode, and the whole array is also distributed in a centrosymmetric mode.
The antenna radiation layer 1 comprises 512 rectangular microstrip radiation patches 122, each row of the radiation microstrip radiation patches 122 are the same, each column of the radiation microstrip radiation patches 122 are distributed in an up-down symmetrical mode, the width of the radiation microstrip radiation patches 122 gradually decreases with respect to the symmetrical center, and the radiation energy can be effectively controlled by adjusting the width of the microstrip radiation patches 122, so that the side lobe level of the pitching surface is suppressed. The microstrip radiation patch 122 is connected with the microstrip radiation patch 122 through a phase modulation microstrip line 123, and then is connected to the substrate integrated waveguide sub power division network 11 through a width gradual change type transition microstrip line 121. The gradually-changing transition microstrip line may be a linear gradually-changing width, or a curve gradually-changing in other shapes, and aims to perform impedance matching between the balanced microstrip radiation patch 122 sub-array 12 and the substrate integrated waveguide sub-power division network 11. The spacing between each row of microstrip radiating patch 122 units is 2.5mm, and the spacing between each row of microstrip radiating patch 122 units is slightly different according to the difference of the resonance lengths of the microstrip radiating patches 122 with different widths, and is about 2.2mm approximately. The total wavefront area was 80mm × 40mm, aspect ratio 2.
Fig. 3 shows a schematic diagram of the substrate integrated waveguide sub-power splitting network 11, which is a one-to-four power splitter. The metal substrate comprises a dielectric substrate, upper and lower surface metal layers and a series of metalized through holes. The lower surface metal layer is provided with a rectangular coupling port 201 for coupling the energy of the feed layer to the antenna radiation layer 1 through the coupling port, transmitting the energy to the output port 111 of the substrate integrated waveguide network through the waveguide sub-power division network, and finally transmitting the energy to each row of rectangular microstrip radiation patches 122 through the output port 111 of the substrate integrated waveguide network for radiation. The dielectric substrate layer is perforated with a series of circular metallized vias in which substrate integrated waveguide peripheral metal posts 112 are used to limit the propagation area of electromagnetic energy. The substrate integrated waveguide power adjusting metal column 113 is used for adjusting the energy output to the output port 111 of the 4-substrate integrated waveguide network, and can distribute the energy equally or unequally. And then the impedance matching adjustment is performed through the substrate integrated waveguide matching adjustment metal column 114, so that the substrate integrated waveguide network impedance is matched with the radiation impedance of each row of radiation microstrip patch 122.
Fig. 5 is a schematic diagram of an antenna coupling layer, which includes 16 rectangular coupling ports 201, and the layer is located on the lower surface of the dielectric substrate of the antenna radiation layer 1, and can be completed by a single-layer PCB process together with the antenna radiation layer 1. The impedance change can be effectively controlled by adjusting the size of the coupling port, and the effect of impedance matching is achieved.
Fig. 6 is a side view of the 1-to-16-waveguide network of the antenna feed layer 3, and fig. 7 is a top view. The waveguide network comprises 4 first feed network sub-arrays 31 and 1 second feed network sub-array 32, and the whole network is distributed in a central symmetry mode. All chamfer directions in the waveguide network are vertical directions, and the design shape is regular, the processing technology is simple, and the waveguide network is suitable for mass production.
As shown in fig. 8, the first feeding network sub-array 31 includes 3E-plane T-type power splitters, 4H-plane waveguides 311, and 10E-plane waveguides 312. The H-plane waveguide 311 is transitioned by step transformation, and the E-plane waveguide 312 is transitioned by corner cut transformation, which is favorable for impedance matching. The energy reaching each coupling port can be controlled by controlling the power division ratio of the E-surface T-shaped power divider, so that the side lobe level of the azimuth plane of the array antenna is controlled.
The E-plane T-type power splitter, as shown in fig. 9, is a three-port network comprising 1 signal input port 315,2 signal output ports 316, a first power splitting tuning diaphragm 314, and a narrow-sided step transition 313. The inserted tuning diaphragm can be triangular or rectangular, and the amount of energy output to the two-end signal output port 316 can be controlled by adjusting the length, width and position of the diaphragm from the center.
As shown in fig. 10, the second feed network sub-array 32 includes 2E-plane T-type power splitters and 1H-plane T-type power splitter, and the second power splitting tuning diaphragm 321 and the third power splitting tuning diaphragm 322 achieve equal distribution of energy, and the broadside step transition 323 achieves matching of port impedance.
Figure 11 is a graph of the standing wave for the preferred embodiment of the invention from which it can be seen that the standing wave for the antenna is less than 2 in the operating bandwidth of 92GHz to 94 GHz.
Fig. 12 is a radiation pattern curve of the positioning plane at the operating frequency points of 92GHz, 93GHz and 94GHz according to the preferred embodiment of the present invention, and it can be seen from the curve that the antenna side lobe level is less than-25 dB, and the beam width is less than 2.5 °.
Fig. 13 is a graph of the radiation pattern of the preferred embodiment of the present invention at the operating frequencies 92GHz, 93GHz, and 94GHz, from which it can be seen that the antenna sidelobe level is less than-18 dB and the beam width is less than 5 °.
Specifically, the curve in fig. 11 is a standing wave curve of the antenna in the operating frequency band, the abscissa is the operating frequency of the antenna, and the ordinate is the standing wave value of the antenna, and the graph can visually reflect the matching characteristic of the antenna. As can be seen from the figure, the standing wave of the antenna is less than 2 in the range of 92GHz to 94GHz, and the impedance matching characteristic is good.
In fig. 12, three curves are radiation patterns of the antenna at operating frequency points 92GHz, 93GHz, and 94GHz, respectively, an abscissa represents an angle of the antenna azimuth plane deviating from the normal direction, and an ordinate represents the antenna gain. It can be seen from the figure that the antenna has maximum gain at normal and then tapers off, with side lobe levels less than-25 dB and a beam width of less than 2.5 °.
In fig. 13, three curves are radiation patterns of the antenna at operating frequencies of 92GHz, 93GHz, and 94GHz, respectively, where an abscissa represents an angle of the pitching surface of the antenna from the normal direction, and an ordinate represents an antenna gain. It can be seen that the antenna has maximum gain at normal and then tapers off, with side lobe levels less than-18 dB and a beam width of less than 5 °.
As described above, the present invention can be preferably realized.
All features disclosed in all embodiments in this specification, or all methods or process steps implicitly disclosed, may be combined and/or expanded, or substituted, in any way, except for mutually exclusive features and/or steps.
The foregoing is only a preferred embodiment of the present invention, and the present invention is not limited thereto in any way, and any simple modification, equivalent replacement and improvement made to the above embodiment within the spirit and principle of the present invention still fall within the protection scope of the present invention.
Claims (8)
1. The balanced type microstrip series-feed array antenna is characterized by comprising an antenna radiation layer (1), an antenna coupling layer (2) and an antenna feed layer (3) which are sequentially connected, wherein the antenna radiation layer (1) comprises two substrate integrated waveguide sub power distribution networks (11) connected with the antenna coupling layer (2) and a plurality of balanced type microstrip radiation patch sub-arrays (12) arranged between the two substrate integrated waveguide sub power distribution networks (11), and the two substrate integrated waveguide sub power distribution networks (11) are symmetrical about the central line of the balanced type microstrip radiation patch sub-arrays (12);
the balanced microstrip radiation patch subarray (12) also comprises a plurality of phase modulation microstrip lines (123), and the plurality of microstrip radiation patches (122) are connected through the phase modulation microstrip lines (123);
the microstrip radiating patch antenna further comprises a width gradually-changing transition microstrip line (121), and a plurality of microstrip radiating patches (122) are connected through a phase modulation microstrip line (123) and then connected with the substrate integrated waveguide sub-power distribution network (11) through the width gradually-changing transition microstrip line (121).
2. The balanced microstrip series fed array antenna according to claim 1, wherein the plurality of balanced microstrip radiating patch sub-arrays (12) are arranged in a central symmetry with respect to a central point of the overall structure formed by the balanced microstrip radiating patch sub-arrays (12).
3. The balanced microstrip series fed array antenna according to claim 2 wherein said balanced microstrip radiating patch sub-array (12) comprises a plurality of microstrip radiating patches (122).
4. The balanced microstrip series fed array antenna according to claim 3 wherein said plurality of microstrip radiating patches (122) are distributed in a centrosymmetric manner about a center point of said balanced microstrip radiating patch sub-array (12).
5. The balanced microstrip series-fed array antenna according to claim 4, wherein the antenna coupling layer (2) includes a rectangular coupling port (201), the substrate integrated waveguide sub-power distribution network (11) includes a substrate integrated waveguide network output port (111), and a substrate integrated waveguide peripheral metal pillar (112), a substrate integrated waveguide power adjusting metal pillar (113) and/or a substrate integrated waveguide matching adjusting metal pillar (114) are/is disposed between the rectangular coupling port (201) and the substrate integrated waveguide network output port (111).
6. The balanced microstrip series fed array antenna according to any one of claims 1 to 5, wherein said antenna feed layer (3) comprises a plurality of waveguide networks, said plurality of waveguide networks being arranged in a central symmetry with respect to the center of the waveguide network.
7. The balanced microstrip series fed array antenna according to claim 6, wherein each waveguide network comprises 4 first feeding network sub-arrays (31) and 1 second feeding network sub-array (32) connected to the 4 first feeding network sub-arrays (31), respectively.
8. The balanced microstrip series fed array antenna according to claim 7, wherein the first feeding network sub-array (31) comprises 4H-plane waveguides (311), 10E-plane waveguides (312), and 3E-plane T-type power dividers connected in sequence, and the second feeding network sub-array (32) comprises 2E-plane T-type power dividers and 1H-plane T-type power divider connected to each other.
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| CN106684561A (en) * | 2017-01-16 | 2017-05-17 | 东南大学 | Antenna structure and design method |
| CN210074171U (en) * | 2019-05-31 | 2020-02-14 | 珠海上富电技股份有限公司 | Multi-beam shaped antenna |
| WO2021068442A1 (en) * | 2019-10-10 | 2021-04-15 | 东南大学 | Low-loss feeding network and high-efficiency antenna device |
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| WO2015172841A1 (en) * | 2014-05-16 | 2015-11-19 | Huawei Technologies Co., Ltd. | A planar multilayer antenna |
| JP2019022088A (en) * | 2017-07-18 | 2019-02-07 | 株式会社フジクラ | antenna |
| CN209056612U (en) * | 2018-10-29 | 2019-07-02 | 成都市克莱微波科技有限公司 | A kind of series feed array microstrip antenna of the series feed network of combination |
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| CN210074171U (en) * | 2019-05-31 | 2020-02-14 | 珠海上富电技股份有限公司 | Multi-beam shaped antenna |
| WO2021068442A1 (en) * | 2019-10-10 | 2021-04-15 | 东南大学 | Low-loss feeding network and high-efficiency antenna device |
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