CN106787914A - LC series resonance-type three-phases high frequency chain matrix inverter topology and modulator approach - Google Patents
LC series resonance-type three-phases high frequency chain matrix inverter topology and modulator approach Download PDFInfo
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- CN106787914A CN106787914A CN201710124842.1A CN201710124842A CN106787914A CN 106787914 A CN106787914 A CN 106787914A CN 201710124842 A CN201710124842 A CN 201710124842A CN 106787914 A CN106787914 A CN 106787914A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
- H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
- H02M5/10—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using transformers
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
- H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
- H02M5/22—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M5/275—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/293—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
- H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
- H02M5/22—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M5/275—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/293—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M5/2932—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage, current or power
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Inverter Devices (AREA)
Abstract
A kind of LC series resonance-types three-phase high frequency chain matrix inverter topology and modulator approach, the LC series resonances three-phase high frequency chain matrix inverter topology are sequentially connected and are constituted by full-bridge LC series resonant inverters, high frequency transformer T, matrix converter, CL mode filters；Modulator approach is SVPWM encourages resonant modulation with current mode half period that coupling is combined of unhitching, it is complementary pwm signal to give transformer prime LC series resonant inverters, pwm signal and SVPWM signals are carried out into the unhitch logical process of coupling of current mode and obtains the drive signal of transformer rear class matrix converter, realize being transmitted to output loading side the control of energy with this；The matrix converter of transformer rear class is decoupled into two common current source inverters and is controlled by the modulation, and switching tube is switched over during transformer zero current is exported, and reduces the loss of switching tube, realizes energy in bidirectional flow and four quadrant running.The present invention has the advantages that power conversion grade is few, control method is simple, circuit stability is high.
Description
Technical field
The present invention relates to electronic power converter topology and modulation field, especially a kind of LC series resonance-types three-phase
The SVPWM of high frequency chain matrix inverter encourages resonant modulation method with current mode half period that coupling is combined of unhitching.
Background technology
Inverter is a kind of topology apparatus for direct current energy being converted into AC energy.High-frequency chain inverter is become using high frequency
Depressor substitute Industrial Frequency Transformer overcome that traditional transformer volume is big, noise big, high cost the shortcomings of.High frequency chain matrix inversion
The conversion process of device has tri- kinds of power features of DC/HFAC/LFAC, wherein, HFAC：High-frequency ac, LFAC：Low-frequency ac.Understand
DC/AC i.e. AC/DC inversion link is occurred in that in such inverter, the link is located at transformer primary side, AC/AC is occurred in that again
That is AC/AC transform part, the link is also commonly referred to as frequency converter or matrix converter link, positioned at transformer secondary.
Matrix converter does not have intermediate energy storage link, using two-way switch compared with conventional transducers, it is possible to achieve the bidirectional flow of energy
It is dynamic, compact conformation, small volume, efficiency high, and output voltage amplitude and frequency can be with independent controls.
Due to the presence of high frequency transformer leakage inductance, during the high frequency chain matrix inverter change of current, become in transformer secondary matrix
Produce larger voltage overshoot on the power tube of parallel operation, thus transformer secondary matrix/frequency converter Safe commutation always
It is to restrict the technological difficulties that high-frequency chain inverter is realized promoting on a large scale.Mainly there are following several Safe commutation strategies at present：①
Suppress voltage overshoot by adding active-clamp, it is possible to achieve Sofe Switch, but the clamp circuit for introducing increased cost, increase
Controlled power pipe also make control increasingly complex；2. unipolarity and bi-polarity phase-shifted control strategy by frequency converter the change of current
Overlap realizes the nature commutation of inductive current, and realizes the ZVS of power tube, but it is whard to control to there is the commutation overlap time
The problems such as；3. introduce series resonant circuit in preceding-stage inversion device to realize the soft commutation of power tube, now require that power tube switches
Occur at the zero current moment, and controlled output energy demand judges resonance working condition so that control mode is complicated.
Although however, above-mentioned strategy can realize Safe commutation, causing the modulation and control of inverter increasingly complex, lead
Cause system reliability to be lowered so that and have impact on promoting the use of for the quasi-converter.
The content of the invention
Present invention aim at providing, a kind of power conversion grade is few, modulate simple LC series resonances three-phase High Frequency Link square
The SVPWM of configuration inverter unhitches the series resonance modulator approach that coupling is combined with current mode.
To achieve the above object, following technical scheme is employed：Inverter topology of the present invention is connected humorous by full-bridge LC
Shake inverter, high frequency transformer T, matrix converter, CL mode filters is sequentially connected composition；
Full-bridge LC series resonant inverters are by DC input voitage Ui, controlled tr tube S1, controlled tr tube S2, controllable open
Close pipe S3, controlled tr tube S4, inductance Lr, electric capacity CrComposition；
Matrix converter is by controlled tr tube S1a, controlled tr tube S4b, controlled tr tube S4a, controlled tr tube S1b, it is controllable
Switching tube S3a, controlled tr tube S6b, controlled tr tube S6a, controlled tr tube S3b, controlled tr tube S5a, controlled tr tube S2b、
Controlled tr tube S2a, controlled tr tube S5bComposition；
CL mode filters are by the first inductance Lf1, the second inductance Lf2, the 3rd inductance Lf3, the first electric capacity Cf1, the second electric capacity Cf2、
3rd electric capacity Cf3, load R1, load R2, load R3Composition；
DC input voitage UiPositive pole respectively with controlled tr tube S1Colelctor electrode, controlled tr tube S3Colelctor electrode phase
Even, DC input voitage UiNegative pole respectively with controlled tr tube S2Emitter stage, controlled tr tube S4Emitter stage be connected；
Controlled tr tube S1Emitter stage respectively with inductance LrOne end, controlled tr tube S2Colelctor electrode be connected；It is controllable to open
Close pipe S3Emitter stage respectively with high frequency transformer T primary sides one end, controlled tr tube S4Colelctor electrode be connected, inductance LrIt is another
End and electric capacity CrOne end connection, electric capacity CrThe other end be connected with the other end of high frequency transformer T primary sides；
One end of high frequency transformer T secondary respectively with controlled tr tube S1aColelctor electrode, controlled tr tube S3aCurrent collection
Pole, controlled tr tube S5aColelctor electrode be connected, the other end of transformer T secondary respectively with controlled tr tube S1bColelctor electrode, can
Control switching tube S3bColelctor electrode, controlled tr tube S5bColelctor electrode be connected；Controlled tr tube S1aEmitter stage and controlled tr tube
S4bEmitter stage be connected, controlled tr tube S3aEmitter stage and controlled tr tube S6bEmitter stage be connected, controlled tr tube S5a's
Emitter stage and controlled tr tube S2bEmitter stage be connected；Controlled tr tube S1bEmitter stage and controlled tr tube S4aEmitter stage
It is connected, controlled tr tube S3bEmitter stage and controlled tr tube S6aEmitter stage be connected, controlled tr tube S5bEmitter stage with can
Control switching tube S2aEmitter stage be connected；
Controlled tr tube S4aColelctor electrode and controlled tr tube S4bColelctor electrode be connected after respectively with the first electric capacity Cf1One
End, the first inductance Lf1One end is connected, the first inductance Lf1The other end and load R1One end is connected, and loads R1The other end respectively with load
R2, load R3It is connected；First electric capacity Cf1The other end respectively with the second electric capacity Cf2, the 3rd electric capacity Cf3It is connected；
Controlled tr tube S6aColelctor electrode and controlled tr tube S6bColelctor electrode be connected after respectively with the second electric capacity Cf2,
Two inductance Lf2One end is connected, the second inductance Lf2The other end and load R2One end is connected, and loads R2The other end respectively with load R1, it is negative
Carry R3It is connected；Second electric capacity Cf2The other end respectively with the first electric capacity Cf1, the 3rd electric capacity Cf3It is connected；
Controlled tr tube S2aColelctor electrode and controlled tr tube S2bColelctor electrode be connected after respectively with the 3rd electric capacity Cf3,
Three inductance Lf3One end is connected, the 3rd inductance Lf3The other end and load R3One end is connected, and loads R3The other end respectively with load R1, it is negative
Carry R2It is connected；3rd electric capacity Cf3The other end respectively with the first electric capacity Cf1, the second electric capacity Cf2It is connected.
The excitation modulator approach of LC series resonances three-phase high frequency chain matrix inverter topology of the present invention, full-bridge LC strings
Connection resonance inverter is controlled using the PWM of certain dutycycle, the controlled tr tube S1, controlled tr tube S4The bridge arm of composition and
Controlled tr tube S2, controlled tr tube S3The bridge arm alternate conduction of composition, makes circuit be in half excitation resonant condition, that is, do not reaching
To shut-off controlled tr tube S during the resonance half period1, controlled tr tube S2, controlled tr tube S3, controlled tr tube S4, terminate circuit
Excitation resonant operational state；Transformer output area is certain and resonance current periodic regression is zero；The matrix of transformer rear class
Converter is equivalent to two groups of common current source inverters and carries out coupling control of unhitching, and is unhitched coupling logic modulation circuit according to current mode
To controlled tr tube S1a~controlled tr tube S6a, controlled tr tube S1b~controlled tr tube S6bIt is controlled, transformer T is defeated
The high-frequency resonant electric current conversion low frequency pulsating electric current for going out.
Further, full-bridge LC series resonant inverters controlled tr tube S conducting dutycycles within the resonance half period are certain,
Its excitation resonant operational state terminates after controlled tr tube S shut-offs, and it is zero that resonance current is returned rapidly, now transformer rear class square
Battle array variator carries out the positive and negative group of switching of switching tube.
Further, the matrix converter of transformer T rear classes is unhitched coupling control using current mode, and matrix converter is switched
Pipe resolves into positive and negative two groups, you can control switching tube S1a~S6aWith controlled tr tube S1b~S6b, negative group is opened when positive group switching tube works
Close pipe all off, and negative group switching tube is just being organized when working all off, rear class matrix converter can be with equivalent common into two groups
Current source inverter.
Further, during Vector operation, vector action time is directly proportional to the instantaneous value of three-phase input current, leads to
The instantaneous value for crossing given three-phase instruction input electric current just can directly determine corresponding vector action time.
The course of work approximately as：
Transformer preceding stage high frequency inverter introduces LC series resonance grooves, using the PWM control methods of certain dutycycle, makes humorous
The groove that shakes works in half excitation resonant condition.The matrix converter of transformer rear class is unhitched coupling phase using new SVPWM and current mode
With reference to modulator approach, by transformer export high-frequency ac current be converted into power current.
Compared with prior art, the invention has the advantages that：The application of LC resonant slots makes the power tube of transformer primary side
Zero current turning-on, and transformer primary secondary voltage without spike, opening for transformer secondary switching tube is in transformer primary side
During electric current is zero, the moment for causing voltage overshoot because interrupting secondary leakage inductance electric current is which reduced so that the loss of switch
Reduce, improve circuit reliability and efficiency.
Brief description of the drawings
Fig. 1 is inverter circuit topology figure of the present invention.
Fig. 2 is the system principle diagram of the inventive method.
Fig. 3 is new SVPWM to unhitch the half excitation resonant modulation method operation principle oscillogram that coupling is combined with current mode.
Fig. 4 is the resonant condition equivalent operation schematic diagram of resonant slots circuit.
Fig. 5 is that transformer secondary matrix converter unhitches coupling schematic diagram in current mode.
Fig. 6 half is encouraged at resonance logic for what the new SVPWM of three-phase high-frequency inverter unhitched that coupling is combined with current mode
Reason circuit diagram.
Fig. 7 is LC series resonance-type three-phases one high frequency period of high frequency chain matrix inverter under the inventive method control
Interior mode circuit diagram.
Specific embodiment
The present invention will be further described below in conjunction with the accompanying drawings：
LC series resonances three-phase high frequency chain matrix inverter of the present invention topology by full-bridge LC series resonant inverters,
High frequency transformer T, matrix converter, CL mode filters are sequentially connected composition；Transformer preceding stage high frequency inverter circuit introduces LC strings
Connection resonant slots, export change to be dominated by electric current, DC input voitage UiBe converted to resonance current ip, coupled by high frequency transformer defeated
Go out to transformer secondary, modulated through transformer rear class matrix converter, by filter filtering output low frequency sinusoidal voltage Uo。
Full-bridge LC series resonant inverters are by DC input voitage Ui, controlled tr tube S1, controlled tr tube S2, controllable open
Close pipe S3, controlled tr tube S4, inductance Lr, electric capacity CrComposition；Matrix converter is by controlled tr tube SP1, controlled tr tube SP2, can
Control switching tube SP3, controlled tr tube SP4, controlled tr tube SN1, controlled tr tube SN2, controlled tr tube SN3, controlled tr tube SN4
Composition；CL mode filters are by the first inductance Lf1, the second inductance Lf2, the 3rd inductance Lf3, the first electric capacity Cf1, the second electric capacity Cf2,
Three electric capacity Cf3, load R1, load R2, load R3Composition；
As shown in figure 1, DC input voitage UiPositive pole respectively with controlled tr tube S1Colelctor electrode, controlled tr tube S3
Colelctor electrode be connected, DC input voitage UiNegative pole respectively with controlled tr tube S2Emitter stage, controlled tr tube S4Transmitting
Extremely it is connected；
Controlled tr tube S1Emitter stage respectively with inductance LrOne end, controlled tr tube S2Colelctor electrode be connected；It is controllable to open
Close pipe S3Emitter stage respectively with high frequency transformer T primary sides one end, controlled tr tube S4Colelctor electrode be connected, inductance LrIt is another
End and electric capacity CrOne end connection, electric capacity CrThe other end be connected with the other end of high frequency transformer T primary sides；
One end of high frequency transformer T secondary respectively with controlled tr tube S1aColelctor electrode, controlled tr tube S3aCurrent collection
Pole, controlled tr tube S5aColelctor electrode be connected, the other end of transformer T secondary respectively with controlled tr tube S1bColelctor electrode, can
Control switching tube S3bColelctor electrode, controlled tr tube S5bColelctor electrode be connected；Controlled tr tube S1aEmitter stage and controlled tr tube
S4bEmitter stage be connected, controlled tr tube S3aEmitter stage and controlled tr tube S6bEmitter stage be connected, controlled tr tube S5a's
Emitter stage and controlled tr tube S2bEmitter stage be connected；Controlled tr tube S1bEmitter stage and controlled tr tube S4aEmitter stage
It is connected, controlled tr tube S3bEmitter stage and controlled tr tube S6aEmitter stage be connected, controlled tr tube S5bEmitter stage with can
Control switching tube S2aEmitter stage be connected；
Controlled tr tube S4aColelctor electrode and controlled tr tube S4bColelctor electrode be connected after respectively with the first electric capacity Cf1One
End, the first inductance Lf1One end is connected, the first inductance Lf1The other end and load R1One end is connected, and loads R1The other end respectively with load
R2, load R3It is connected；First electric capacity Cf1The other end respectively with the second electric capacity Cf2, the 3rd electric capacity Cf3It is connected；
Controlled tr tube S6aColelctor electrode and controlled tr tube S6bColelctor electrode be connected after respectively with the second electric capacity Cf2,
Two inductance Lf2One end is connected, the second inductance Lf2The other end and load R2One end is connected, and loads R2The other end respectively with load R1, it is negative
Carry R3It is connected；Second electric capacity Cf2The other end respectively with the first electric capacity Cf1, the 3rd electric capacity Cf3It is connected；
Controlled tr tube S2aColelctor electrode and controlled tr tube S2bColelctor electrode be connected after respectively with the 3rd electric capacity Cf3,
Three inductance Lf3One end is connected, the 3rd inductance Lf3The other end and load R3One end is connected, and loads R3The other end respectively with load R1, it is negative
Carry R2It is connected；3rd electric capacity Cf3The other end respectively with the first electric capacity Cf1, the second electric capacity Cf2It is connected.
As shown in Fig. 2 modulator approach of the present invention is as follows：
Full-bridge LC series resonant inverters are controlled using the PWM of certain dutycycle, the controlled tr tube S1, gate-controlled switch
Pipe S4The bridge arm and controlled tr tube S of composition2, controlled tr tube S3The bridge arm alternate conduction of composition, is in circuit and partly encourages humorous
Shake state, i.e., controlled tr tube S is turned off in the not up to resonance half period1, controlled tr tube S2, controlled tr tube S3, controllable open
Close pipe S4, terminate circuit activation resonant operational state；Transformer output area is certain and resonance current periodic regression is zero；Become
The matrix converter of depressor rear class is equivalent to two groups of common current source inverters and carries out coupling control of unhitching, and is unhitched according to current mode
Coupling logic modulation circuit is to controlled tr tube S1a~controlled tr tube S6a, controlled tr tube S1b~controlled tr tube S6bControlled
System, the high-frequency resonant electric current that transformer T is exported changes low frequency pulsating electric current.
Fig. 2 includes that PWM and SVPWM information Risk factor, SVPWM unhitch the half period excitation that coupling is combined with current mode
Resonant modulation logic processing circuit and controlled device LC series resonance three-phase high frequency chain matrix inverters, wherein PWM and
SVPWM information Risk factor produces the pwm signal and six road SPWM signals of a pair of complementations, and transfers to SVPWM to be unhitched with current mode
The half excitation resonant modulation logic circuit that coupling is combined carries out signal transacting, and gained drive signal can become transformer rear class matrix
Parallel operation is modulated into two common current source inverters and carries out coupling control of unhitching, and controls transformer prime LC series-resonant invertings
The signal and pwm signal of device realize that DC/AC is converted with frequency different duty, are carried out during transformer zero current is exported
The switching of matrix converter switching tube, realizes Zero Current Switch.
Half period excitation resonance of the present invention refers to that the ON time of transformer preceding stage high frequency inverter switching device pipe is
The half period of LC series resonances, resonance current is tied rapidly by the anti-paralleled diode afterflow of switching tube after switching tube shut-off
Shu Jili resonant conditions, prime resonance electric current is zeroed rapidly.Unhitched coupling for current mode of the present invention, comprising
" decoupling " and " knot coupling " two parts work.First, decoupling work is directed to the analysis of circuit feature and physical connection, decomposition pressure swing
Device output alternating current is DC pulse electric current, and it is unidirectional gate-controlled switch circuit to decompose two-way gate-controlled switch circuit, therefore can be by week
Wave converter is decoupled into positive and negative two groups of common current source inverters.Second, knot coupling work then lays particular emphasis on logical conversion and control
Realize, its core controls the thinking to be：Positive group inverter bears group inverter power tube when working is completely in off state, together
Reason, the power tube for bearing positive group inverter when group inverter works is all off, according to transformer output current polarity and output end
The polar selecting switch pipe conducting of three-phase main-frequency sinusoidal modulation signal.
Fig. 3 is new SVPWM encourages resonant modulation method operation principle ripple with current mode half period that coupling is combined of unhitching
Shape figure.U in figurep、UnIt is respectively transformer primary secondary voltage, irIt is transformer primary side resonance current, S1、S4And S2、S3It is transformation
The drive signal of device preceding stage high frequency inverter power pipe, V1、V2It is and carrier frequency identical complementation high-frequency square-wave signal, S1a~
S6a、S1b~S6bIt is the drive signal of transformer rear class matrix converter power tube.As seen from Figure 3, transformer primary side is high
Frequency inverter switching device pipe S1、S4And S2、S3It is to be turned within the resonance half period, circuit activation resonant condition after switching tube shut-off
Terminate, the resonance current in resonant slots quickly falls to zero, terminates the energy transmission to load-side, so referred to as half period excitation
Resonant modulation.Filter capacitor short circuit, the two-way switch of transformer rear class matrix converter when at any time, in order to avoid the change of current
Pipe cannot simultaneously be opened and turned off, it is necessary to timesharing driving, i.e., every two-way switch pipe all only has a switching tube open-minded, another
Diode is only equivalent to, switch switching has Dead Time.
Fig. 4 is the resonant condition equivalent operation schematic diagram of resonant slots circuit.Wherein UiIt is DC input voitage, UCf/ n is defeated
Go out the equivalent magnitude of voltage to transformer primary side of filter capacitor voltage, n is transformer voltage ratio, UrIt is resonant network both end voltage, irFor
Resonance current.Resonance circuit can be divided into excitation resonance and feedback resonance two states under the modulation system, as switching tube S1、S4
Or S2、S3During conducting, circuit is in excitation resonant condition, DC input voitage UiAs voltage drive source, with equivalent voltage UCf/n
Subtract each other and act on resonant network, resonant network both end voltage UrWith resonance current irSame-phase is kept, energy is by DC voltage through humorous
Vibrating network is transmitted to outlet side；After switching tube is all off, circuit is in feedback resonant condition, DC input voitage UiWith etc.
Effect voltage UCf/ n is added acting in opposition in resonant network, resonance current is declined rapidly, resonant network both end voltage UrAnd resonance
Electric current irKeep 180 degree anti-phase, energy is transmitted from resonant network to DC voltage and outlet side, and resonance current reduces rapidly.
Fig. 5 is the circuit decoupling principle figure of transformer rear class matrix converter.The modulator approach makes matrix converter equivalent
Resolve into two common current source inverters.When transformer imput current is timing, the S of positive group inverter1a、S2a、S3a、S4a、
S5a、S6aConducting, bears group inverter S1b、S2b、S3b、S4b、S5b、S6bIt is off state；Transformer imput current signal is negative
When, bear group inverter S1b、S2b、S3b、S4b、S5b、S6bConducting, the S of positive group inverter1a、S2a、S3a、S4a、S5a、S6aIt is off
State.
Fig. 6 is that the SVPWM of the LC series resonance-type three-phase high frequency chain matrix inverters is combined with the current mode coupling that unhitches
Half period excitation resonance logic processing circuit.V1、V2It is the signal with carrier wave with frequency, V1Negate and just obtained V2, through overvoltage
Six road signals of Vector Modulation output are respectively SPWM1, SPWM2, SPWM3, SPWM4, SPWM5, SPWM6, by SPWM1 and V1
Carry out logic and operation and obtain S1a, SPWM3 and V1Carry out logic and operation and obtain S3a, SPWM5 and V1Logic and operation is carried out to obtain
To S5a, SPWM4 and V2Carry out logic and operation and obtain S4b, SPWM6 and V2Carry out logic and operation and obtain S6b, SPWM2 and V2Enter
Row logic and operation obtains S2b, SPWM4 and V1Carry out logic and operation and obtain S4a, SPWM6 and V1Logic and operation is carried out to obtain
S6a, SPWM2 and V1Carry out logic and operation and obtain S2a, SPWM1 and V2Carry out logic and operation and obtain S1b, SPWM3 and V2Carry out
Logic and operation obtains S3b, SPWM5 and V2Carry out logic and operation and obtain S5b。
Fig. 7 is SVPWM of the present invention to unhitch under the half period excitation resonant modulation method control that coupling is combined with current mode
Each stage equivalent circuit diagram of LC mode of resonance three-phase high frequency chain matrix inverters.Figure (a)~(j) is respectively following operation modes 1
~10.It is assumed that all components in topology are preferable component, according to operation principle, there is 10 in a high frequency period
Individual working condition, specific model analysis is as follows：
1) [the t of operation mode 10-t1], t0Moment switching tube S1、S4Conducting, DC input voitage UiIt is added in LC series resonance grooves
On, resonance current ipRise, and speed, matrix converter switching tube S3a、S6aIn the conduction state, other switching tubes are in
Off state, direct current input side energy is transmitted by resonant slots to load-side, and now resonance circuit is in excitation resonant condition, defeated
Go out filter capacitor CfWith inductance LfPlace's freewheeling state on last stage.
2) [the t of operation mode 21-t2], t1Moment switching tube S1、S4Continue to turn on, matrix converter switching tube S3aShut-off, opens
Close pipe S5aTurn on, now DC input voitage UiThe voltage difference to transformer primary side equivalent with filter capacitor is added in resonant slots
On, make resonance current irContinue to rise, slow before speed ratio, direct current input side energy continues to be transmitted to load-side.Filtering net
C phases electric capacity charges in network, the electric discharge of a, b phase electric capacity.
3) [the t of operation mode 32-t3], t2Moment switching tube S1、S4Continue to turn on, matrix converter switching tube S5aShut-off, opens
Close pipe S1aConducting, DC input voitage UiThe voltage difference to transformer primary side equivalent with filter capacitor is still added in resonant slots,
Resonance current irKeep rising, speed is slower, direct current input energy continues to be transmitted to load-side.A phases electric capacity fills in filter network
Electricity, the electric discharge of b, c phase electric capacity.
4) [the t of operation mode 43-t4], in t3Moment switching tube S1、S4Continue to turn on, matrix converter switching tube S1aShut-off,
Switching tube S3aConducting, resonance current irRise, and speed, export the state that filter network remains a mode.
5) [the t of operation mode 54-t5], in t4Moment switching tube S1、S4Shut-off, excitation resonant condition terminates, and resonance current leads to
Cross switching tube S2、S3Anti-paralleled diode afterflow, energy is back to DC terminal by resonant network, until resonance current is zero, filter
Wave network still remains the continuous current circuit of a mode.
6) [the t of operation mode 65-t6], in t5Moment switching tube S2、S3It is open-minded, DC input voitage UiReversely it is added in resonant slots
On, now resonance circuit is in excitation resonant condition, resonance current irNegative sense increases.Rear class matrix converter switching tube S3b、S6b
It is in the conduction state, secondary voltage clamper to zero.Filter network state is identical with previous mode.
7) [the t of operation mode 76-t7], in t6Moment switching tube S2、S3Continue to turn on, now DC input voitage UiAnd filtering
The equivalent voltage difference to transformer primary side of capacitance voltage is added in resonant slots, resonance current irThe rate of climb slows down.Rear class square
Battle array converter switches pipe S6bShut-off, S2bIn the conduction state, b phases electric capacity charges in filter network, the electric discharge of a, c phase electric capacity.
8) [the t of operation mode 87-t8], in t7Moment switching tube S2、S3Still turn on, DC input voitage UiWith filter capacitor electricity
The equivalent voltage difference to transformer primary side is pressed to be added in resonant slots, resonance current irThe rate of climb is slow.Matrix converter is opened
Close pipe S2bShut-off, S4bIn the conduction state, b phases electric capacity charges in filter network, the electric discharge of a, c phase electric capacity.
9) [the t of operation mode 98-t9], in t8Moment switching tube S2、S3Still turn on, only dc source acts on Resonance Neural Network
Network, resonance current irThe rate of climb is very fast.Switching tube S4bShut-off, S6bIt is open-minded, transformer secondary voltage clamping to zero.Filter network
In freewheeling state.
10) [the t of operation mode 109-t10], in t9Moment switching tube S2、S3Shut-off, resonance current irBy switching tube S1、S4
Anti-paralleled diode carry out afterflow, to DC terminal, until resonance current is zero, secondary voltage is still for the energy feedback of resonant network
It is clamped to zero.The state of filter network is identical with previous mode.
It is fixed that the operative duty cycles of transformer prime resonance circuit excitation resonant condition are can be seen that by the above course of work
Value, if changing the size of dutycycle, then the energy transmitted to load-side changes therewith, periodically returns in guarantee resonance current
Under conditions of zero certain dutycycle, positive and negative group of switching tube of transformer rear class frequency converter switches during zero current is exported,
Reduce switching loss.
Example discussed above is only that the preferred embodiment of the present invention is described, not to the scope of the present invention
It is defined, on the premise of design spirit of the present invention is not departed from, those of ordinary skill in the art are to technical scheme
The various modifications made and improvement, all should fall into the protection domain of claims of the present invention determination.
Claims (5)
1. a kind of LC series resonance-types three-phase high frequency chain matrix inverter is topological, it is characterised in that：The inverter topology by
Full-bridge LC series resonant inverters, high frequency transformer T, matrix converter, CL mode filters are sequentially connected composition；
Full-bridge LC series resonant inverters are by DC input voitage Ui, controlled tr tube S1, controlled tr tube S2, controlled tr tube
S3, controlled tr tube S4, inductance Lr, electric capacity CrComposition；
Matrix converter is by controlled tr tube S1a, controlled tr tube S4b, controlled tr tube S4a, controlled tr tube S1b, gate-controlled switch
Pipe S3a, controlled tr tube S6b, controlled tr tube S6a, controlled tr tube S3b, controlled tr tube S5a, controlled tr tube S2b, it is controllable
Switching tube S2a, controlled tr tube S5bComposition；
CL mode filters are by the first inductance Lf1, the second inductance Lf2, the 3rd inductance Lf3, the first electric capacity Cf1, the second electric capacity Cf2, the 3rd
Electric capacity Cf3, load R1, load R2, load R3Composition；
DC input voitage UiPositive pole respectively with controlled tr tube S1Colelctor electrode, controlled tr tube S3Colelctor electrode be connected, directly
Stream input voltage UiNegative pole respectively with controlled tr tube S2Emitter stage, controlled tr tube S4Emitter stage be connected；
Controlled tr tube S1Emitter stage respectively with inductance LrOne end, controlled tr tube S2Colelctor electrode be connected；Controlled tr tube
S3Emitter stage respectively with high frequency transformer T primary sides one end, controlled tr tube S4Colelctor electrode be connected, inductance LrThe other end with
Electric capacity CrOne end connection, electric capacity CrThe other end be connected with the other end of high frequency transformer T primary sides；
One end of high frequency transformer T secondary respectively with controlled tr tube S1aColelctor electrode, controlled tr tube S3aColelctor electrode, controllable
Switching tube S5aColelctor electrode be connected, the other end of transformer T secondary respectively with controlled tr tube S1bColelctor electrode, gate-controlled switch
Pipe S3bColelctor electrode, controlled tr tube S5bColelctor electrode be connected；Controlled tr tube S1aEmitter stage and controlled tr tube S4bHair
Emitter-base bandgap grading is connected, controlled tr tube S3aEmitter stage and controlled tr tube S6bEmitter stage be connected, controlled tr tube S5aEmitter stage
With controlled tr tube S2bEmitter stage be connected；Controlled tr tube S1bEmitter stage and controlled tr tube S4aEmitter stage be connected, can
Control switching tube S3bEmitter stage and controlled tr tube S6aEmitter stage be connected, controlled tr tube S5bEmitter stage and gate-controlled switch
Pipe S2aEmitter stage be connected；
Controlled tr tube S4aColelctor electrode and controlled tr tube S4bColelctor electrode be connected after respectively with the first electric capacity Cf1One end,
One inductance Lf1One end is connected, the first inductance Lf1The other end and load R1One end is connected, and loads R1The other end respectively with load R2, it is negative
Carry R3It is connected；First electric capacity Cf1The other end respectively with the second electric capacity Cf2, the 3rd electric capacity Cf3It is connected；
Controlled tr tube S6aColelctor electrode and controlled tr tube S6bColelctor electrode be connected after respectively with the second electric capacity Cf2, second electricity
Sense Lf2One end is connected, the second inductance Lf2The other end and load R2One end is connected, and loads R2The other end respectively with load R1, load R3
It is connected；Second electric capacity Cf2The other end respectively with the first electric capacity Cf1, the 3rd electric capacity Cf3It is connected；
Controlled tr tube S2aColelctor electrode and controlled tr tube S2bColelctor electrode be connected after respectively with the 3rd electric capacity Cf3, the 3rd electricity
Sense Lf3One end is connected, the 3rd inductance Lf3The other end and load R3One end is connected, and loads R3The other end respectively with load R1, load R2
It is connected；3rd electric capacity Cf3The other end respectively with the first electric capacity Cf1, the second electric capacity Cf2It is connected.
2. it is a kind of based on described in claim 1 LC series resonances three-phase high frequency chain matrix inverter topology excitation modulation methods
Method, it is characterised in that：Full-bridge LC series resonant inverters are controlled using the PWM of certain dutycycle, the controlled tr tube S1, can
Control switching tube S4The bridge arm and controlled tr tube S of composition2, controlled tr tube S3The bridge arm alternate conduction of composition, makes circuit be in half
Excitation resonant condition, i.e., turn off controlled tr tube S in the not up to resonance half period1, controlled tr tube S2, controlled tr tube S3、
Controlled tr tube S4, terminate circuit activation resonant operational state；Transformer exports area necessarily and resonance current periodic regression
It is zero；The matrix converter of transformer rear class is equivalent to two groups of common current source inverters and carries out coupling control of unhitching, according to electricity
Flow pattern unhitches coupling logic modulation circuit to controlled tr tube S1a~controlled tr tube S6a, controlled tr tube S1b~controlled tr tube
S6bIt is controlled, the high-frequency resonant electric current that transformer T is exported changes low frequency pulsating electric current.
3. excitation modulator approach according to claim 2, it is characterised in that：Full-bridge LC series resonant inverters are in resonance half
Controlled tr tube S conducting dutycycles are certain in cycle, and its excitation resonant operational state terminates after controlled tr tube S shut-offs, resonance
It is zero that electric current is returned rapidly, and now transformer rear class matrix converter carries out the positive and negative group of switching of switching tube.
4. excitation modulator approach according to claim 2, it is characterised in that：The matrix converter of transformer T rear classes is used
Current mode is unhitched coupling control, and matrix converter switching tube is resolved into positive and negative two groups, you can control switching tube S1a~S6aOpened with controllable
Close pipe S1b~S6b, negative group switching tube is all off during positive group switching tube work, and positive group is all closed during negative group switching tube work
Disconnected, rear class matrix converter can be with equivalent into two groups of common current type inverters.
5. half period according to claim 2 excitation modulator approach, it is characterised in that：During Vector operation, vector
Action time is directly proportional to the instantaneous value of three-phase input current, just can be with by the instantaneous value of the three-phase instruction input electric current for giving
Directly determine corresponding vector action time.
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