Compact Planar Magneto-Electric Dipole-Like Circul
Compact Planar Magneto-Electric Dipole-Like Circul
Compact Planar Magneto-Electric Dipole-Like Circul
DOI: 10.1049/cmu2.12499
ORIGINAL RESEARCH
1
Department of Electronics and Communication Abstract
Engineering, Visvesvaraya National Institute of
A novel circularly polarized (CP) substrate integrated magneto-electric dipole (MED)
Technology, Nagpur, Maharashtra, India
2
antenna has been designed for appropriate wireless communication. The antenna com-
Department of Electrical Engineering, College of
Engineering, Jouf University, Sakaka, Aljouf, Saudi
prises two printed radiating arc-shaped patches and a feeding strip on top, two rows of
Arabia embedded metallic vias, and a ground plane. A coax probe is used to excite the patches
3
Department of Electronics and Communication and via rows simultaneously with the help of a printed feeding strip. Finally, the antenna
Engineering, SRM University AP, Amravati, India design has been prototyped and its performance experimentally was verified in terms of
4
School of Electronics Engineering, Vellore Institute impedance bandwidth, axial-ratio (AR), gain, efficiency, and radiation patterns. The mea-
of Technology, Vellore, India sured impedance bandwidth (under −10 dB) and AR bandwidth (under 3 dB) are 6.15–7.01
5
School of Electrical and Computer Engineering, (13%) GHz and 6.24–6.40 (2.53%) GHz respectively. Typically, the measured gain value
Shiraz University, Shiraz, Iran within 3-dB AR bandwidth at 6.3 GHz is 4.5 dBic with average measured in-band antenna
efficiency of 85.2%. Moreover, the proposed antenna shows an acceptable agreement with
Correspondence
predicted counterparts, including unidirectional radiation patterns.
Farnaz Ahmadfard, School of Electrical and
Computer Engineering Shiraz University, Shiraz,
Iran.
Email: fahmadfard@gmail.com
This is an open access article under the terms of the Creative Commons Attribution License, which permits use, distribution and reproduction in any medium, provided the original work is
properly cited.
© 2022 The Authors. IET Communications published by John Wiley & Sons Ltd on behalf of The Institution of Engineering and Technology.
0 10 0 10
S11, (dB)
-10
S11, (dB)
-10
0 0
-20 -20
-5 -5
0 0
5.5 6.0 6.5 7.0 7.5 5.5 6.0 6.5 7.0 7.5
Frequency, (GHz) Frequency, (GHz)
(c) (c)
FIGURE 3 Simulated results for different values of parameter ‘wp ’: FIGURE 4 Simulated results for different values of parameter ‘a’:
(a) Reflection coefficient (S11 ), (b) gain, and (c) axial-ratio (AR) (a) Reflection coefficient (S11 ), (b) gain and (c) axial-ratio (AR)
effect of the parameter ‘wp ’ (i.e. the width of the patch) on the
antenna performance is shown in Figure 3. The outer circum-
ference of the proposed patch can be changed by increasing the
outer radius, this helps in the shifting of the centre frequency.
As the value of the ‘wp ’ increases, the size of the electric dipole
(patch) increases and vice-versa. Thus, the resonant frequency
can be tuned at the lower and higher end of the desired fre-
quency in sub-6 GHz band as shown in Figure 3a. Moreover,
the operating bandwidth also can be controlled by tuning this
parameter, while gain and AR are affected at minimum extends
as shown in Figure 3b,c. Probe-feed location on the metallic
strip plays a critical role in matching the proper input impedance FIGURE 5 Prototyped sample of the proposed antenna
due to its function of coupling the electromagnetic energy. 50 Ω
input impedance on the metallic strip is realized with the help of
the trial-method. c. Implant the two rows of metallic vias as close as to the inner
Figure 4 shows the influence of parameter ‘a’ on the antenna corner of patches.
performance. The parameter ‘a’ is the location of the coax- d. Use coax probe and feeding strip to excite magneto and elec-
probe on the feeding strip, and the length of this strip is tric dipoles, simultaneously (as shown in Figure 1). Tune
maintained the same as ‘wp ’ parameter. Thus, parameter ‘a’ is the feeding point and inner radius to achieve better input
optimized to tune the coax probe at 50 Ω. Also, this parame- impedance matching.
ter controls the phase difference between two curved patches.
It is noted that by mirroring the parameter ’a’ around the
centroid, LHCP radiation can be realized. Furthermore, it 3 EXPERIMENTAL RESULTS AND
is observed that the gain in above-mentioned cases remains VERIFICATIONS
consistent.
Finally, brief design steps for the proposed antenna are To confirm the expected performance of the antenna, the
summarized as: design is prototyped and results are tested experimentally. The
antenna is prototyped on dielectric material Rogers RO4003C
a. Choose the proper thickness of the dielectric substrate, (ide- as shown in the photograph (Figure 5). The input impedance
ally height of the magneto-electric dipole antenna should matching and far-field radiation patterns are tested by Anritsu
be 𝜆g ∕4, however larger thickness may lead to the excita- (Shock-Line MS46122B series) network analyzer and an ane-
tion of unwanted surface waves). Here, 𝜆g is the guiding choic chamber. Simulated and measured reflection coefficients
wavelength at the centre frequency of the operating band. (S-parameter) of the antenna are plotted in Figure 6. The sim-
b. Design two identical annular arc-shaped dipoles. Opt the ulated S-parameter shows that the bandwidth of the antenna
length of the outer arc as 0.5𝜆g . is extending from 6.10 to 6.90 GHz, 815 MHz, while the
KUMAR ET AL. 2451
10 10
Sim. RHCP
5 5 Sim. LHCP
Meas. RHCP
0 0 Meas. LHCP
-5 -5 0 0
100 40
95 measurement is referenced back to the phase and magnitude of
35
90 the source. If we use the same measurement antenna (e.g. a horn
85 30
antenna) and rotate it 90o to capture each component, then
Antenna efficiency, %
80
Axial ratio, dB
BW in GHz, (%) 4.98–6.01 (18) 5.01–5.92 (13) 5.63–5.88 (4.3) 6.15–7.01 (13)
height (h) 6.0 mm 5.0 mm 2.0 mm 3.0 mm
(λo ) (0.111λo ) (0.091λo ) (0.039λo ) (0.050λo )
ARBW (%) – – 4.3 2.5
Peak gain 6.8 6.4 2.4 4.5
dBi dBi dBic dBic
Cross pol. 22 >15 dB 10 ∼12 dB
Effi. (%) 81 – 62 85.2
Size (mm3 ) 36 × 36 × 6.0 37 × 37 × 5.0 90 × 17 × 2.0 36 × 36 × 3.0
Remarks Multilayer PCBs; Complex Multilayer PCBs; Complex Single-layer PCB; simple Single layer PCB; simple
fabrication fabrication design, Narrow impedance design; wide impedance
BW band BW
magneto-electric dipole antennas [12, 13], the design maintains DATA AVAILABILITY STATEMENT
a low-profile and planar structure of 0.05𝜆o in thickness. Data sharing not applicable – no new data generated Data shar-
The originality of this work is to introduce a design to ing is not applicable to this article as no new data were created
decrease the height of a planar MED antenna. This design is or analyzed in this study.
simpler than other designs available in the literature [14, 15,
23–25]. The proposed novel MED antenna also can be easily ORCID
realized by existing PCB on the single-layered substrate. Fur- Arvind Kumar https://orcid.org/0000-0002-9695-4399
thermore, the compact size (36 mm × 36 mm) of the antenna Ayman A. Althuwayb https://orcid.org/0000-0001-5160-
is encouraging towards realizing planar integration with wireless 5016
communication transceivers on restricted radio-frequency ele- Divya Chaturvedi https://orcid.org/0000-0003-0141-2034
ments space. The proposed design can be easily extended to a Rajkishor Kumar https://orcid.org/0000-0002-6140-1241
wideband CP array by opting suitable corporate feeding system. Farnaz Ahmadfard https://orcid.org/0000-0002-2962-3389
Besides, our proposed antenna is one of the good candidates
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