Nothing Special   »   [go: up one dir, main page]

You seem to have javascript disabled. Please note that many of the page functionalities won't work as expected without javascript enabled.
 
 
Sign in to use this feature.

Years

Between: -

Subjects

remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline

Journals

remove_circle_outline
remove_circle_outline
remove_circle_outline

Article Types

Countries / Regions

remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline

Search Results (1,635)

Search Parameters:
Keywords = permanent magnet motors

Order results
Result details
Results per page
Select all
Export citation of selected articles as:
53 pages, 2639 KiB  
Article
A New Paradigm in AC Drive Control: Data-Driven Control by Learning Through the High-Efficiency Data Set—Generalizations and Applications to a PMSM Drive Control System
by Madalin Costin and Ion Bivol
Sensors 2024, 24(22), 7313; https://doi.org/10.3390/s24227313 (registering DOI) - 15 Nov 2024
Abstract
This paper presents a new means to control the processes involving energy conversion. Electric machines fed by electronic converters provide a useful power defined by the inner product of two generalized energetic variables: effort and flow. The novelty in this paper is controlling [...] Read more.
This paper presents a new means to control the processes involving energy conversion. Electric machines fed by electronic converters provide a useful power defined by the inner product of two generalized energetic variables: effort and flow. The novelty in this paper is controlling the desired energetic variables by a Data-Driven Control (DDC) law, which comprises the effort and flow and the corresponding process control. The same desired useful power might be obtained with different controls at different efficiencies. Solving the regularization problem is based on building a knowledge database that contains the maximum efficiency points. Knowing a reasonable number of optimal efficiency operation points, an interpolation Radial Base Function (RBF) control was built. The RBF algorithm can be found by training and testing the optimal controls for any admissible operation points of the process. The control scheme developed for Permanent Magnet Synchronous Motor (PMSM) has an inner DDC loop that performs converter control based on measured speed and demanded torque by the outer loop, which handles the speed. A comparison of the DDC with the Model Predictive Control (MPC) of the PMSM highlights the advantages of the new control method: the method is free from the process nature and guarantees higher efficiency. Full article
(This article belongs to the Special Issue Magnetoelectric Sensors and Their Applications)
18 pages, 38170 KiB  
Article
Design of Small Permanent-Magnet Linear Motors and Drivers for Automation Applications with S-Curve Motion Trajectory Control and Solutions for End Effects and Cogging Force
by Chia-Hsiang Ho and Jonq-Chin Hwang
Energies 2024, 17(22), 5719; https://doi.org/10.3390/en17225719 - 15 Nov 2024
Abstract
This paper designs and fabricates a small-type permanent-magnet linear motor and driver for automation applications. It covers structural design, magnetic circuit analysis, control strategies, and hardware development. Magnetic circuit analysis software JMAG is used for flux density distribution, back electromotive force (back-EMF), and [...] Read more.
This paper designs and fabricates a small-type permanent-magnet linear motor and driver for automation applications. It covers structural design, magnetic circuit analysis, control strategies, and hardware development. Magnetic circuit analysis software JMAG is used for flux density distribution, back electromotive force (back-EMF), and electromagnetic force analysis. To address the lack of a complete closed magnetic circuit path at the ends of the linear motor, which causes magnetic field asymmetry, a phenomenon known as end effects, auxiliary core structures are proposed to compensate for the magnetic field at the ends. It successfully utilizes auxiliary cores to achieve the phase voltages of each phase, which are balanced at a phase voltage error of 0.02 V. To address the cogging force caused by variations in the magnetic reluctance of the core, this paper analyzes the relationship between electromagnetic force and mover position, conducting harmonic content analysis to obtain parameters. These parameters are applied to the designed cogging force control compensation strategy. It successfully achieves q-axis current compensation of around 1.05 A based on the mover’s position, ensuring that no jerking caused by cogging force occurs during closed-loop electromagnetic force control. The S-curve motion trajectory control is proposed to replace the traditional trapezoidal acceleration and deceleration, resulting in smoother position control of the linear motor. Simulations using JMAG-RT models in MATLAB/Simulink verified these control strategies. After verification, practical test results showed a maximum position error of approximately 5.0 μm. Practical tests show that the designed small-type permanent-magnet linear motor and its driver provide efficient, stable, and high-precision solutions for automation applications. Full article
(This article belongs to the Section F: Electrical Engineering)
Show Figures

Figure 1

Figure 1
<p>Cross-sectional view of the motor structure.</p>
Full article ">Figure 2
<p>Three-phase motor with 6 coils and 7-pole magnets: (<b>a</b>) wiring; (<b>b</b>) vector.</p>
Full article ">Figure 3
<p>Motor dimensions schematic diagram.</p>
Full article ">Figure 4
<p>Electromagnetic force from current control analysis with a peak current of 1 A per phase.</p>
Full article ">Figure 5
<p>Permanent-magnet linear motor closed-loop control block diagram of the dq-axis current with electromagnetic force ripple compensation.</p>
Full article ">Figure 6
<p>Three-phase motor with 6 coils and 7-pole magnets: (<b>a</b>) S-curve motion trajectory. (<b>b</b>) Trapezoidal motion trajectory.</p>
Full article ">Figure 7
<p>S-curve motion trajectory control block diagram.</p>
Full article ">Figure 8
<p>Permanent-magnet linear motor position closed-loop control block diagram.</p>
Full article ">Figure 9
<p>Simulation of electromagnetic force command <math display="inline"><semantics> <msubsup> <mi>F</mi> <mi>e</mi> <mo>*</mo> </msubsup> </semantics></math> = 5.46 N: (<b>a</b>) phase current of the linear motor; (<b>b</b>) dq-axis current; (<b>c</b>) electromagnetic force.</p>
Full article ">Figure 10
<p>Simulation of electromagnetic force command <math display="inline"><semantics> <msubsup> <mi>F</mi> <mi>e</mi> <mo>*</mo> </msubsup> </semantics></math> = 5.46 N with ripple compensation: (<b>a</b>) phase current of the linear motor; (<b>b</b>) dq-axis current; (<b>c</b>) electromagnetic force.</p>
Full article ">Figure 11
<p>Simulation of S-curve motion trajectory for mover position command <math display="inline"><semantics> <msubsup> <mi>Z</mi> <mi>m</mi> <mo>*</mo> </msubsup> </semantics></math> = 80 mm: (<b>a</b>) position; (<b>b</b>) speed; (<b>c</b>) acceleration.</p>
Full article ">Figure 12
<p>Small-type permanent-magnet linear motor driver block diagram.</p>
Full article ">Figure 13
<p>Physical implementation of the driver circuit: (<b>a</b>) front view; (<b>b</b>) rear view.</p>
Full article ">Figure 14
<p>Small-type permanent-magnet linear motor physical implementation.</p>
Full article ">Figure 15
<p>Small-type permanent-magnet linear motor pull-test platform.</p>
Full article ">Figure 16
<p>Small-type permanent-magnet linear motor back-EMF.</p>
Full article ">Figure 17
<p>Electromagnetic force test platform.</p>
Full article ">Figure 18
<p>With cogging force compensation and <math display="inline"><semantics> <msubsup> <mi>F</mi> <mrow> <mi>e</mi> </mrow> <mo>*</mo> </msubsup> </semantics></math> = 0.0 N control: (<b>a</b>) q-axis current feedback <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo stretchy="false">^</mo> </mover> <mi>q</mi> </msub> </semantics></math>; (<b>b</b>) position feedback <math display="inline"><semantics> <msub> <mover accent="true"> <mi>Z</mi> <mo stretchy="false">^</mo> </mover> <mi>m</mi> </msub> </semantics></math>.</p>
Full article ">Figure 19
<p>S-curve motion trajectory testing: (<b>a</b>) <math display="inline"><semantics> <msub> <mi>Z</mi> <mi>m</mi> </msub> </semantics></math> position curve; (<b>b</b>) <math display="inline"><semantics> <msub> <mi>υ</mi> <mi>m</mi> </msub> </semantics></math> speed curve.</p>
Full article ">
16 pages, 3155 KiB  
Article
Fixed-Time Consensus Multi-Agent-Systems-Based Speed Cooperative Control for Multiple Permanent Magnet Synchronous Motors with Complementary Sliding Mode Control
by Limin Hou and Xiaoru Lan
Electronics 2024, 13(22), 4407; https://doi.org/10.3390/electronics13224407 - 11 Nov 2024
Viewed by 342
Abstract
To improve the tracking performance and robustness of traditional multi-motor speed cooperative control, this paper proposes a speed cooperative control method for multiple permanent magnet synchronous motors (multi-PMSMs) based on the fixed-time consensus protocol for multi-agent systems (MASs) combined with CSMC. Firstly, the [...] Read more.
To improve the tracking performance and robustness of traditional multi-motor speed cooperative control, this paper proposes a speed cooperative control method for multiple permanent magnet synchronous motors (multi-PMSMs) based on the fixed-time consensus protocol for multi-agent systems (MASs) combined with CSMC. Firstly, the speed regulation system of multi-PMSMs is regarded as a MAS. By designing a distributed consensus protocol based on an undirected communication topology, the system achieves fixed-time consensus convergence. Then, a terminal integral sliding mode observer (TISMO) is designed to estimate disturbances, and feedforward compensation is introduced into the consensus protocol to obtain the desired q-axis current. Furthermore, within the framework of the vector control speed cooperative system of PMSMs, a CSMC is designed to track the q-axis reference current. Meanwhile, the stability of the above controllers and observers is theoretically proven using the Lyapunov functions. Finally, comparative experiments are conducted on a multi-PMSM speed regulation experimental platform to verify the proposed control method against the traditional deviation coupling control (DCC) method. The results indicate that under the new control method proposed in this paper, the chattering phenomenon is reduced by about 2 r/min compared to the traditional DCC method. During sudden load and sudden relief load conditions, the speed fluctuation is reduced by approximately 4%, demonstrating good tracking performance and strong robustness. Full article
(This article belongs to the Section Systems & Control Engineering)
Show Figures

Figure 1

Figure 1
<p>Schematic diagram of the traditional DCC method for multi-PMSMs.</p>
Full article ">Figure 2
<p>Schematic diagram of multi-PMSM control method.</p>
Full article ">Figure 3
<p>CSMC schematic diagram.</p>
Full article ">Figure 4
<p>Multi-motor speed control and load integration experimental platform.</p>
Full article ">Figure 5
<p>Comparative experimental results of speed-up and speed-down as well as forward and reverse operation. (<b>a</b>) Comparative curve of speed response. (<b>b</b>) Comparative curve of speed tracking error. (<b>c</b>) Comparative curve of speed synchronization error.</p>
Full article ">Figure 6
<p>Comparative experimental results of load addition and reduction. (<b>a</b>) Comparative curve of speed response. (<b>b</b>) Comparative curve of speed tracking error. (<b>c</b>) Comparative curve of speed synchronization error.</p>
Full article ">Figure 7
<p>Comparative experimental results of low-speed operation. (<b>a</b>) Comparative curve of speed response. (<b>b</b>) Comparative curve of speed tracking error. (<b>c</b>) Comparative curve of speed synchronization error.</p>
Full article ">
17 pages, 5582 KiB  
Article
A Novel Capacitance Estimation Method of Modular Multilevel Converters for Motor Drives Using Recurrent Neural Networks with Long Short-Term Memory
by Mehdi Syed Musadiq and Dong-Myung Lee
Energies 2024, 17(22), 5577; https://doi.org/10.3390/en17225577 - 8 Nov 2024
Viewed by 306
Abstract
Accurate estimation of submodule capacitance in modular multilevel converters (MMCs) is essential for optimal performance and reliability, particularly in motor drive applications such as permanent magnet synchronous motor (PMSM) drives. This paper presents a novel approach utilizing recurrent neural networks with long short-term [...] Read more.
Accurate estimation of submodule capacitance in modular multilevel converters (MMCs) is essential for optimal performance and reliability, particularly in motor drive applications such as permanent magnet synchronous motor (PMSM) drives. This paper presents a novel approach utilizing recurrent neural networks with long short-term memory (RNN–LSTM) to precisely estimate capacitance in MMC-based PMSM drives. By leveraging simulation data from MATLAB, the LSTM neural network is trained to predict capacitance based on voltage, current, and their temporal variations. The proposed LSTM architecture effectively captures the dynamic behavior of MMCs in PMSM drives, providing high-precision capacitance estimates. The results demonstrate significant improvements in estimation accuracy, validated through mean squared error (MSE) metrics and comparative analysis of actual versus estimated capacitance. The method’s robustness is further confirmed under varying operating conditions, highlighting its practical utility for real-time applications in power electronic systems. Full article
(This article belongs to the Section F3: Power Electronics)
Show Figures

Figure 1

Figure 1
<p>Schematic diagram of MMC-based PMSM drive system topology.</p>
Full article ">Figure 2
<p>Depicts the MMC connected to the PMSM drive, including control blocks for current and voltage regulation, measurement units for voltage, current and capacitor voltages, and interfaces for input parameters and load variations.</p>
Full article ">Figure 3
<p>Neural network structure for RNN layers.</p>
Full article ">Figure 4
<p>Flow chart of RNN–LSTM model working and testing.</p>
Full article ">Figure 5
<p>RNN–LSTM algorithm for capacitance estimation in an MMC motor drive.</p>
Full article ">Figure 6
<p>Regression response for the LSTM model.</p>
Full article ">Figure 7
<p>The simulation results at 500 W power level: (<b>a</b>) actual capacitance; (<b>b</b>) estimated capacitance.</p>
Full article ">Figure 8
<p>The simulation results at 400 W and 300 W power levels: (<b>a</b>) estimated capacitance at 400 W; (<b>b</b>) estimated capacitance at 300 W.</p>
Full article ">Figure 9
<p>Estimated capacitance by different power levels.</p>
Full article ">Figure 10
<p>Estimated capacitance by different fault conditions.</p>
Full article ">Figure 11
<p>Estimated capacitance by different techniques and its accuracy.</p>
Full article ">Figure 12
<p>Three-phase Current from simulation in current control block.</p>
Full article ">Figure 13
<p>Speed Reference and actual speed across the PMSM drive.</p>
Full article ">
16 pages, 3829 KiB  
Article
Research on Radial Vibration Model and Low-Frequency Vibration Suppression Method in PMSM by Injecting Multiple Symmetric Harmonic Currents
by Le Kang, He Zhang, Jiakuan Xia, Meijun Qi and Yunqi Zhao
Actuators 2024, 13(11), 448; https://doi.org/10.3390/act13110448 - 8 Nov 2024
Viewed by 349
Abstract
Driven by frequency conversion, the windings of a three-phase permanent magnet synchronous motor (PMSM) contain both odd and even harmonic currents. Due to the motor’s pole–slot conductance modulation, the interaction between the magnetic fields generated by these harmonic currents and the permanent magnet [...] Read more.
Driven by frequency conversion, the windings of a three-phase permanent magnet synchronous motor (PMSM) contain both odd and even harmonic currents. Due to the motor’s pole–slot conductance modulation, the interaction between the magnetic fields generated by these harmonic currents and the permanent magnet field results in harmonic radial vibrations of the motor. This paper analyzes the three-phase currents of the prototype and derives the radial magnetomotive force (MMF) spatiotemporal models for symmetric harmonic currents. By integrating Maxwell’s magnetic force formula and vibration response formula, the radial vibration models for symmetric harmonic currents are developed. The characteristics of vibrations caused by odd and even harmonic currents, as well as positive sequence and negative sequence harmonic currents, are analyzed separately. A cyclic sequence, low-frequency vibration suppression control method incorporating multiple harmonic current injections was designed. Experimental results of this method are compared with those obtained using an ideal sinusoidal current. Except for the second harmonic vibration, all other vibrations are significantly suppressed, with a maximum suppression rate of 92.28%. The total vibration level is reduced by 12.7619 dB, and the average torque is reduced by 0.67% with the total harmonic distortion of the current at 2.89%. The experimental results show that the vibration method in this paper has little influence on the average torque of the motor, the current distortion rate is small, and the vibration suppression effect is good. Full article
(This article belongs to the Section Control Systems)
Show Figures

Figure 1

Figure 1
<p>The time domain diagram of the motor radial vibration.</p>
Full article ">Figure 2
<p>The amplitude spectrums of radial vibration with kth harmonic current injection. (<b>a</b>) The vibration caused by no injection and injection of positive and negative sequence 6th harmonic current; (<b>b</b>) The vibration caused by no injection and injection of positive and negative sequence 7th harmonic current.</p>
Full article ">Figure 3
<p>Vibration amplitude variation with seventh harmonic current injection.</p>
Full article ">Figure 4
<p>Sixth harmonic vibration amplitude versus phase change.</p>
Full article ">Figure 5
<p>Sixth harmonic vibration amplitude versus amplitude change.</p>
Full article ">Figure 6
<p>Experimental setup.</p>
Full article ">Figure 7
<p>The three-phase current time domain diagram. (<b>a</b>) The three phase current before harmonic current injection; (<b>b</b>) The three phase current with the ideal sinusoidal current; (<b>c</b>) The three phase current with the vibration suppression method in this paper.</p>
Full article ">Figure 8
<p>The current amplitude spectrum diagram. (<b>a</b>) The spectrogram of phase current amplitude before harmonic current injection; (<b>b</b>) The spectrogram of phase current amplitude with the ideal sinusoidal current; (<b>c</b>) The spectrogram of phase current amplitude with the vibration suppression method in this paper.</p>
Full article ">Figure 9
<p>Radial vibration time domain diagram. (<b>a</b>) The radial vibration of the motor before harmonic current injection; (<b>b</b>) The radial vibration of the motor with the ideal sinusoidal current; (<b>c</b>) The radial vibration of the motor with the vibration suppression method in this paper.</p>
Full article ">Figure 9 Cont.
<p>Radial vibration time domain diagram. (<b>a</b>) The radial vibration of the motor before harmonic current injection; (<b>b</b>) The radial vibration of the motor with the ideal sinusoidal current; (<b>c</b>) The radial vibration of the motor with the vibration suppression method in this paper.</p>
Full article ">Figure 10
<p>Radial vibration amplitude spectrum diagram. (<b>a</b>) The spectrogram of radial vibration before harmonic current injection; (<b>b</b>) The spectrogram of radial vibration with the ideal sinusoidal current; (<b>c</b>) The spectrogram of radial vibration with the vibration suppression method in this paper.</p>
Full article ">
16 pages, 2528 KiB  
Article
Model Reference Adaptive System of Permanent Magnet Synchronous Motor Based on Current Residual Compensation Without Position Measurement
by Yuanchao Cao, Xing Ren, Qing Guo, Haoran Zhan, Wei Li, Guicheng Wu and Qiang Long
Actuators 2024, 13(11), 446; https://doi.org/10.3390/act13110446 - 7 Nov 2024
Viewed by 297
Abstract
There exists an inaccurate measurement problem in permanent magnet synchronous motors (PMSMs) due to low motor speed operation, high temperatures and humid environments, which will degrade the motion performance and stability of PMSMs. In this study, a model reference adaptive system without position [...] Read more.
There exists an inaccurate measurement problem in permanent magnet synchronous motors (PMSMs) due to low motor speed operation, high temperatures and humid environments, which will degrade the motion performance and stability of PMSMs. In this study, a model reference adaptive system without position measurement is presented in a PMSM to improve the output performance with external disturbance suppression caused by an environmental change. Firstly, a PI adaptive estimation law is designed to identify the motor speed. Then, a optimization method based on the sliding mode variable structure technique is proposed to realize the stability augmentation of the speed loop by using the parametric fuzzy logic design. To reject the current loop noise, an extended Kalman filter (EKF) is adopted to compensate the input signal in the current loop. The effectiveness of this proposed method is verified via a numerical simulation in the case of different speeds and external loads. Full article
(This article belongs to the Section Actuators for Manufacturing Systems)
Show Figures

Figure 1

Figure 1
<p>(<b>a</b>) Input variables <math display="inline"><semantics> <msub> <mi>e</mi> <mrow> <mi>α</mi> <mi>β</mi> </mrow> </msub> </semantics></math> and membership functions. (<b>b</b>) Input variables <math display="inline"><semantics> <msub> <mover accent="true"> <mi>e</mi> <mo>˙</mo> </mover> <mrow> <mi>α</mi> <mi>β</mi> </mrow> </msub> </semantics></math> and membership functions. (<b>c</b>) Output variables. input variables <math display="inline"><semantics> <mi>δ</mi> </semantics></math>, and membership functions. (<b>d</b>) The input and output relationship of fuzzy logic.</p>
Full article ">Figure 2
<p>The block diagram of model reference adaptive system based on fuzzy sliding mode variable structure optimization.</p>
Full article ">Figure 3
<p>The whole control scheme of the PMSM.</p>
Full article ">Figure 4
<p>PMSM control system model in Matlab/Simulink.</p>
Full article ">Figure 5
<p>Simulation A-Case I: (<b>a</b>) Actual rotor speed and estimated rotor speed. (<b>b</b>) Estimated error of rotor speed. (<b>c</b>) Actual rotor position and estimated rotor position. (<b>d</b>) Estimated error of rotor position. Simulation A-Case II: (<b>e</b>) Actual rotor speed and estimated rotor speed. (<b>f</b>) Estimated error of rotor speed. (<b>g</b>) Actual rotor position and estimated rotor position. (<b>h</b>) Estimated error of rotor position.</p>
Full article ">Figure 6
<p>Simulation B-Case I: (<b>a</b>) Actual rotor speed and estimated rotor speed. (<b>b</b>) Estimated error of rotor speed. (<b>c</b>) Actual rotor position and estimated rotor position. (<b>d</b>) Estimated error of rotor position. Simulation B-Case II: (<b>e</b>) Actual rotor speed and estimated rotor speed. (<b>f</b>) Estimated error of rotor speed. (<b>g</b>) Actual rotor position and estimated rotor position. (<b>h</b>) Estimated error of rotor position.</p>
Full article ">Figure 7
<p>Simulation C-Case I: (<b>a</b>) Actual rotor speed and estimated rotor speed. (<b>b</b>) Estimated error of rotor speed. (<b>c</b>) Actual rotor position and estimated rotor position. (<b>d</b>) Estimated error of rotor position. Simulation C-Case I: (<b>e</b>) <span class="html-italic">d</span>-axis current and estimated current. (<b>f</b>) Estimated error of <span class="html-italic">d</span>-axis current. (<b>g</b>) <span class="html-italic">q</span>-axis current and estimated current. (<b>h</b>) Estimated error of <span class="html-italic">q</span>-axis current.</p>
Full article ">Figure 8
<p>Simulation C-Case II: (<b>a</b>) Actual rotor speed and estimated rotor speed. (<b>b</b>) Estimated error of rotor speed. (<b>c</b>) Actual rotor position and estimated rotor position. (<b>d</b>) Estimated error of rotor position. Simulation C-Case II: (<b>e</b>) <span class="html-italic">d</span>-axis current and estimated current. (<b>f</b>) Estimated error of <span class="html-italic">d</span>-axis current. (<b>g</b>) <span class="html-italic">q</span>-axis current and estimated current. (<b>h</b>) Estimated error of <span class="html-italic">q</span>-axis current.</p>
Full article ">Figure 9
<p>The comparative results of the PMSM’s speed control in with and without an improvement, as well as with and without an EKF. (<b>a</b>) Speed in Case I. (<b>b</b>) Speed tracking error in Case I. (<b>c</b>) Speed in Case II. (<b>d</b>) Speed tracking error in Case II.</p>
Full article ">
22 pages, 9548 KiB  
Article
Research on the Synchronization Control Strategy of Regenerative Braking of Distributed Drive Electric Vehicles
by Ren He and Yukun Xie
World Electr. Veh. J. 2024, 15(11), 512; https://doi.org/10.3390/wevj15110512 - 7 Nov 2024
Viewed by 361
Abstract
To solve the problem of asynchronous speed between the coaxial in-wheel motors of distributed drive electric vehicle caused by changes in the road surface, load, and other factors during the regenerative braking of the vehicle, which may result in a yaw motion of [...] Read more.
To solve the problem of asynchronous speed between the coaxial in-wheel motors of distributed drive electric vehicle caused by changes in the road surface, load, and other factors during the regenerative braking of the vehicle, which may result in a yaw motion of the vehicle and a reduction in vehicle stability, a synchronization control strategy of regenerative braking for distributed drive electric vehicles is proposed. Firstly, a ring-coupled synchronous control strategy with the current compensation module is designed. Then, the speed controller of a permanent magnet synchronous in-wheel motor and a compensation controller of synchronous control are designed based on the non-singular fast terminal sliding mode control. Combining this with the regenerative braking control strategy, a regenerative braking synchronization control strategy is designed. The simulation results show that compared with the existing synchronization control strategy, the designed new ring-coupled synchronization control strategy can improve the speed synchronization performance between the motors after the disturbance. Moreover, compared with the conventional regenerative braking control strategy, the regenerative braking synchronization control strategy can reduce the speed synchronization error between the motors during the regenerative braking process, so as to improve the synchronization and output stability of the motors during the braking process. Full article
(This article belongs to the Special Issue Intelligent Electric Vehicle Control, Testing and Evaluation)
Show Figures

Figure 1

Figure 1
<p>The structure of the distributed drive electric vehicle braking system.</p>
Full article ">Figure 2
<p>The one-quarter dynamics vehicle model.</p>
Full article ">Figure 3
<p>The structure of <math display="inline"><semantics> <mrow> <msub> <mi>i</mi> <mi>d</mi> </msub> <mo>=</mo> <mn>0</mn> </mrow> </semantics></math> strategy.</p>
Full article ">Figure 4
<p>The simulation results of the battery during regenerative braking: (<b>a</b>) motor speed; (<b>b</b>) SOC (state of charge); (<b>b</b>) current; (<b>d</b>) voltage.</p>
Full article ">Figure 5
<p>The structure of synchronous control strategy: (<b>a</b>) the ring-coupling control (RCC) strategy; (<b>b</b>) current compensation ring-coupled control (CCRCC).</p>
Full article ">Figure 6
<p>The structure diagram of regenerative braking synchronous control strategy for distributed drive electric vehicles.</p>
Full article ">Figure 7
<p>Comparison of motor output speed and torque: (<b>a</b>) speeds at no-load starting; (<b>b</b>) torques at no-load starting; (<b>c</b>) speeds at load variation; (<b>d</b>) torques at load variation.</p>
Full article ">Figure 8
<p>Comparison of motor speed variation for three synchronous control strategies: (<b>a</b>) M-S; (<b>b</b>) RCC; (<b>c</b>) CCRCC.</p>
Full article ">Figure 9
<p>Comparison of synchronization errors under three control strategies.</p>
Full article ">Figure 10
<p>Comparison of motor torque for three synchronous control strategies: (<b>a</b>) M-S; (<b>b</b>) RCC; (<b>c</b>) CCRCC.</p>
Full article ">Figure 11
<p>Graph of speed change during regenerative braking disturbance at 0.12 braking intensity: (<b>a</b>) without synchronization control; (<b>b</b>) adopting the synchronization control strategy of regenerative braking.</p>
Full article ">Figure 12
<p>Graph of speed change during regenerative braking disturbance at 0.25 braking intensity: (<b>a</b>) without synchronization control; (<b>b</b>) adopting the synchronization control strategy of regenerative braking.</p>
Full article ">Figure 13
<p>Simulation results motor parameters are changed: (<b>a</b>) the speed of motors and reference without control strategy; (<b>b</b>) the <span class="html-italic">q</span>-axis current of motors without control strategy; (<b>c</b>) the speed of motors and reference with regenerative braking synchronous control strategy; (<b>d</b>) the <span class="html-italic">q</span>-axis current of motors with regenerative braking synchronous control strategy.</p>
Full article ">
25 pages, 3366 KiB  
Review
An Overview of the R&D of Flywheel Energy Storage Technologies in China
by Xingjian Dai, Xiaoting Ma, Dongxu Hu, Jibing Duan and Haisheng Chen
Energies 2024, 17(22), 5531; https://doi.org/10.3390/en17225531 - 5 Nov 2024
Viewed by 524
Abstract
The literature written in Chinese mainly and in English with a small amount is reviewed to obtain the overall status of flywheel energy storage technologies in China. The theoretical exploration of flywheel energy storage (FES) started in the 1980s in China. The experimental [...] Read more.
The literature written in Chinese mainly and in English with a small amount is reviewed to obtain the overall status of flywheel energy storage technologies in China. The theoretical exploration of flywheel energy storage (FES) started in the 1980s in China. The experimental FES system and its components, such as the flywheel, motor/generator, bearing, and power electronic devices, were researched around thirty years ago. About twenty organizations devote themselves to the R&D of FES technology, which is developing from theoretical and laboratory research to the stage of engineering demonstration and commercial application. After the research and accumulation in the past 30 years, the initial FES products were developed by some companies around 10 years ago. Today, the overall technical level of China’s flywheel energy storage is no longer lagging behind that of Western advanced countries that started FES R&D in the 1970s. The reported maximum tip speed of the new 2D woven fabric composite flywheel arrived at 900 m/s in the spin test. A steel alloy flywheel with an energy storage capacity of 125 kWh and a composite flywheel with an energy storage capacity of 10 kWh have been successfully developed. Permanent magnet (PM) motors with power of 250–1000 kW were designed, manufactured, and tested in many FES assemblies. The lower loss is carried out through innovative stator and rotor configuration, optimizing magnetic flux and winding arrangement for harmonic magnetic field suppression. Permanent magnetic bearings with high load ability up to 50–100 kN were developed both for a 1000 kW/16.7 kWh flywheel used for the drilling practice application in hybrid power of an oil well drilling rig and for 630 kW/125 kWh flywheels used in the 22 MW flywheel array applied to the flywheel and thermal power joint frequency modulation demonstration project. It is expected that the FES demonstration application power stations with a total cumulative capacity of 300 MW will be built in the next five years. Full article
(This article belongs to the Section D: Energy Storage and Application)
Show Figures

Figure 1

Figure 1
<p>Configuration of flywheel energy storage system.</p>
Full article ">Figure 2
<p>Six kinds of flywheel: (<b>a</b>) 1000 kWh flywheel concept design; (<b>b</b>) 200 Wh winding composite AMB flywheel; (<b>c</b>) woven fabric composite flywheel; (<b>d</b>) magnet element embedded fiber spoke flywheel; (<b>e</b>) 10 kWh composite flywheel (Tsinghua Univ.); and (<b>f</b>) 90 kWh steel flywheel (IET, CAS).</p>
Full article ">Figure 3
<p>A new type of M/G and flywheel. (<b>a</b>) The 3D model of the flywheel and M/G. (<b>b</b>) The profile view of the M/G.</p>
Full article ">Figure 4
<p>A 50–100 kN permanent magnetic bearing stator. (<b>a</b>) Permanent ring with sector blocks. (<b>b</b>) Halbach array magnetic ring.</p>
Full article ">Figure 5
<p>Charging and discharging principles of motor-power electronic system: (<b>a</b>) charging and (<b>b</b>) discharging.</p>
Full article ">Figure 5 Cont.
<p>Charging and discharging principles of motor-power electronic system: (<b>a</b>) charging and (<b>b</b>) discharging.</p>
Full article ">Figure 6
<p>Integration flywheel energy storage system.</p>
Full article ">Figure 7
<p>Flywheel energy storage unit and array built in China: (<b>a</b>) 500 kw/50 kWh FESU, 2023, and (<b>b</b>) 20 MW Flywheels Array, 2023.</p>
Full article ">Figure 8
<p>Simulink model of the control of FES and wind power system.</p>
Full article ">Figure 9
<p>FES application in PV power.</p>
Full article ">Figure 10
<p>Potential energy regenerating and load leveling of oil drilling rig.</p>
Full article ">
19 pages, 3446 KiB  
Article
Improving the Dynamics of an Electrical Drive Using a Modified Controller Structure Accompanied by Delayed Inputs
by Konrad Urbanski and Dariusz Janiszewski
Appl. Sci. 2024, 14(22), 10126; https://doi.org/10.3390/app142210126 - 5 Nov 2024
Viewed by 483
Abstract
This paper presents the operation of a modified speed controller with a standard PI/PID structure that includes the preprocessing of the controller’s input signal, focusing on the past behavior of control errors. The modification involves adding a delay line, with the outputs of [...] Read more.
This paper presents the operation of a modified speed controller with a standard PI/PID structure that includes the preprocessing of the controller’s input signal, focusing on the past behavior of control errors. The modification involves adding a delay line, with the outputs of the individual line segments summed with a weighting method, as detailed in the paper. One of the significant advantages of this method is its use of a standard industrial controller structure, which makes it highly practical and easily implementable in existing systems. By relying on well-established control frameworks, this approach reduces the need for specialized hardware or complex modifications, allowing for smoother integration and lower implementation costs. The delay-based signal shaping shows excellent properties for the electric drive system powered by a hard-switching PWM converter. The set of weighted delays acts as a filter whose parameters are chosen using the quality function to test different configurations for optimal performance. When tested in a speed control system for a Permanent Magnet Synchronous Motor, the modifications improved the control quality index, indicating better performance and efficiency. Importantly, the system allows for reducing or eliminating the gain in the differentiating part of the controller, which decreases motor current chattering and noise. This paper includes an experimental verification of the proposed solution in a laboratory setting under semi-industrial conditions. Full article
(This article belongs to the Collection Modeling, Design and Control of Electric Machines: Volume II)
Show Figures

Figure 1

Figure 1
<p>Basic implementation of a PID speed controller. A system with one input (error) and one output (control signal).</p>
Full article ">Figure 2
<p>Visualization of speed controller parameter determination—selection of weights or/and controller parameters—algorithm RWC.</p>
Full article ">Figure 3
<p>Modified speed controller structure called MPID. Weighted (<math display="inline"><semantics> <msub> <mi>W</mi> <mi>i</mi> </msub> </semantics></math>) multi-input circuit with <math display="inline"><semantics> <mi>τ</mi> </semantics></math> time delay.</p>
Full article ">Figure 4
<p>General view of the control structure for a simple object.</p>
Full article ">Figure 5
<p>Simulation: Selected sets for step response and disturbance reaction for the I2PD system in <a href="#applsci-14-10126-f004" class="html-fig">Figure 4</a>. (<b>a</b>) The step response for the setting <span class="html-italic">Skogestad</span>. (<b>b</b>) The step response after PID optimization. (<b>c</b>) The step response in the case of the MPID controller for <math display="inline"><semantics> <mrow> <msub> <mi>γ</mi> <mn>1</mn> </msub> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>. (<b>d</b>) The step response in the case of the MPID controller for <math display="inline"><semantics> <mrow> <msub> <mi>γ</mi> <mn>1</mn> </msub> <mo>=</mo> <mn>0</mn> </mrow> </semantics></math>.</p>
Full article ">Figure 6
<p>General view of the control structure for a drive with PMSM.</p>
Full article ">Figure 7
<p>Simulation: The response of the system to a step change in the speed reference. Once the speed is set, the load change step sequence is performed. The speed changes in the following sequence: <math display="inline"><semantics> <mrow> <mn>0.6</mn> <mo>·</mo> <mn>98</mn> <mspace width="0.166667em"/> <mo>%</mo> <mo>→</mo> <mn>0.6</mn> </mrow> </semantics></math> p.u. The current limit is set to <math display="inline"><semantics> <mrow> <mn>0.4</mn> </mrow> </semantics></math> p.u. (<b>a</b>) Using an MPI speed controller. (<b>b</b>) Using a PID speed controller.</p>
Full article ">Figure 8
<p>Simulation: The response of the system to a sloped change in the speed reference. Once the speed is set, the load change step sequence is performed. The speed changes in the following sequence: <math display="inline"><semantics> <mrow> <mn>0.6</mn> <mo>·</mo> <mn>98</mn> <mspace width="0.166667em"/> <mo>%</mo> <mo>→</mo> <mn>0.6</mn> </mrow> </semantics></math> p.u. (about <math display="inline"><semantics> <mrow> <mn>199.7</mn> <mo>→</mo> <mn>203.8</mn> </mrow> </semantics></math> [rad/s]). The load varies in sequence from zero to <math display="inline"><semantics> <mrow> <mn>0.2</mn> </mrow> </semantics></math> p.u. (<math display="inline"><semantics> <mrow> <mn>2.7</mn> <mspace width="0.166667em"/> <mi>A</mi> </mrow> </semantics></math>). The current limit is set to <math display="inline"><semantics> <mrow> <mn>0.4</mn> </mrow> </semantics></math> p.u. (<b>a</b>) Using an MPI speed controller. (<b>b</b>) Using a PID speed controller.</p>
Full article ">Figure 9
<p>Simulation: The current waveforms of the reference <span class="html-italic">q</span>-axis for the response of the system to a step change in the speed setpoint. Corresponds to the waveforms in <a href="#applsci-14-10126-f007" class="html-fig">Figure 7</a>. (<b>a</b>) Using an MPI speed controller. (<b>b</b>) Using a PID speed controller; the current is filtered for better clarity.</p>
Full article ">Figure 10
<p>Simulation: The current waveforms of the reference <span class="html-italic">q</span>-axis for the response of the system to a sloped change in the speed setpoint. Corresponds to the waveforms in <a href="#applsci-14-10126-f008" class="html-fig">Figure 8</a>. (<b>a</b>) Using an MPI speed controller. (<b>b</b>) Using a PID speed controller; the current is filtered for better clarity.</p>
Full article ">Figure 11
<p>General structure of control system with PMSM.</p>
Full article ">Figure 12
<p>General view of the test site. In the foreground, the sandwich-like connection with the control system and two inverters can be seen. In the background, two PMSMs connected by a shaft can be seen.</p>
Full article ">Figure 13
<p>Experiment: The response of the system to a step change in the speed reference. Once the speed is set, the load change step sequence is performed. The speed changes in the following sequence: <math display="inline"><semantics> <mrow> <mn>0.6</mn> <mo>·</mo> <mn>98</mn> <mspace width="0.166667em"/> <mo>%</mo> <mo>→</mo> <mn>0.6</mn> </mrow> </semantics></math> p.u. (about 199.7→203.8 [rad/s]). The load varies in the sequence from 0 to <math display="inline"><semantics> <mrow> <mn>0.2</mn> </mrow> </semantics></math> p.u. (<math display="inline"><semantics> <mrow> <mn>2.7</mn> </mrow> </semantics></math> A). The current limit is set to 0.4 p.u. (<b>a</b>) Using an MPI speed controller. (<b>b</b>) Using a PID speed controller.</p>
Full article ">Figure 14
<p>Experiment: The response of the system to a sloped change in the speed reference. Once the speed is set, the load change step sequence is performed. The speed changes in the following sequence: <math display="inline"><semantics> <mrow> <mn>0.6</mn> <mo>·</mo> <mn>98</mn> <mspace width="0.166667em"/> <mo>%</mo> <mo>→</mo> <mn>0.6</mn> </mrow> </semantics></math> p.u. (about <math display="inline"><semantics> <mrow> <mn>199.7</mn> <mo>→</mo> <mn>203.8</mn> </mrow> </semantics></math> rad/s). The load varies in the sequence from 0 to <math display="inline"><semantics> <mrow> <mn>0.2</mn> </mrow> </semantics></math> p.u. (<math display="inline"><semantics> <mrow> <mn>2.7</mn> </mrow> </semantics></math> A). The current limit is set to <math display="inline"><semantics> <mrow> <mn>0.4</mn> </mrow> </semantics></math> p.u. (<b>a</b>) Using an MPI speed controller. (<b>b</b>) Using a PID speed controller.</p>
Full article ">Figure 15
<p>Experiment: The current waveforms of the reference <span class="html-italic">q</span>-axis (channel 1) and measured <span class="html-italic">q</span>-axis (channel-2) for the response of the system to a step change in the speed setpoint and reaction to a disturbance. Corresponds to the waveforms in <a href="#applsci-14-10126-f013" class="html-fig">Figure 13</a>. (<b>a</b>) Using an MPI speed controller. (<b>b</b>) Using a PID speed controller.</p>
Full article ">Figure 16
<p>Experiment: The current waveforms of the reference <span class="html-italic">q</span>-axis (channel 1) and measured <span class="html-italic">q</span>-axis (channel-2) for the response of the system to a sloped change in the speed setpoint and reaction to a disturbance. Corresponds to the waveforms in <a href="#applsci-14-10126-f014" class="html-fig">Figure 14</a>. (<b>a</b>) Using an MPI speed controller. (<b>b</b>) Using a PID speed controller.</p>
Full article ">
7 pages, 1104 KiB  
Proceeding Paper
Comparative Analysis of Field Oriented Control and Direct Torque Control Through Simulation in MATLAB Simulink for an Automotive Drive Motor
by Miklós Gábor Simon and Dénes Fodor
Eng. Proc. 2024, 79(1), 33; https://doi.org/10.3390/engproc2024079033 - 5 Nov 2024
Viewed by 250
Abstract
Field oriented control (FOC) and direct torque control (DTC) are two strategies used in electric motor control, both with their respective advantages and disadvantages. This paper presents a comparative analysis of these two control methodologies, focusing on their application and performance within a [...] Read more.
Field oriented control (FOC) and direct torque control (DTC) are two strategies used in electric motor control, both with their respective advantages and disadvantages. This paper presents a comparative analysis of these two control methodologies, focusing on their application and performance within a MATLAB Simulink (R2024b) environment for an automotive Permanent Magnet Synchronous Motor (PMSM) drive. The models are created with a focus on realistic drive and test parameters. The simulation results are analyzed to highlight the strengths and weaknesses of each strategy and identify use cases where one method may be superior to the other. In conclusion, this paper contributes to the understanding of FOC and DTC by offering a systematic comparison of their features, performance characteristics, and application scenarios for automotive use. Full article
Show Figures

Figure 1

Figure 1
<p>Control diagrams for FOC and DTC. (<b>a</b>) Control diagram of FOC for PMSM using currents as reference; (<b>b</b>) Control diagram of DTC for PMSM using torque and flux as reference.</p>
Full article ">Figure 2
<p>Sectors and voltage vectors.</p>
Full article ">Figure 3
<p>Reference and response (<b>a</b>) DTC and FOC; (<b>b</b>) DTC and FOC detail; (<b>c</b>) DTC and FOC 100 Nm step and slope; (<b>d</b>) DTC and FOC 100 Nm step and slope detail.</p>
Full article ">
15 pages, 3753 KiB  
Article
FPGA-Based High-Frequency Voltage Injection Sensorless Control with Novel Rotor Position Estimation Extraction for Permanent Magnet Synchronous Motor
by Indra Ferdiansyah and Tsuyoshi Hanamoto
World Electr. Veh. J. 2024, 15(11), 506; https://doi.org/10.3390/wevj15110506 - 5 Nov 2024
Viewed by 455
Abstract
This study developed a realization of sensorless control for a permanent magnet synchronous motor (PMSM) using a field-programmable gate array (FPGA). Both position and speed were estimated using a high-frequency (HF) injection scheme. Accurate estimation is essential to ensure the proper functioning of [...] Read more.
This study developed a realization of sensorless control for a permanent magnet synchronous motor (PMSM) using a field-programmable gate array (FPGA). Both position and speed were estimated using a high-frequency (HF) injection scheme. Accurate estimation is essential to ensure the proper functioning of sensorless motor control. To improve the estimation accuracy of the rotor position and reduce the motor speed ripple found in conventional methods, a new extraction strategy for estimating the rotor position and motor speed is proposed. First, signal modulation compensation was applied to expand the information of the error function in order to provide more accurate data to the tracking loop system for rotor position extraction. Second, to minimize the motor speed ripple caused by the HF injection, motor speed estimation was performed after obtaining the rotor position information using a differential equation with a low-pass filter (LPF) to avoid the direct effect of the injected signal. Verified experimentally, the results showed that the rotor position error did not exceed 10 el.deg, so these methods effectively reduce the rotor position estimation error by about 30%, along with the motor speed ripple. Therefore, better performance in sensorless PMSM control can be achieved in motor control applications. Full article
Show Figures

Figure 1

Figure 1
<p>The correlation of rotor position between actual and estimated in a two-phase rotating reference frame.</p>
Full article ">Figure 2
<p>The extraction information of <math display="inline"><semantics> <mrow> <mi>f</mi> <mo>Δ</mo> <mi>θ</mi> </mrow> </semantics></math> for tracking loop rotor position estimation: (<b>a</b>) without compensation in the modulation signal; (<b>b</b>) with compensation in the modulation signal.</p>
Full article ">Figure 3
<p>Rotor position estimation tracking loop systems: (<b>a</b>) conventional method; (<b>b</b>) proposed method.</p>
Full article ">Figure 4
<p>Motor speed estimation under 150 min<sup>−1</sup>: (<b>a</b>) conventional method; (<b>b</b>) proposed method.</p>
Full article ">Figure 5
<p>Vector control FPGA implementation architecture for sensorless PMSM.</p>
Full article ">Figure 6
<p>FPGA implementation hardware architecture for extraction of rotor position and motor speed.</p>
Full article ">Figure 7
<p>Experimental setup.</p>
Full article ">Figure 8
<p>Rotor position estimation under constant speed at 100 min<sup>−1</sup>: (<b>a</b>) steady-state performance with conventional method; (<b>b</b>) steady-state performance with proposed method.</p>
Full article ">Figure 9
<p>Rotor position estimation under sudden direction change from 100 min<sup>−1</sup> to −100 min<sup>−1</sup>: (<b>a</b>) conventional method; (<b>b</b>) proposed method.</p>
Full article ">Figure 10
<p>Rotor position estimation under sudden direction change of −100 min<sup>−1</sup> to 100 min<sup>−1</sup>: (<b>a</b>) conventional method; (<b>b</b>) proposed method.</p>
Full article ">Figure 11
<p>Rotor position estimation under 100 min<sup>−1</sup>: (<b>a</b>) rotor position estimation with a load of 0.3 Nm; (<b>b</b>) correlation of rotor position estimation error with varying load.</p>
Full article ">Figure 12
<p>Comparison of motor control step response 120 min<sup>−1</sup> to 150 min<sup>−1</sup> between sensored and sensorless systems: (<b>a</b>) sensored control; (<b>b</b>) proposed sensorless control.</p>
Full article ">
24 pages, 6414 KiB  
Article
Robust Driving Control Design for Precise Positional Motions of Permanent Magnet Synchronous Motor Driven Rotary Machines with Position-Dependent Periodic Disturbances
by Syh-Shiuh Yeh and Zhi-Hong Liu
Machines 2024, 12(11), 771; https://doi.org/10.3390/machines12110771 - 1 Nov 2024
Viewed by 557
Abstract
Position-dependent periodic disturbances often limit the accuracy and smoothness of the positional motion of permanent magnet synchronous motor (PMSM)-driven rotary machines. Because the period of these disturbances varies with the motion velocity of the rotary machine, spatial domain control methods such as spatial [...] Read more.
Position-dependent periodic disturbances often limit the accuracy and smoothness of the positional motion of permanent magnet synchronous motor (PMSM)-driven rotary machines. Because the period of these disturbances varies with the motion velocity of the rotary machine, spatial domain control methods such as spatial iterative learning control (SILC) and spatial repetitive control (SRC) have been proposed and applied to improve rotary machine motion control designs. However, problems with learning period convergence and rotary machine dynamics significantly affect transient motion, further constraining the overall motion performance. To address these challenges, this study developed a robust driving control (RDC) that integrates a robust control design with position-dependent periodic disturbance feedforward compensation, rotary machine dynamics compensation, and proportional–proportional integral feedback control. A position-dependent periodic disturbance model was developed using multiple position–sinusoidal signals and identified using a spatial fast Fourier transform. RDC compensates for disturbances and dynamics and considers the effects of model parameter uncertainty and modeling error on the stability of the control system. Several motion control experiments were conducted on a PMSM test bench to compare the RDC, SILC, and SRC. The experimental results demonstrated that although both SILC and SRC can effectively suppress position-dependent periodic disturbances, SILC provides slower position error convergence owing to the learning process, and SILC and SRC result in significant position errors because of the influence of the PMSM-driven rotary machine dynamics. RDC not only suppresses position-dependent periodic disturbances, but also significantly reduces position errors with a reduction rate of 90%. Therefore, the RDC developed in this study effectively suppressed position-dependent periodic disturbances and significantly improved both the transient-state and steady-state position-tracking performances of the PMSM-driven rotary machine. Full article
Show Figures

Figure 1

Figure 1
<p>P-PI feedback control and compensation: (<b>a</b>) P-PI feedback control structure. (<b>b</b>) P-PI feedback-and-compensation control structure [<a href="#B33-machines-12-00771" class="html-bibr">33</a>].</p>
Full article ">Figure 2
<p>SILC design based on P-PI feedback control structure.</p>
Full article ">Figure 3
<p>SRC design based on the P-PI feedback control structure.</p>
Full article ">Figure 4
<p>RDC design based on the P-PI feedback-and-compensation control structure.</p>
Full article ">Figure 5
<p>The PMSM test bench used in this study.</p>
Full article ">Figure 6
<p>Position-dependent periodic disturbance estimation results (for a complete turn).</p>
Full article ">Figure 7
<p>Spatial FFT of the position-dependent periodic disturbance (corresponding to <a href="#machines-12-00771-f006" class="html-fig">Figure 6</a>).</p>
Full article ">Figure 8
<p>Position-dependent periodic disturbance estimation and modeling.</p>
Full article ">Figure 9
<p>Experimental results of the drive motor operating for ten turns (SILC).</p>
Full article ">Figure 10
<p>Experimental results of transient-state and steady-state operation of the drive motor (SILC) (circular angle axis unit: degree; radial axis unit: radian).</p>
Full article ">Figure 11
<p>Experimental results of drive motor operating for ten turns (SRC).</p>
Full article ">Figure 12
<p>Experimental results of transient-state and steady-state operation of the drive motor (SRC) (circular angle axis unit: degree; radial axis unit: radian).</p>
Full article ">Figure 13
<p>Experimental results of the drive motor operating for ten turns (RDC).</p>
Full article ">Figure 14
<p>Experimental results of transient-state and steady-state operation of the drive motor (RDC) (circular angle axis unit: degree; radial axis unit: radian).</p>
Full article ">Figure 15
<p>Position error in the drive motor operating process (left: first three turns; right: tenth turn).</p>
Full article ">Figure 16
<p>Comparison of MAX and AVG position errors (left: MAX; right: AVG).</p>
Full article ">
21 pages, 10520 KiB  
Article
The Design of Improved Series Hybrid Power System Based on Compound-Wing VTOL
by Siqi An, Guichao Cai, Xu Peng, Mingxiao Dai and Guolong Yang
Drones 2024, 8(11), 634; https://doi.org/10.3390/drones8110634 - 1 Nov 2024
Viewed by 514
Abstract
Hybrid power systems are now widely utilized in a variety of vehicle platforms due to their efficacy in reducing pollution and enhancing energy utilization efficiency. Nevertheless, the existing vehicle hybrid systems are of a considerable size and weight, rendering them unsuitable for integration [...] Read more.
Hybrid power systems are now widely utilized in a variety of vehicle platforms due to their efficacy in reducing pollution and enhancing energy utilization efficiency. Nevertheless, the existing vehicle hybrid systems are of a considerable size and weight, rendering them unsuitable for integration into 25 kg compound-wing UAVs. This study presents a design solution for a compound-wing vertical takeoff and landing unmanned aerial vehicle (VTOL) equipped with an improved series hybrid power system. The system comprises a 48 V lithium polymer battery(Li-Po battery), a 60cc internal combustion engine (ICE), a converter, and a dedicated permanent magnet synchronous machine (PMSM) with four motors, which collectively facilitate dual-directional energy flow. The four motors serve as a load and lift assembly, providing the requisite lift during the take-off, landing, and hovering phases, and in the event of the ICE thrust insufficiency, as well as forward thrust during the level cruise phase by mounting the variable pitch propeller directly on the ICE. The entire hybrid power system of the UAV undergoes numerical modeling and experimental simulation to validate the feasibility of the complete hybrid power configuration. The validation is achieved by comparing and analyzing the results of the numerical simulations with ground tests. Moreover, the effectiveness of this hybrid power system is validated through the successful completion of flight test experiments. The hybrid power system has been demonstrated to significantly enhance the endurance of vertical flight for a compound-wing VTOL by more than 25 min, thereby establishing a solid foundation for future compound-wing VTOLs to enable multi-destination flights and multiple takeoffs and landings. Full article
Show Figures

Figure 1

Figure 1
<p>Two typical configurations of the UAV.</p>
Full article ">Figure 2
<p>Typical multi-points flight mission profile.</p>
Full article ">Figure 3
<p>(<b>a</b>) Typical configuration of the compound-wing VTOL; (<b>b</b>) 25 kg MTOW compound-wing VTOL prototype.</p>
Full article ">Figure 4
<p>The improved series hybrid architecture and three different energy paths of the hybrid power system under different thrust modes. (<b>a</b>) The diagram illustrates the bidirectional flow path of energy throughout the hybrid system; (<b>b</b>) energy flow path in the full thrust mode, illustrates that in the case of vertical lift; (<b>c</b>) illustrates the energy flow path in cruise mode, in which the UAV is airborne; (<b>d</b>) energy flow path in the emergency thrust mode, shows the emergency mode.</p>
Full article ">Figure 5
<p>Selecting or designing the five main components of the system, the second floor of the diagram shows the main factors to consider and the third floor shows the main system components.</p>
Full article ">Figure 6
<p>(<b>a</b>) Piston ICE that drives a propeller in the cruise mode to provide the forward thrust for the aircraft. It also drives the PMSM to generate AC, which is passed through a rectifier to charge the batteries used in the drogue phase; (<b>b</b>) the Li-Po battery used in drones is designed as a single unit, usually a single unit with a voltage of 3.8 V to 4.2 V. The power system battery is made up of 12 pieces connected in parallel to ensure that the dropping voltage reaches 48 V and above.</p>
Full article ">Figure 7
<p>(<b>a</b>) This is a multi-rotor brushless DC motor. It is DC powered to generate the upward lift; (<b>b</b>) this is a permanent magnet synchronous motor (PMSM), which is driven by an internal combustion engine for the generation of AC; (<b>c</b>) this is a three-phase bridge rectifier in the VTOL, which is a device that is used to convert AC to DC.</p>
Full article ">Figure 8
<p>The general character map of the ICE.</p>
Full article ">Figure 9
<p>The R-int model of battery.</p>
Full article ">Figure 10
<p>(<b>a</b>) Shows five connections. The lower three interfaces in the diagram access the three-phase AC generated by the synchronous motor and the DC is connected via the upper two connectors; (<b>b</b>) shows the rectifier circuit working principle.</p>
Full article ">Figure 11
<p>The schematic diagram of VPP.</p>
Full article ">Figure 12
<p>The thrust performance of the 17-inch, 20-inch, and 22-inch propellers.</p>
Full article ">Figure 13
<p>The simulation configuration of VPP.</p>
Full article ">Figure 14
<p>(<b>a</b>) The output thrust character (2D) of VPP; (<b>b</b>) the output thrust character (3D) of VPP.</p>
Full article ">Figure 15
<p>(<b>a</b>): Simulation thrust from VPP compared with demanded thrust; (<b>b</b>): simulation electric load that represents the lift on rotor.</p>
Full article ">Figure 16
<p>Simulation of ICE rotational speed, SOC, throttle opening, and generated power versus time.</p>
Full article ">Figure 17
<p>The specifically made ground test bench.</p>
Full article ">Figure 18
<p>The ground experiment of the entire hybrid power system.</p>
Full article ">Figure 19
<p>Flight profile data from ground experiment.</p>
Full article ">Figure 20
<p>(<b>a</b>) The output thrust character of the VPP (ground experiment); (<b>b</b>) difference between measured data from the ground experiment and numerically simulated values.</p>
Full article ">Figure 21
<p>The configuration of the hybrid compound-wing VTOL.</p>
Full article ">Figure 22
<p>The hovering experiment of compound-wing VTOL.</p>
Full article ">Figure 23
<p>The flight data based on the hovering experiment of compound-wing VTOL.</p>
Full article ">
17 pages, 2765 KiB  
Article
A Neuroadaptive Position-Sensorless Robust Control for Permanent Magnet Synchronous Motor Drive System with Uncertain Disturbance
by Omar Aguilar-Mejia, Antonio Valderrabano-Gonzalez, Norberto Hernández-Romero, Juan Carlos Seck-Tuoh-Mora, Julio Cesar Hernandez-Ochoa and Hertwin Minor-Popocatl
Energies 2024, 17(21), 5477; https://doi.org/10.3390/en17215477 - 1 Nov 2024
Viewed by 494
Abstract
The Permanent Magnet Synchronous Motor (PMSM) drive system is extensively utilized in high-precision positioning applications that demand superior dynamic performance across various operating conditions. Given the non-linear characteristics of the PMSM, a neuroadaptive sensorless controller based on B-spline neural networks is proposed to [...] Read more.
The Permanent Magnet Synchronous Motor (PMSM) drive system is extensively utilized in high-precision positioning applications that demand superior dynamic performance across various operating conditions. Given the non-linear characteristics of the PMSM, a neuroadaptive sensorless controller based on B-spline neural networks is proposed to determine the control signals necessary for achieving the desired performance. The proposed control technique considers the system’s non-linearities and can be adapted to varying operating conditions, all while maintaining a low computational cost suitable for real-time operation. The introduced neuroadaptive controller is evaluated under conditions of uncertainty, and its performance is compared to that of a conventional PI controller optimized using the Whale Optimization Algorithm (WOA). The results demonstrate the viability of the proposed approach. Full article
Show Figures

Figure 1

Figure 1
<p>Control scheme to regulate the position of the PMSM with sensorless NCPI.</p>
Full article ">Figure 2
<p>Structure of the BSNN used for the NCPI.</p>
Full article ">Figure 3
<p>Block diagram of structure diagram of adaptive sliding mode observer.</p>
Full article ">Figure 4
<p>Block diagram of the control scheme to regulate the position of the PMSM regulated by an optimized sensorless PI controller.</p>
Full article ">Figure 5
<p>Iterations of the WOA to calculate the parameters of the SPI-Opt controller.</p>
Full article ">Figure 6
<p>Dynamic response of SNCPI and SPI-OPt controller following a reference path.</p>
Full article ">Figure 7
<p>Error signal from SNCPI and SPI-Opt controllers.</p>
Full article ">Figure 8
<p>Rotor position estimation performance comparison between the SNCPI and SPI-OPt, for the case 1.</p>
Full article ">Figure 9
<p>IAE of the SNCPI and SPI-Opt controllers of the follow-up of a desired trajectory for the three operating conditions.</p>
Full article ">Figure 10
<p>Dynamic response of observador para el caso 3.</p>
Full article ">
16 pages, 11983 KiB  
Article
A Study on Series-Parallel Winding Changeover Circuit and Control Method for Expanding the High-Efficiency Operating Range of IPMSM for xEV Drive Systems
by Yangjin Shin, Suyeon Cho and Ju Lee
World Electr. Veh. J. 2024, 15(11), 501; https://doi.org/10.3390/wevj15110501 - 31 Oct 2024
Viewed by 515
Abstract
The motor characteristics control method using the winding changeover technique can improve the matching ratio between the most frequent operating point of electric vehicle (EV) and the motor’s high-efficiency operating point, thereby enhancing the overall average efficiency of the drive system. This technology [...] Read more.
The motor characteristics control method using the winding changeover technique can improve the matching ratio between the most frequent operating point of electric vehicle (EV) and the motor’s high-efficiency operating point, thereby enhancing the overall average efficiency of the drive system. This technology reduces back electromotive force and winding resistance by adjusting the effective number of motor winding turns according to the EV’s operating speed, ultimately improving the average efficiency. In this paper, we propose a winding changeover circuit and control method that maximizes the average efficiency in the main driving regions to extend the driving range per charge and improve the fuel efficiency of EVs. The proposed circuit is constructed using thyristor switching devices, offering the advantage of relatively lower overall system losses compared to conventional circuits. Due to the characteristics of the thyristor switching devices used in the proposed circuit, seamless winding changeover is possible during motor operation. Additionally, no extra snubber circuits are required, and the relatively low switch losses suggest the potential for improved efficiency and lightweight design in EV drive systems. To verify the proposed winding changeover circuit and control scheme, experiments were conducted using a dynamometer with an 80 kW permanent magnet motor, inverter, and the developed prototype of the winding changeover circuit. Full article
Show Figures

Figure 1

Figure 1
<p>Efficiency map of the IPMSM for the entire driving range with overlapping main driving points of the two driving modes.</p>
Full article ">Figure 2
<p>Torque-Speed characteristics of two-stage changeover system.</p>
Full article ">Figure 3
<p>The structure of the conventional changeover circuit.</p>
Full article ">Figure 4
<p>Voltage vector diagrams according the winding connections in the conventional neutral-point shift type changeover circuit. (<b>a</b>) Low-speed mode; (<b>b</b>) high-speed mode.</p>
Full article ">Figure 5
<p>Simulation results of the conventional changeover circuit.</p>
Full article ">Figure 6
<p>Proposed series-parallel winding changeover circuit.</p>
Full article ">Figure 7
<p>Connection status of the proposed changeover circuit based on motor speed. (<b>a</b>) Low-speed mode; (<b>b</b>) high-speed mode.</p>
Full article ">Figure 8
<p>Thyristor switching operation in the proposed changeover circuit.</p>
Full article ">Figure 9
<p>Phase angle detection for current zero-crossing in the proposed changeover circuit.</p>
Full article ">Figure 10
<p>Control method for thyristor gate signals during changeover operation. (<b>a</b>) Series, low-speed mode to parallel, high-speed mode; (<b>b</b>) parallel, high-speed mode to series, low-speed mode.</p>
Full article ">Figure 11
<p>Simulation waveforms during changeover operation. (<b>a</b>) Series, low-speed mode to parallel, high-speed mode; (<b>b</b>) parallel, high-speed mode to series, low-speed mode.</p>
Full article ">Figure 12
<p>Simulation waveforms during changeover operation for distorted currents. (<b>a</b>) Series, low-speed mode to parallel, high-speed mode; (<b>b</b>) parallel, high-speed mode to series, low-speed mode.</p>
Full article ">Figure 13
<p>Current specification of main components in the conventional changeover circuit by speed mode at 80 kW. (<b>a</b>) Low-speed mode; (<b>b</b>) high-speed mode.</p>
Full article ">Figure 14
<p>Current specification of thyristor in the proposed changeover circuit by speed mode at 80 kW. (<b>a</b>) Series, low-speed mode; (<b>b</b>) parallel, high-speed mode.</p>
Full article ">Figure 15
<p>Comparison of losses and costs between the proposed and conventional changeover circuit. (<b>a</b>) Loss comparison at 80 kW; (<b>b</b>) costs comparison.</p>
Full article ">Figure 16
<p>Dynamometer test setup for the proposed 80 kW changeover circuit with IPMSM and inverter. (<b>a</b>) Prototype of the proposed changeover circuit; (<b>b</b>) experimental setup.</p>
Full article ">Figure 17
<p>Experimental waveforms from the dynamometer test of the 80 kW changeover circuit. (<b>a</b>) Series, low-speed mode at 2000 RPM, 20 Nm; (<b>b</b>) series, low-speed mode at 2000 RPM, 30 Nm; (<b>c</b>) parallel, high-speed mode at 1000 RPM, 20 Nm; (<b>d</b>) parallel, high-speed mode at 1000 RPM, 30 Nm.</p>
Full article ">Figure 18
<p>Current and gate waveforms during winding changeover operation in the proposed circuit at 1000 RPM, 10 Nm. (<b>a</b>) Series, low-speed mode to parallel, high-speed mode; (<b>b</b>) parallel, high-speed mode to series, low-speed mode.</p>
Full article ">Figure 19
<p>Current and gate waveforms during winding changeover operation with and without inverter controller feedforward at 1000 RPM, 10 Nm. (<b>a</b>) Parallel, high-speed mode to series, low-speed mode without feedforward; (<b>b</b>) parallel, high-speed mode to series, low-speed mode with feedforward; (<b>c</b>) series, low-speed mode to parallel, high-speed mode without feedforward; (<b>d</b>) series, low-speed mode to parallel, high-speed mode with feedforward.</p>
Full article ">Figure 20
<p>Efficiency map based on winding configuration. (<b>a</b>) Motor efficiency map for parallel winding; (<b>b</b>) motor efficiency map for series winding; (<b>c</b>) integrated motor efficiency map for the entire speed range; (<b>d</b>) inverter efficiency map for parallel winding; (<b>e</b>) inverter efficiency map for series winding; (<b>f</b>) integrated inverter efficiency map for the entire speed range; (<b>g</b>) system efficiency map for parallel winding; (<b>h</b>) system efficiency map for series winding; (<b>i</b>) integrated system efficiency map for the entire speed range.</p>
Full article ">
Back to TopTop