Nothing Special   »   [go: up one dir, main page]

You seem to have javascript disabled. Please note that many of the page functionalities won't work as expected without javascript enabled.
 
 
Sign in to use this feature.

Years

Between: -

Subjects

remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline

Journals

Article Types

Countries / Regions

remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline
remove_circle_outline

Search Results (927)

Search Parameters:
Keywords = PMSM

Order results
Result details
Results per page
Select all
Export citation of selected articles as:
31 pages, 4082 KiB  
Article
A Study on a Speed Regulation Method for Mining Scraper Conveyors and a Control Strategy for Permanent Magnet Drive Systems
by Xi Zhang, Mingming Ren, Hongju Wang, Hongyu Xu, Bin Shi and Miaomiao Gao
Actuators 2025, 14(3), 106; https://doi.org/10.3390/act14030106 - 21 Feb 2025
Abstract
To address the mismatch between materials and operational speed in mine scraper conveyors under time-varying load conditions, this paper proposes a methodology for the regulation of speed based on the quantity of coal transported by the scraper conveyor. Furthermore, a vector control strategy [...] Read more.
To address the mismatch between materials and operational speed in mine scraper conveyors under time-varying load conditions, this paper proposes a methodology for the regulation of speed based on the quantity of coal transported by the scraper conveyor. Furthermore, a vector control strategy for permanent magnet synchronous motors (PMSMs) is presented, underpinned by a global fast terminal sliding mode controller. Firstly, a calculation model for the real-time coal volume of the scraper conveyor was developed based on the double-end oblique cutting coal mining technology in fully mechanized mining operations. This model takes into account the operational condition of the shearer and the scraper conveyor. In addition, a graded speed regulation control method was introduced. Secondly, a global fast terminal controller was developed by integrating the features of linear and terminal sliding mode surfaces. An enhanced sliding mode vector control strategy for the permanent magnet drive motor of the scraper conveyor was subsequently proposed. Finally, a simulation and ground test were subsequently performed on the PMSM experimental bench and SGZ2×1200 scraper conveyor to validate the proposed control strategy. The results indicated that the proposed control strategy not only diminished the overshoot of the rotational speed and decreased the dynamic response time but also improved the anti-interference capabilities of the PMSM relative to the original PI control. Moreover, the ground test validated the feasibility of the suggested speed regulation method. Full article
(This article belongs to the Section Control Systems)
25 pages, 9780 KiB  
Article
Efficiency Optimization of PMSM-Type Elevator Machine: An Industrial Comparison
by Mucahit Soyaslan, Osman Eldogan, Ahmet Fenercioglu, Yusuf Avsar, Nurdogan Ceylan and Muhammed Salih Sarıkaya
Machines 2025, 13(3), 173; https://doi.org/10.3390/machines13030173 - 21 Feb 2025
Abstract
This study presents the design, modeling, and prototyping of an external rotor permanent magnet synchronous motor (ER-PMSM) specifically for elevator traction systems. The external rotor design aims to surpass the efficiency of conventional inner rotor gearless elevator traction motors. A commercially available 4 [...] Read more.
This study presents the design, modeling, and prototyping of an external rotor permanent magnet synchronous motor (ER-PMSM) specifically for elevator traction systems. The external rotor design aims to surpass the efficiency of conventional inner rotor gearless elevator traction motors. A commercially available 4 kW inner rotor permanent magnet synchronous motor (IR-PMSM) was selected for comparative analysis. Critical parameters, including stator tooth tip thickness, slot tip radius, slot height, stator yoke height, stator tooth thickness, and the number of turns per phase, were optimized to enhance efficiency. The artificial bee colony (ABC) algorithm was utilized for the first time to determine the optimal configuration of an external rotor PMSM. The prototype was fabricated and subjected to rigorous testing using a dedicated electrical motor test setup. Comparative results demonstrated a significant improvement in efficiency for the ER-PMSM over the IR-PMSM, with the efficiency increasing from 72.5% to 84.67% at nominal operating conditions. Full article
Show Figures

Figure 1

Figure 1
<p>Inner and external rotor topologies [<a href="#B14-machines-13-00173" class="html-bibr">14</a>].</p>
Full article ">Figure 2
<p>Dimensions of the ER-PMSM section.</p>
Full article ">Figure 3
<p>(<b>a</b>) Magnetic equivalent circuit model [<a href="#B15-machines-13-00173" class="html-bibr">15</a>,<a href="#B16-machines-13-00173" class="html-bibr">16</a>], and (<b>b</b>) path of magnetic flux.</p>
Full article ">Figure 4
<p>ER-PMSM’s equivalent electrical circuit model along the (<b>a</b>) d axis and (<b>b</b>) q axis [<a href="#B1-machines-13-00173" class="html-bibr">1</a>].</p>
Full article ">Figure 5
<p>Slot area and dimensions.</p>
Full article ">Figure 6
<p>(<b>a</b>) Cogging torque graph for the embrace values between 0.7 and 0.8; and (<b>b</b>) FFT of induced voltage for the embrace value of 0.78 [<a href="#B11-machines-13-00173" class="html-bibr">11</a>].</p>
Full article ">Figure 7
<p>Algorithm of motor design.</p>
Full article ">Figure 8
<p>Optimization of efficiency with the ABC algorithm.</p>
Full article ">Figure 9
<p>Mesh structure of the ER-PMSM.</p>
Full article ">Figure 10
<p>Magnetic flux density—<span class="html-italic">B</span> (Tesla).</p>
Full article ">Figure 11
<p>Magnetic field strength—<span class="html-italic">H</span> (A/m) and magnetic vector potential—<span class="html-italic">A</span> (Wb/m) of the ER-PMSM.</p>
Full article ">Figure 12
<p>Electrical current density—J (A/m<sup>2</sup>).</p>
Full article ">Figure 13
<p>Current graph.</p>
Full article ">Figure 14
<p>Induced back-EMF voltages.</p>
Full article ">Figure 15
<p>Output torque graph.</p>
Full article ">Figure 16
<p>Speed graph.</p>
Full article ">Figure 17
<p>Efficiency graph.</p>
Full article ">Figure 18
<p>Thermal analysis results: (<b>a</b>) temperature distribution, and (<b>b</b>) total heat flux.</p>
Full article ">Figure 19
<p>The ER-PMSM’s final design.</p>
Full article ">Figure 20
<p>Assembly photos of the prototype motor.</p>
Full article ">Figure 21
<p>Produced ER-PMSM Dimensions.</p>
Full article ">Figure 22
<p>Experimental setup: (1) prototype motor, (2) torque sensor, (3) reducer, (4) loading servo motor, (5) couplings, (6) driver of the loading motor, (7) driver of the prototype motor, (8) power supply and power analyzer, (9) multimeter, (10) data acquisition card, and (11) computer.</p>
Full article ">Figure 23
<p>Induced back-EMF voltage.</p>
Full article ">Figure 24
<p>Torque–time graph for various loading rates.</p>
Full article ">Figure 25
<p>Torque–current graph for various loading rates.</p>
Full article ">Figure 26
<p>Torque–current graph of the ER-PMSM.</p>
Full article ">Figure 27
<p>Torque–current test results graph of the IR-PMSM and ER-PMSM.</p>
Full article ">Figure A1
<p>Comparison inner rotor elevator traction machine [<a href="#B49-machines-13-00173" class="html-bibr">49</a>].</p>
Full article ">
19 pages, 3452 KiB  
Article
Sensorless Control of Ultra-High-Speed PMSM via Improved PR and Adaptive Position Observer
by Xiyue Bai, Weiguang Huang, Chuang Gao and Yingna Wu
Sensors 2025, 25(5), 1290; https://doi.org/10.3390/s25051290 - 20 Feb 2025
Abstract
To improve the precision of the position and speed estimation in ultra-high-speed (UHS) permanent magnet synchronous motors (PMSM) without position sensors, multiple refinements to the traditional extended electromotive force (EEMF) estimation algorithm are proposed in this paper. The key improvements include discretization compensation, [...] Read more.
To improve the precision of the position and speed estimation in ultra-high-speed (UHS) permanent magnet synchronous motors (PMSM) without position sensors, multiple refinements to the traditional extended electromotive force (EEMF) estimation algorithm are proposed in this paper. The key improvements include discretization compensation, high-frequency harmonic filtering, and the real-time adjustment of the phase-locked loop (PLL) bandwidth. Firstly, a discrete model is introduced to address EMF cross-coupling issues. Secondly, an improved proportional resonant (IPR) controller eliminating static errors is utilized in place of the conventional proportional-integral (PI) controller and low-pass filter (LPF) to enable precise electromotive force extraction, effectively filtering high-frequency harmonics that arise in low carrier ratio conditions. Based on a standard PR design, the IPR controller offers a streamlined calculation for target leading angles in delay compensation schemes to effectively mitigate discretization and delay errors. Additionally, an adaptive phase-locked loop (AQPLL) dynamically adjusts its bandwidth during acceleration to balance noise rejection and phase delay, reducing position estimation errors and optimizing torque. Simulations and experimental analyses on a motor (90,000 rpm, 30 kW) validate the effectiveness of the proposed sensorless driving techniques and demonstrate enhanced performance in position and velocity estimation, compared to the conventional EEMF approach. Full article
(This article belongs to the Section Physical Sensors)
Show Figures

Figure 1

Figure 1
<p>Overview of DSP-based sensorless FOC strategy.</p>
Full article ">Figure 2
<p>Overview of the conventional sensorless control strategy.</p>
Full article ">Figure 3
<p>Conventional EEMF observer.</p>
Full article ">Figure 4
<p>EMF cross-coupling decoupling during A/D conversion.</p>
Full article ">Figure 5
<p>Conventional QPLL structure.</p>
Full article ">Figure 6
<p>Bode diagram of conventional PR controller.</p>
Full article ">Figure 7
<p>(<b>a</b>) Block diagrams of continuous-domain resonant controllers featuring dual integrators, denoted as <math display="inline"><semantics> <mrow> <msub> <mi>G</mi> <mrow> <mi>P</mi> <msub> <mi>R</mi> <mi>h</mi> </msub> </mrow> </msub> <mrow> <mo stretchy="false">(</mo> <mi>s</mi> <mo stretchy="false">)</mo> </mrow> </mrow> </semantics></math>. (<b>b</b>) Resonant controllers with a phase lead <math display="inline"><semantics> <mrow> <msubsup> <mi>G</mi> <mrow> <mi>P</mi> <msub> <mi>R</mi> <mi>h</mi> </msub> </mrow> <mi>d</mi> </msubsup> <mrow> <mo stretchy="false">(</mo> <mi>s</mi> <mo stretchy="false">)</mo> </mrow> </mrow> </semantics></math>. (<b>c</b>) Digital resonant controllers with corrected poles <math display="inline"><semantics> <mrow> <msubsup> <mi>G</mi> <mrow> <mi>P</mi> <msub> <mi>R</mi> <mi>h</mi> </msub> </mrow> <mi>d</mi> </msubsup> <mrow> <mo stretchy="false">(</mo> <mi>z</mi> <mo stretchy="false">)</mo> </mrow> </mrow> </semantics></math>.</p>
Full article ">Figure 8
<p>Rapid motor speed variations resulting from a low QPLL bandwidth lead to misalignment in the control frames.</p>
Full article ">Figure 9
<p>Block diagram of the adaptive QPLL.</p>
Full article ">Figure 10
<p>Pole-zero map of AQPLL with fixed damping factor and increased natural frequency.</p>
Full article ">Figure 11
<p>Overview of the optimization sensorless control strategy.</p>
Full article ">Figure 12
<p>Experimental setup for sensorless FOC of the high-speed PMSM (<b>a</b>) Motor and compressor load. (<b>b</b>) Motor controller.</p>
Full article ">Figure 13
<p>Comparison of experimental results corresponding to the time when the motor speed increases from 50,000 rpm to 90,000 rpm within 0.6 s: (<b>a</b>) traditional EEMF, (<b>b</b>) IPR-based EEMF, and (<b>c</b>) adding AQPLL.</p>
Full article ">Figure 14
<p>When the motor is running stably, a 3Nm load is added within 0.25s, and the corresponding change in speed and position is reached when the load reaches stable operation again: (<b>a</b>) traditional EEMF, (<b>b</b>) IPR-based EEMF, and (<b>c</b>) adding AQPLL.</p>
Full article ">Figure 15
<p>Three methods of position error when the motor reaches steady-state operation at 90,000 rpm.</p>
Full article ">Figure 16
<p>Speed and position estimation errors when the motor parameters change to 2R and 0.8L under the EEMF method.</p>
Full article ">Figure 17
<p>Comparison of harmonic frequencies of current and EMF signals before and after IPR.</p>
Full article ">
26 pages, 25224 KiB  
Article
A Multi-Task Causal Knowledge Fault Diagnosis Method for PMSM-ITSF Based on Meta-Learning
by Ping Lan, Liguo Yao, Yao Lu and Taihua Zhang
Sensors 2025, 25(4), 1271; https://doi.org/10.3390/s25041271 - 19 Feb 2025
Abstract
In the process of diagnosing the inter-turn short circuit fault of the joint permanent magnet synchronous motor of an industrial robot, due to the small and sparse fault sample data, it is easy to misdiagnose, and it is difficult to quickly and accurately [...] Read more.
In the process of diagnosing the inter-turn short circuit fault of the joint permanent magnet synchronous motor of an industrial robot, due to the small and sparse fault sample data, it is easy to misdiagnose, and it is difficult to quickly and accurately evaluate the fault degree, lock the fault location, and track the fault causes. A multi-task causal knowledge fault diagnosis method for inter-turn short circuits of permanent magnet synchronous motors based on meta-learning is proposed. Firstly, the variation of parameters under the motor’s inter-turn short circuit fault is thoroughly investigated, and the fault characteristic quantity is selected. Comprehensive simulations are conducted using Simulink, Simplorer, and Maxwell to generate data under different inter-turn short circuit fault states; meanwhile, the sample data are accurately labeled. Secondly, the sample data are introduced into the learning network for training, and the multi-task synchronous diagnosis of the fault degree and position of the short circuit between turns is realized. Finally, the Neo4j database based on causality knowledge of motor inter-turn short circuit fault is constructed. Experiments show that this method can diagnose the fault location, fault degree, and fault cause of the motor with different voltage unbalanced degrees. The diagnosis accuracy of fault degree is 99.75 ± 0.25%, and the diagnosis accuracy of fault location and fault degree is 99.45 ± 0.21%. Full article
(This article belongs to the Special Issue Robot Swarm Collaboration in the Unstructured Environment)
Show Figures

Figure 1

Figure 1
<p>PMSM-ITSF Simulation Model.</p>
Full article ">Figure 2
<p>PMSM-ITSF Schematic Drawing.</p>
Full article ">Figure 3
<p>Multi-task meta-learning PMSM-ITSF causal knowledge diagnosis framework.</p>
Full article ">Figure 4
<p>Multi-task learning network.</p>
Full article ">Figure 5
<p>Meta-learning training process.</p>
Full article ">Figure 6
<p>MAML stochastic gradient descent algorithm.</p>
Full article ">Figure 7
<p>Knowledge graph fault diagnosis.</p>
Full article ">Figure 8
<p>Knowledge graph fault diagnosis system.</p>
Full article ">Figure 9
<p>Loss value and accurate value of the number of internal and external cycles.</p>
Full article ">Figure 10
<p>Fault diagnosis result of single-task unit learning.</p>
Full article ">Figure 11
<p>Fault diagnosis results of multi-task meta-learning.</p>
Full article ">Figure 12
<p>Voltage balance, Normal.</p>
Full article ">Figure 13
<p>Voltage balance, Phase C minor inter-turn short circuit fault.</p>
Full article ">Figure 14
<p>The voltage unbalance is 0.56%, Phase C minor inter-turn short circuit fault.</p>
Full article ">Figure 15
<p>The voltage unbalance is 2.8%, Phase C minor inter-turn short circuit fault.</p>
Full article ">Figure 16
<p>Voltage unbalance 0.56% diagnostic loss value and accurate value.</p>
Full article ">Figure 17
<p>Voltage unbalance 2.8% diagnostic loss value and accurate value.</p>
Full article ">Figure 18
<p>Diagnostic loss value and accurate value under different voltage balance degrees.</p>
Full article ">Figure 19
<p>Diagnostic loss and accuracy under voltage balance.</p>
Full article ">Figure 20
<p>Diagnostic loss and accuracy at 0.56% voltage unbalance.</p>
Full article ">Figure 21
<p>Diagnostic loss and accuracy at 2.8% voltage unbalance.</p>
Full article ">Figure 22
<p>Loss value and accuracy of diagnosis under different voltage balance degrees.</p>
Full article ">Figure 23
<p>PMSM-ITSF Fault Diagnosis Knowledge Graph.</p>
Full article ">
13 pages, 9723 KiB  
Article
Demagnetization Fault Diagnosis for PMSM Drive System with Dual Extended Kalman Filter
by Jiahan Wang, Chen Li and Zhanqing Zhou
World Electr. Veh. J. 2025, 16(2), 112; https://doi.org/10.3390/wevj16020112 - 18 Feb 2025
Abstract
Aiming at the irreversible demagnetization of permanent magnet synchronous motors (PMSMs) under extreme working conditions, a fault diagnosis method for permanent magnet demagnetization based on multi-parameter estimation is proposed in this paper. This scheme aims to provide technical support for enhancing the safety [...] Read more.
Aiming at the irreversible demagnetization of permanent magnet synchronous motors (PMSMs) under extreme working conditions, a fault diagnosis method for permanent magnet demagnetization based on multi-parameter estimation is proposed in this paper. This scheme aims to provide technical support for enhancing the safety and reliability of permanent magnet motor drive systems. In the proposed scheme, multiple operating states of the motor are acquired by injecting sinusoidal current signals into the d-axis, ensuring that the parameter estimation equation satisfies the full rank condition. Furthermore, the accurate dq-axis inductance parameters are obtained based on a recursive least square method. Subsequently, a dual extended Kalman filter is employed to acquire real-time permanent magnet flux linkage data of PMSMs, and the estimation data between the two algorithms are transferred to each other to eliminate the bias of permanent magnet flux estimation caused by a parameter mismatch. Finally, accurate evaluation of the remanence level of the rotor permanent magnet and demagnetization fault diagnosis can be achieved based on the obtained permanent magnet flux linkage parameters. The experimental results show that the relative estimation errors of the dq-axis inductance and permanent magnet flux linkage are within 5%, which can realize the effective diagnosis of demagnetization fault and high-precision condition monitoring of a permanent magnet health. Full article
Show Figures

Figure 1

Figure 1
<p>Block diagram of the demagnetization fault diagnosis based on DEKF.</p>
Full article ">Figure 2
<p>Control block diagram of the proposed demagnetization fault diagnosis method.</p>
Full article ">Figure 3
<p>Experimental platform.</p>
Full article ">Figure 4
<p>Experimental waveforms of the stator current and its spectrum. (<b>a</b>) M1. (<b>b</b>) M2. (<b>c</b>) M3.</p>
Full article ">Figure 5
<p>Experimental results of the proposed diagnosis method in M1.</p>
Full article ">Figure 6
<p>Experimental results of the proposed diagnosis method in M2.</p>
Full article ">Figure 7
<p>Experimental results of the proposed diagnosis method in M3.</p>
Full article ">Figure 8
<p>Experimental results of the proposed diagnosis method at 1.2 N·m (<b>a</b>) M1 (<b>b</b>) M2, (<b>c</b>) M3.</p>
Full article ">
24 pages, 3724 KiB  
Review
Towards Digital Twin Modeling and Applications for Permanent Magnet Synchronous Motors
by Grace Firsta Lukman and Cheewoo Lee
Energies 2025, 18(4), 956; https://doi.org/10.3390/en18040956 - 17 Feb 2025
Abstract
This paper explores the potential of Digital Twin (DT) technology for Permanent Magnet Synchronous Motors (PMSMs) and establishes a foundation for its modeling and applications. While DTs have been widely applied in complex systems and simulation software, their use in electric motors, especially [...] Read more.
This paper explores the potential of Digital Twin (DT) technology for Permanent Magnet Synchronous Motors (PMSMs) and establishes a foundation for its modeling and applications. While DTs have been widely applied in complex systems and simulation software, their use in electric motors, especially PMSMs, remains limited. This study examines physics-based, data-driven, and hybrid modeling approaches and evaluates their feasibility for real-time simulation, fault detection, and predictive maintenance. It also identifies key challenges such as computational demands, data integration, and the lack of standardized frameworks. By assessing current developments and outlining future directions, this work provides insights into how DTs can be implemented for PMSMs and drive advancements in industrial applications. Full article
(This article belongs to the Section F3: Power Electronics)
Show Figures

Figure 1

Figure 1
<p>The number of publications about Industry 4.0, IoT, and Digital Twin, and the trend line of Digital Twin research.</p>
Full article ">Figure 2
<p>Data flow in (<b>a</b>) digital model; (<b>b</b>) digital shadow; and (<b>c</b>) Digital Twin (adapted from [<a href="#B16-energies-18-00956" class="html-bibr">16</a>]).</p>
Full article ">Figure 3
<p>Digital twin configuration for electric motors.</p>
Full article ">Figure 4
<p>PMSM key components.</p>
Full article ">Figure 5
<p>Physics-based motor modeling.</p>
Full article ">Figure 6
<p>Data-driven-based motor modeling.</p>
Full article ">Figure 7
<p>Physics-informed data-driven-based motor modeling.</p>
Full article ">Figure 8
<p>Real-life applications of PMSMs.</p>
Full article ">Figure 9
<p>Monitoring framework (adapted from [<a href="#B44-energies-18-00956" class="html-bibr">44</a>], Digital Twin route added).</p>
Full article ">Figure 10
<p>The most efficient motor selection process using Digital Twin (adapted from [<a href="#B49-energies-18-00956" class="html-bibr">49</a>]).</p>
Full article ">
15 pages, 10230 KiB  
Article
A Real-Time Demanded Current Observation-Based Sliding Mode Control of Permanent Magnet Synchronous Motors
by Guangping Li, Guolong Zhong, Likun Hu, Pingping Gong and Gaoxiang Li
Machines 2025, 13(2), 146; https://doi.org/10.3390/machines13020146 - 13 Feb 2025
Abstract
To improve the dynamic and steady-state performance of permanent magnet synchronous motors (PMSM), this paper proposes a real-time demanded current observation based sliding mode control strategy. Firstly, based on the mechanism between motor speed and current, a real-time demanded current observer is proposed, [...] Read more.
To improve the dynamic and steady-state performance of permanent magnet synchronous motors (PMSM), this paper proposes a real-time demanded current observation based sliding mode control strategy. Firstly, based on the mechanism between motor speed and current, a real-time demanded current observer is proposed, which can obtain the demanded current based on the motor speed. Secondly, the demanded current is directly used to calibrate the q-axis current reference in real-time, which can update the current reference value faster than the sliding mode controller. Due to the real-time demanded current feedforward, the anti-interference performance of the PMSM under the proposed control is improved effectively. Compared with the conventional sliding mode control, the proposed control has a better dynamic and steady-state performance. Finally, the effectiveness of the proposed control has been verified through simulation and experiments. Full article
(This article belongs to the Section Automation and Control Systems)
Show Figures

Figure 1

Figure 1
<p>Motion trajectory of SMC.</p>
Full article ">Figure 2
<p>Structural diagram of ESO.</p>
Full article ">Figure 3
<p>Overall block diagram of the control system.</p>
Full article ">Figure 4
<p>Simulation results of startup response under different <span class="html-italic">α</span>. (<b>a</b>) Speed response of startup. (<b>b</b>) Overshoot and adjustment time. (<b>c</b>) Steady-state error.</p>
Full article ">Figure 5
<p>Simulation results of startup response under different <span class="html-italic">δ</span>. (<b>a</b>) Speed response of startup. (<b>b</b>) Overshoot and adjustment time. (<b>c</b>) Steady-state error.</p>
Full article ">Figure 6
<p>Simulation results of startup response under different <span class="html-italic">β</span><sub>1</sub>. (<b>a</b>) Speed response of startup. (<b>b</b>) Overshoot and adjustment time. (<b>c</b>) Steady-state error.</p>
Full article ">Figure 7
<p>Simulation results of startup response under different <span class="html-italic">β</span><sub>2</sub>. (<b>a</b>) Speed response of startup. (<b>b</b>) Overshoot and adjustment time. (<b>c</b>) Steady-state error.</p>
Full article ">Figure 8
<p>Simulation results of startup response under different <span class="html-italic">b</span><sub>0</sub>. (<b>a</b>) Speed response of startup. (<b>b</b>) Overshoot and adjustment time. (<b>c</b>) Steady-state error.</p>
Full article ">Figure 9
<p>Real-time demanded current observer.</p>
Full article ">Figure 10
<p>Simulation results of response of startup.</p>
Full article ">Figure 11
<p>Simulation results of response of speed change.</p>
Full article ">Figure 12
<p>Simulation results of response of load change.</p>
Full article ">Figure 13
<p>Simulation results of a-phase current with load.</p>
Full article ">Figure 14
<p>Experimental platform.</p>
Full article ">Figure 15
<p>Experimental results of response of startup under different control strategies. (<b>a</b>) SMC-ESO. (<b>b</b>) SMC. (<b>c</b>) PID.</p>
Full article ">Figure 16
<p>Experimental results of response of speed change under different control strategies. (<b>a</b>) SMC-ESO. (<b>b</b>) SMC. (<b>c</b>) PID.</p>
Full article ">Figure 17
<p>Experimental results of response to load change under different control strategies. (<b>a</b>) SMC-ESO. (<b>b</b>) SMC. (<b>c</b>) PID.</p>
Full article ">Figure 18
<p>Experimental results of torque output of load change under different control strategies. (<b>a</b>) SMC-ESO. (<b>b</b>) SMC. (<b>c</b>) PID.</p>
Full article ">Figure 19
<p>Experimental results of a-phase current with load under different control strategies. (<b>a</b>) SMC-ESO. (<b>b</b>) SMC. (<b>c</b>) PID.</p>
Full article ">Figure 20
<p>Experimental data of the response under different control strategies during disturbance. (<b>a</b>) Speed change. (<b>b</b>) Load change.</p>
Full article ">
15 pages, 4396 KiB  
Article
Speed Optimization Control of a Permanent Magnet Synchronous Motor Based on TD3
by Zuolei Hu, Yingjie Zhang, Ming Li and Yuhua Liao
Energies 2025, 18(4), 901; https://doi.org/10.3390/en18040901 - 13 Feb 2025
Abstract
Permanent magnet synchronous motors (PMSMs) are widely used in industrial automation and electric vehicles due to their high efficiency and excellent dynamic performance. However, controlling PMSMs presents challenges such as parameter variations and system nonlinearities. This paper proposes a twin delayed deep deterministic [...] Read more.
Permanent magnet synchronous motors (PMSMs) are widely used in industrial automation and electric vehicles due to their high efficiency and excellent dynamic performance. However, controlling PMSMs presents challenges such as parameter variations and system nonlinearities. This paper proposes a twin delayed deep deterministic policy gradient (TD3)-based energy-saving optimization control method for PMSM drive systems. The TD3 algorithm uses double networks, target policy smoothing regularization, and delayed actor network updates to improve training stability and accuracy. Simulation experiments under two operating conditions show that the TD3 algorithm outperforms traditional proportional–integral (PI) controllers and linear active disturbance rejection control (LADRC) controllers in terms of reference trajectory tracking, q-axis current regulation, and speed tracking error minimization. The results demonstrate the TD3 algorithm’s effectiveness in enhancing motor efficiency and system robustness, offering a novel approach to PMSM drive system control through deep reinforcement learning. Full article
(This article belongs to the Section F1: Electrical Power System)
Show Figures

Figure 1

Figure 1
<p>Three-phase PMSM vector control block diagram.</p>
Full article ">Figure 2
<p>Structure of the TD3 algorithm.</p>
Full article ">Figure 3
<p>The dual closed-loop control structure of PMSM speed and current based on TD3.</p>
Full article ">Figure 4
<p>Snapshot of the implemented software.</p>
Full article ">Figure 5
<p>Training results for working condition 1.</p>
Full article ">Figure 6
<p>Experimental results of a PMSM operating in working condition 1. (<b>a</b>) Rotor speed; (<b>b</b>) Q-axis current; (<b>c</b>) speed tracking error.</p>
Full article ">Figure 7
<p>Training results for working condition 2.</p>
Full article ">Figure 8
<p>Experimental results of PMSM operating in working condition 2. (<b>a</b>) Rotor speed; (<b>b</b>) Q-axis current; (<b>c</b>) speed tracking error.</p>
Full article ">Figure 9
<p>Experimental results of a PMSM operating in working condition 2 with torque disturbances. (<b>a</b>) Working condition 1; (<b>b</b>) working condition 2.</p>
Full article ">
18 pages, 4733 KiB  
Article
Cascaded Extended State Observer-Based Composite Sliding-Mode Controller for a PMSM Speed-Loop Anti-Interference Control Strategy
by Yifan Xu, Bin Zhang, Yuxin Kang and He Wang
Sensors 2025, 25(4), 1133; https://doi.org/10.3390/s25041133 - 13 Feb 2025
Abstract
To enhance the speed-control performance of a permanent magnet synchronous motor (PMSM) drive system, an improved sliding-mode anti-interference control strategy is presented. Firstly, to tackle the speed fluctuation issue caused by cogging torque (a periodic disturbance) and time-varying disturbances at low set speeds [...] Read more.
To enhance the speed-control performance of a permanent magnet synchronous motor (PMSM) drive system, an improved sliding-mode anti-interference control strategy is presented. Firstly, to tackle the speed fluctuation issue caused by cogging torque (a periodic disturbance) and time-varying disturbances at low set speeds in PMSM, an improved sliding-mode control (ISMC) is proposed. It consists of a continuous adaptive fast terminal sliding-mode surface (CAFTSMS) and a new reaching law (NRL). The CAFTSMS boosts the system’s immunity to interference, while the NRL, improved via an adaptive function, enhances the fast transient response and notably reduces speed fluctuations. Secondly, a quasi-proportional resonant (QPR) controller is introduced. It suppresses specific-order system harmonics, significantly reducing the harmonic amplitude and strengthening the system’s ability to handle periodic disturbances. Finally, a cascaded extended state observer (CESO) with a special cascade structure is proposed to solve the observation-delay problem in the traditional cascade structure. Experimental results show that the proposed sliding-mode anti-disturbance control strategy performs excellently in overcoming disturbances. Full article
(This article belongs to the Section Intelligent Sensors)
Show Figures

Figure 1

Figure 1
<p>Comparison of the terminal attraction term with traditional sign function.</p>
Full article ">Figure 2
<p>ISMC control-block diagram.</p>
Full article ">Figure 3
<p>Bode diagrams of the QPR controller with one variable parameter. (<b>a</b>) <math display="inline"><semantics> <msub> <mi>k</mi> <mi>p</mi> </msub> </semantics></math>. (<b>b</b>) <math display="inline"><semantics> <msub> <mi>ω</mi> <mi>r</mi> </msub> </semantics></math>. (<b>c</b>) <math display="inline"><semantics> <msub> <mi>ω</mi> <mi>c</mi> </msub> </semantics></math>. (<b>d</b>) <math display="inline"><semantics> <msub> <mi>k</mi> <mi>r</mi> </msub> </semantics></math>.</p>
Full article ">Figure 4
<p>Control block diagram for the CESO.</p>
Full article ">Figure 5
<p>PMSM speed-regulation system.</p>
Full article ">Figure 6
<p>Experimental platform for permanent magnet synchronous motors.</p>
Full article ">Figure 7
<p>Step response of three algorithms at a set speed of 100 rpm, steady state speed fluctuation values and FFT analysis of speeds. (<b>a</b>) PI. (<b>b</b>) SMC. (<b>c</b>) ISMC.</p>
Full article ">Figure 8
<p>Steady state speed fluctuation values and FFT analysis of speeds at a set speed of 50 rpm. (<b>a</b>) PI. (<b>b</b>) SMC. (<b>c</b>) ISMC.</p>
Full article ">Figure 9
<p>Steady state speed fluctuation values and FFT analysis of speeds at a set speed of 75 rpm. (<b>a</b>) PI. (<b>b</b>) SMC. (<b>c</b>) ISMC.</p>
Full article ">Figure 10
<p>Comparison of maximum speed fluctuation values of three algorithms.</p>
Full article ">Figure 11
<p>The experimental results of introducing QPR on the basis of ISMC. (<b>a</b>) No QPR introduced. (<b>b</b>) 1 th. (<b>c</b>) 1 th and 2 th.</p>
Full article ">Figure 12
<p>The experimental results of applying and unloading the same magnitude of load to three algorithms. (<b>a</b>) SMC. (<b>b</b>) QPR-ISMC. (<b>c</b>) QPR-ISMC+CESO.</p>
Full article ">Figure 13
<p>Comparison of the observation error between ESO and CESO.</p>
Full article ">Figure 14
<p>Observation error of the observer when different observer bandwidths <math display="inline"><semantics> <msub> <mi>ω</mi> <mn>0</mn> </msub> </semantics></math> are selected. (<b>a</b>) <math display="inline"><semantics> <msub> <mi>ω</mi> <mn>0</mn> </msub> </semantics></math> = 20. (<b>b</b>) <math display="inline"><semantics> <msub> <mi>ω</mi> <mn>0</mn> </msub> </semantics></math> = 40. (<b>c</b>) <math display="inline"><semantics> <msub> <mi>ω</mi> <mn>0</mn> </msub> </semantics></math> = 60.</p>
Full article ">
21 pages, 3397 KiB  
Article
A Novel Filtering Observer: A Cost-Effective Estimation Solution for Industrial PMSM Drives Using in-Motion Control Systems
by Cagatay Dursun and Selin Ozcira Ozkilic
Energies 2025, 18(4), 883; https://doi.org/10.3390/en18040883 - 12 Feb 2025
Abstract
This paper presents a cost-efficient estimation method, the filtering observer (FOBS), which provides a smooth estimation through prior estimation, enhancing the field-oriented control (FOC) performance of motion control systems by estimating the angular rotor position, angular rotor velocity, and disturbance torque of permanent [...] Read more.
This paper presents a cost-efficient estimation method, the filtering observer (FOBS), which provides a smooth estimation through prior estimation, enhancing the field-oriented control (FOC) performance of motion control systems by estimating the angular rotor position, angular rotor velocity, and disturbance torque of permanent magnet synchronous motors (PMSMs). The cost-effective FOBS demonstrates characteristics akin to optimal estimating methods and employs arbitrary pole placement, facilitating more straightforward adjustment of the FOBS gain. The non-linear characteristics of low-resolution and low-cost encoders, the computation of angular rotor velocity using traditional techniques, and disturbances over broad frequency ranges in the servo drive system impair the efficacy of the motion control system. As a cost-effective solution, the FOBS minimizes the deficiencies of the low-cost encoder, reduces oscillations and measurement delays in the speed feedback signal, and provides smooth estimation of disturbance torque. Based on the results from experiments, the FOBS was compared against traditional approaches and the performance of the motion control system was examined. Also, the performance of the motion control system was investigated. The results indicate that these enhancements were achieved with low processing power and an easily implementable estimate technique suitable for low-cost industrial systems. Full article
Show Figures

Figure 1

Figure 1
<p>Illustration of M/T-method speed estimation method.</p>
Full article ">Figure 2
<p>Timeline of a priori and a posteriori state estimation.</p>
Full article ">Figure 3
<p>Illustration of proposed scheme for industrial PMSM drive system.</p>
Full article ">Figure 4
<p>(<b>a</b>) Pole and zero locations of the designed FOBS. (<b>b</b>) Variation of pole and zero locations for different inertias. (<b>c</b>) Variation of pole and zero locations for different sampling times. (<b>d</b>) Zoomed view of variation of pole and zero locations for different sampling times.</p>
Full article ">Figure 5
<p>(<b>a</b>) Block diagram of drive system. (<b>b</b>) Illustration of experimental test set-up.</p>
Full article ">Figure 6
<p>(<b>a</b>) Comparison of position feedback measured by QEP and FOBS at 600 r/min. (<b>b</b>) Zoomed response of position feedback measured by QEP and FOBS at 600 r/min. (<b>c</b>) Position error between QEP and FOBS at 30 r/min. (<b>d</b>) Comparison of position feedback measured by QEP and FOBS at 30 r/min. (<b>e</b>) Zoomed response of position feedback measured by QEP and FOBS at 30 r/min. (<b>f</b>) Position error between QEP and FOBS at 30 r/min.</p>
Full article ">Figure 7
<p>Velocity estimation performances of mentioned estimation methods: (<b>a</b>) 30 r/min, (<b>b</b>) zoomed view at 30 r/min, (<b>c</b>) zoomed view at 30 r/min with the FOBS and SSKF, (<b>d</b>) 600 r/min, (<b>e</b>) zoomed view at 600 r/min, (<b>f</b>) zoomed view at 600 r/min with the FOBS and SSKF, (<b>g</b>) 1800 r/min, (<b>h</b>) zoomed view at 1800 r/min, (<b>i</b>) zoom edview at 1800 r/min with the FOBS and SSKF.</p>
Full article ">Figure 8
<p>(<b>a</b>) Estimation of <math display="inline"><semantics> <mrow> <msub> <mrow> <mover accent="true"> <mrow> <mi>T</mi> </mrow> <mo>^</mo> </mover> </mrow> <mrow> <msub> <mrow> <mi>L</mi> </mrow> <mrow> <mi>k</mi> </mrow> </msub> </mrow> </msub> </mrow> </semantics></math> by the FOBS, SSKF, and SOBS under 0.5 Nm steady load. (<b>b</b>) Estimation of <math display="inline"><semantics> <mrow> <msub> <mrow> <mover accent="true"> <mrow> <mi>T</mi> </mrow> <mo>^</mo> </mover> </mrow> <mrow> <msub> <mrow> <mi>L</mi> </mrow> <mrow> <mi>k</mi> </mrow> </msub> </mrow> </msub> </mrow> </semantics></math> by the FOBS, SSKF, and SOBS under 1 Nm steady load.</p>
Full article ">Figure 9
<p>(<b>a</b>) Position loop response of the control system and estimation of angular position under 1 Nm steady load with various inertia mismatches. (<b>b</b>) Speed loop response of the control system and estimation of angular velocity under 1 Nm steady load with various inertia mismatches. (<b>c</b>) Disturbance torque estimation under 1 Nm steady load with various inertia mismatches.</p>
Full article ">Figure 10
<p>Execution times of mentioned estimation methods measured by a logic analyzer. (<b>a</b>) M/T method at moderate speed. (<b>b</b>) M/T method at low speed. (<b>c</b>) SOBS. (<b>d</b>) FOBS. (<b>e</b>) SSKF.</p>
Full article ">
16 pages, 7869 KiB  
Article
Enhanced Raccoon Optimization Algorithm for PMSM Electrical Parameter Identification
by Zhihong Hu, Jihao Zhan, Zelan Li, Xiangqing Hou, Zhiang Fu and Xiaoliang Yang
Energies 2025, 18(4), 869; https://doi.org/10.3390/en18040869 - 12 Feb 2025
Abstract
This article proposes an improved algorithm for the parameter identification of permanent magnet synchronous motors (PMSMs). An enhanced raccoon optimization algorithm (EROA) was formed by combining the raccoon optimization algorithm (ROA) with the adaptive exploration radius, raccoon-washing-food-inspired, and escaping-predator strategies. First, using some [...] Read more.
This article proposes an improved algorithm for the parameter identification of permanent magnet synchronous motors (PMSMs). An enhanced raccoon optimization algorithm (EROA) was formed by combining the raccoon optimization algorithm (ROA) with the adaptive exploration radius, raccoon-washing-food-inspired, and escaping-predator strategies. First, using some of the functions in IEEE CEC2015, the EROA solution has a large improvement in convergence speed and solution accuracy compared with other algorithms. Second, the EROA solution is more stable under the same conditions, as demonstrated by MATLAB parameter identification simulation. Finally, EROA is applied to motor parameter identification through motor control experiments. Full article
(This article belongs to the Special Issue Renewable Energy Management System and Power Electronic Converters)
Show Figures

Figure 1

Figure 1
<p>EROA main loop.</p>
Full article ">Figure 2
<p>Test results comparing EROA with other typical algorithms after 1000 iterations.</p>
Full article ">Figure 3
<p>TMDSHVMTRPFCKIT experimental bench.</p>
Full article ">Figure 4
<p>Experimental process.</p>
Full article ">Figure 5
<p>Comparison diagram of the algorithm iteration process.</p>
Full article ">Figure 6
<p>Results of 70 sets of data identification in MATLAB.</p>
Full article ">Figure 7
<p>Parameter identification process on a motor control platform.</p>
Full article ">Figure 8
<p>EROA Recognition Results in the Experimental Platform Chip.</p>
Full article ">
24 pages, 11241 KiB  
Article
Comparative Analysis of the Effect of Rotor Faults in the Performance of Low-Speed High-Torque Machines
by Carlos Madariaga-Cifuentes, Cesar Gallardo, Jose E. Ruiz-Sarrio, Juan A. Tapia and Jose A. Antonino-Daviu
Appl. Sci. 2025, 15(4), 1721; https://doi.org/10.3390/app15041721 - 8 Feb 2025
Abstract
Several studies have focused on modeling and analyzing the impact of rotor faults in conventional low-pole-count machines, while related research on low-speed high-torque (LSHT) machines with a high pole count remains limited. In these machines, the combination of low speed, high inertia, and [...] Read more.
Several studies have focused on modeling and analyzing the impact of rotor faults in conventional low-pole-count machines, while related research on low-speed high-torque (LSHT) machines with a high pole count remains limited. In these machines, the combination of low speed, high inertia, and high torque levels presents a critical application for advanced diagnosis techniques. The present paper aims to describe and quantify the impact of rotor faults on the performance of LSHT machine types during the design stage. Specifically, 10-pole and 16-pole synchronous reluctance machines (SynRMs), permanent magnet synchronous machines (PMSMs), and squirrel-cage induction machines (SCIMs) are assessed by means of detailed 2D simulations. The effects of eccentricity, broken rotor bars, and partial demagnetization are studied, with a focus on performance variations. The results show that LSHT PMSMs are not significantly affected by the partial demagnetization of a few magnets, and the same holds true for common faults in SynRMs and SCIMs. Nonetheless, a significant increase in torque ripple was observed for all evaluated faults, with different origins and diverse effects on the torque waveform, which could be hard or invasive to analyze. Furthermore, it was concluded that specialized diagnosis techniques are effectively required for detecting the usual faults in LSHT machines, as their effect on major performance indicators is mostly minimal. Full article
Show Figures

Figure 1

Figure 1
<p>LSHT machines in 3D sketches: (<b>a</b>) example of LSHT PMSM with 14 poles; (<b>b</b>) example of LSHT SCIM with 16 poles; (<b>c</b>) example of LSHT SynRM with 16 poles. The three-phase windings are highlighted in red, green, and blue for phases A, B, and C, respectively.</p>
Full article ">Figure 2
<p>Different eccentricity types in electric machines: (<b>a</b>) faultless machine; (<b>b</b>) machine with static eccentricity; (<b>c</b>) machine with dynamic eccentricity.</p>
Full article ">Figure 3
<p>Different misalignment types: (<b>a</b>) reference faultless machine; (<b>b</b>) parallel misalignment; (<b>c</b>) angular misalignment.</p>
Full article ">Figure 4
<p>Types of demagnetization in electrical machines: (<b>a</b>) position of magnetization probes; (<b>b</b>) machine with uniform demagnetization; (<b>c</b>) machine with partial demagnetization.</p>
Full article ">Figure 5
<p>Flowchart of the assessment of selected machines using FE simulations.</p>
Full article ">Figure 6
<p>Optimized machines for 10-pole LSHT applications: (<b>a</b>) PMSM; (<b>b</b>) SynRM; (<b>c</b>) SCIM.</p>
Full article ">Figure 7
<p>The resulting optimized 10-pole LSHT machines in 3D sketches: (<b>a</b>) PMSM; (<b>b</b>) SynRM; (<b>c</b>) SCIM.</p>
Full article ">Figure 8
<p>The 2D FE model used for the evaluation of 10-pole LSHT machines: (<b>a</b>) meshed best PMSM model; (<b>b</b>) meshed best SynRM model; (<b>c</b>) meshed best SCIM model. A quad-layer airgap was considered in all FE models to enhance accuracy.</p>
Full article ">Figure 9
<p>Optimized LSHT 16-pole machines: (<b>a</b>) PMSM; (<b>b</b>) SynRM; (<b>c</b>) SCIM.</p>
Full article ">Figure 10
<p>The resulting optimized 16-pole LSHT machines in 3D sketches: (<b>a</b>) PMSM; (<b>b</b>) SynRM; (<b>c</b>) SCIM.</p>
Full article ">Figure 11
<p>The 2D FE model used for the evaluation of 16-pole LSHT machines: (<b>a</b>) meshed best PMSM model; (<b>b</b>) meshed best SynRM model; (<b>c</b>) meshed best SCIM model. A quad-layer airgap was considered in all FE models to enhance accuracy.</p>
Full article ">
13 pages, 5279 KiB  
Article
Nonlinear Control of a Permanent Magnet Synchronous Motor Based on State Space Neural Network Model Identification and State Estimation by Using a Robust Unscented Kalman Filter
by Sergio Velarde-Gomez and Eduardo Giraldo
Eng 2025, 6(2), 30; https://doi.org/10.3390/eng6020030 - 7 Feb 2025
Abstract
This work proposes a nonlinear modeling of a permanent magnet synchronous motor (PMSM) based on state space neural networks. The state space neural network is trained and the state variables (currents in a direct–quadrature frame and the rotational speed) are estimated by considering [...] Read more.
This work proposes a nonlinear modeling of a permanent magnet synchronous motor (PMSM) based on state space neural networks. The state space neural network is trained and the state variables (currents in a direct–quadrature frame and the rotational speed) are estimated by considering a robust Unscented Kalman Filter (UKF). Two contributions are presented in this work: the fist one is a nonlinear modeling structure for a PMSM based on a state space neural network that allows real-time parameter identification, and the second one is PMSM neural network training and state estimation based on a robust UKF. The robustness of the UKF is obtained by using a singular value decomposition of the covariance matrix. A comparison analysis is performed over a real PMSM motor by considering the proposed approach and a linear approximation of the nonlinear model where the states and parameters are computed by using an Extended Kalman Filter. The identified model is validated in closed loop by considering a nonlinear control strategy based on state feedback linearization. Full article
(This article belongs to the Special Issue Artificial Intelligence for Engineering Applications)
Show Figures

Figure 1

Figure 1
<p>Block diagram that summarizes the proposed approach.</p>
Full article ">Figure 2
<p>Outputs of UKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 5 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100.</p>
Full article ">Figure 3
<p>States of UKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 5 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100.</p>
Full article ">Figure 4
<p>Inputs of UKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 5 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100.</p>
Full article ">Figure 5
<p>Parameters of UKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 5 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100.</p>
Full article ">Figure 6
<p>Outputs of EKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 5 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100.</p>
Full article ">Figure 7
<p>States of EKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 5 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100.</p>
Full article ">Figure 8
<p>Inputs of EKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 5 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100.</p>
Full article ">Figure 9
<p>Parameters of EKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 5 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100.</p>
Full article ">Figure 10
<p>Noise comparison for the output UKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 10, 25, 50, and 100 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100, 250, 500, and 1000.</p>
Full article ">Figure 11
<p>Noise comparison for the parameters UKF considering <math display="inline"><semantics> <mi>η</mi> </semantics></math> variance of 10, 25, 50, and 100 and <math display="inline"><semantics> <mi>ε</mi> </semantics></math> variance of 100, 250, 500, and 1000.</p>
Full article ">Figure 12
<p>High-speed reference tracking test from 800 to 1000 RPM.</p>
Full article ">
23 pages, 5948 KiB  
Article
Optimization of Ship Permanent Magnet Synchronous Motor ADRC Based on Improved QPSO
by Hongbo Xu, Jundong Zhang, Jiale Liu, Yang Cao and Ao Ma
Appl. Sci. 2025, 15(3), 1608; https://doi.org/10.3390/app15031608 - 5 Feb 2025
Abstract
To address the impact of load variations, external environmental changes, and the tuning of the parameters on Permanent Magnet Synchronous Motors (PMSMs) used in ships, this study proposes an Active Disturbance Rejection Control (ADRC) strategy for PMSMs, optimized by the Quantum-behaved Particle Swarm [...] Read more.
To address the impact of load variations, external environmental changes, and the tuning of the parameters on Permanent Magnet Synchronous Motors (PMSMs) used in ships, this study proposes an Active Disturbance Rejection Control (ADRC) strategy for PMSMs, optimized by the Quantum-behaved Particle Swarm Optimization (QPSO) algorithm. First, based on the PMSM model, the study addresses the limited disturbance rejection capability of the traditional fal function in the Extended State Observer (ESO) of conventional ADRC. To improve the accuracy of the state observer, the faln function is introduced as a replacement for the traditional fal function. Second, due to the numerous parameters in ADRC, which are difficult to tune, the QPSO algorithm—known for its strong global search capabilities and fast convergence speed—is utilized for parameter optimization. Additionally, the position update formula within the optimization algorithm is revised and optimized. Finally, simulation experiments are conducted using the Matlab/Simulink platform, where practical conditions, such as load fluctuations and random noise, are incorporated. The simulation results demonstrate that, compared to PSO-ADRC control, IPSO-ADRC control, and ICFO-ADRC control, the proposed method offers a superior dynamic response. Specifically, the speed control accuracy is improved by 46.7%, torque ripple is reduced by 50.8%, and harmonic distortion decreases by 23.1%. These results highlight the significant advantages of this method in enhancing system robustness, dynamic response speed, and steady-state accuracy, making it particularly suitable for PMSM control systems in complex dynamic environments, such as those encountered on ships. Full article
(This article belongs to the Special Issue Control of Power Systems II)
Show Figures

Figure 1

Figure 1
<p>Structure of Permanent Magnet Synchronous Motor Control System.</p>
Full article ">Figure 2
<p>ADRC Structure Diagram.</p>
Full article ">Figure 3
<p>Graph of the <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>f</mi> </mrow> <mrow> <mi>a</mi> <mi>l</mi> </mrow> </msub> </mrow> </semantics></math> function.</p>
Full article ">Figure 4
<p>Graph of the <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>f</mi> </mrow> <mrow> <mi>a</mi> <mi>l</mi> <mi>n</mi> </mrow> </msub> </mrow> </semantics></math> function.</p>
Full article ">Figure 5
<p>Particle Swarm Motion Diagram.</p>
Full article ">Figure 6
<p>QPSO Optimization Algorithm Flowchart.</p>
Full article ">Figure 7
<p>Ackley Function.</p>
Full article ">Figure 8
<p>Rastrigin function.</p>
Full article ">Figure 9
<p>Rosenbrock function.</p>
Full article ">Figure 10
<p>Griewank function.</p>
Full article ">Figure 11
<p>Time Comparison.</p>
Full article ">Figure 12
<p>Speed Curve Comparison.</p>
Full article ">Figure 13
<p>Speed Curve Comparison at 0.1 s.</p>
Full article ">Figure 14
<p>Speed Curve Comparison at 0.12 s.</p>
Full article ">Figure 15
<p>PSO-ADRC Control Torque Curve.</p>
Full article ">Figure 16
<p>QPSO-ADRC Control Torque Curve.</p>
Full article ">Figure 17
<p>FFT Analysis of Phase A.</p>
Full article ">
25 pages, 9084 KiB  
Article
Real-Time Modeling of Static, Dynamic and Mixed Eccentricity in Permanent Magnet Synchronous Machines
by Ramón Pérez, Jérôme Cros and Mathieu Picard
Machines 2025, 13(2), 120; https://doi.org/10.3390/machines13020120 - 4 Feb 2025
Abstract
Eccentricity faults are one of the main causes that significantly affect the performance of permanent magnet synchronous machines (PMSMs). Monitoring eccentricity in real time could prevent failures by adapting operation conditions and maintenance schedule when early signs of deterioration are detected. This article [...] Read more.
Eccentricity faults are one of the main causes that significantly affect the performance of permanent magnet synchronous machines (PMSMs). Monitoring eccentricity in real time could prevent failures by adapting operation conditions and maintenance schedule when early signs of deterioration are detected. This article proposes making a circuit-type model of a permanent magnet machine with an easily configurable eccentricity for simulations and real-time analysis of signals under different operating conditions. The basis for the construction of the circuit model will be the simulation of the PMSM with 49 different coordinates of the rotor center, using the finite element analysis (FEA). The presence of eccentricity causes a variation in the inductances, the no-load flux and the expansion torque depending on the position of the rotor. The model proposes the use of bilinear interpolation (BI) to estimate the inductance matrix, the no-load flux vector captured by the stator winding and the cogging torque due to the presence of the magnets in the rotor, all of them for each rotor position. The validation is done by comparing the precision in the results of the machine’s self-inductances, the torque and the voltage waveform at the PMSM terminals and the static torque of the PMSM. The circuit model results are validated in two ways: (1) through experimental simulation, comparing the same results obtained using FEA and (2) through practical experimentation, producing a dynamic eccentricity in the machine of 0.3 mm. The results show that the proposed model is capable of accurately reproducing the behavior of the PMSM against eccentricity faults and presents computational time savings close to 99% compared to the response time obtained using FEA. This rapid PMSM model, parameterizable according to the degree of eccentricity, is the basis for the real-time simulation of the main machine waveforms, such as voltage, current and torque. Full article
(This article belongs to the Special Issue Fault Diagnostics and Fault Tolerance of Synchronous Electric Drives)
Show Figures

Figure 1

Figure 1
<p>Graphic representation of eccentricity on the machine. (<b>a</b>) Healthy machine; (<b>b</b>) Static eccentricity; (<b>c</b>) Dynamic eccentricity.</p>
Full article ">Figure 2
<p>Graphical representation of bilinear interpolation.</p>
Full article ">Figure 3
<p>Procedure for the identification of <math display="inline"><semantics> <mrow> <mfenced open="[" close="]" separators="|"> <mrow> <mi mathvariant="bold-italic">L</mi> <mfenced separators="|"> <mrow> <mi>θ</mi> </mrow> </mfenced> </mrow> </mfenced> </mrow> </semantics></math> of given machine excentricity <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>x</mi> </mrow> <mrow> <mi>i</mi> </mrow> </msub> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>y</mi> </mrow> <mrow> <mi>i</mi> </mrow> </msub> </mrow> </semantics></math> with FE model.</p>
Full article ">Figure 4
<p>Procedure for the identification of <math display="inline"><semantics> <mrow> <mfenced open="[" close="]" separators="|"> <mrow> <msub> <mrow> <mi mathvariant="bold-italic">λ</mi> </mrow> <mrow> <mi>m</mi> </mrow> </msub> <mfenced separators="|"> <mrow> <mi>θ</mi> </mrow> </mfenced> </mrow> </mfenced> </mrow> </semantics></math> of given machine excentricity <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>x</mi> </mrow> <mrow> <mi>i</mi> </mrow> </msub> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>y</mi> </mrow> <mrow> <mi>i</mi> </mrow> </msub> </mrow> </semantics></math> with FE model.</p>
Full article ">Figure 5
<p>(<b>a</b>) PMSM used for the study and (<b>b</b>) the rotor center coordinates.</p>
Full article ">Figure 6
<p>Geometry and meshing of the PMSM with an FEA model.</p>
Full article ">Figure 7
<p>Parameters of phase A in the presence of static eccentricity as a function of the rotor position for 3 different CR positions. (<b>a</b>) Self-inductance; (<b>b</b>) no-load flow captured by the winding.</p>
Full article ">Figure 8
<p>Block diagram of command method implemented in MATLAB/Simulink.</p>
Full article ">Figure 9
<p>Bilinear interpolation carried out in the Simulink environment.</p>
Full article ">Figure 10
<p>Detail of the PMSM command diagram.</p>
Full article ">Figure 11
<p>PMSM coupled circuit model in Simulink block diagram.</p>
Full article ">Figure 12
<p>Self-inductance variations for (<b>a</b>) SE with <math display="inline"><semantics> <mrow> <mi>x</mi> </mrow> </semantics></math> = −0.15 mm and <math display="inline"><semantics> <mrow> <mi>y</mi> </mrow> </semantics></math> = 0.1 mm, (<b>b</b>) DE = 0.3 mm, (<b>c</b>) ME: SE with <math display="inline"><semantics> <mrow> <mi>x</mi> </mrow> </semantics></math> = −0.15 mm and <math display="inline"><semantics> <mrow> <mi>y</mi> </mrow> </semantics></math> = 0.1 mm + DE = 0.3 mm.</p>
Full article ">Figure 13
<p>No-load flux captured by the stator winding results: (<b>a</b>) SE with <math display="inline"><semantics> <mrow> <mi>x</mi> </mrow> </semantics></math> = −0.15 mm and <math display="inline"><semantics> <mrow> <mi>y</mi> </mrow> </semantics></math> = 0.1 mm, (<b>b</b>) DE = 0.3 mm, (<b>c</b>) ME: SE with <math display="inline"><semantics> <mrow> <mi>x</mi> </mrow> </semantics></math> = −0.15 mm and <math display="inline"><semantics> <mrow> <mi>y</mi> </mrow> </semantics></math> = 0.1 mm + DE = 0.3 mm.</p>
Full article ">Figure 13 Cont.
<p>No-load flux captured by the stator winding results: (<b>a</b>) SE with <math display="inline"><semantics> <mrow> <mi>x</mi> </mrow> </semantics></math> = −0.15 mm and <math display="inline"><semantics> <mrow> <mi>y</mi> </mrow> </semantics></math> = 0.1 mm, (<b>b</b>) DE = 0.3 mm, (<b>c</b>) ME: SE with <math display="inline"><semantics> <mrow> <mi>x</mi> </mrow> </semantics></math> = −0.15 mm and <math display="inline"><semantics> <mrow> <mi>y</mi> </mrow> </semantics></math> = 0.1 mm + DE = 0.3 mm.</p>
Full article ">Figure 14
<p>Voltage in phase A of the PMSM for a DE = 0.3 mm.</p>
Full article ">Figure 15
<p>Torque developed by the PMSM for (<b>a</b>) SE with x = −0.15 mm and y = 0.1 mm. (<b>b</b>) Relative error for SE; (<b>c</b>) DE = 0.3 mm and (<b>d</b>) relative error for DE.</p>
Full article ">Figure 16
<p>Bushings to produce static eccentricity. (<b>a</b>) Front view, (<b>b</b>) side view and dynamic eccentricity (<b>c</b>) front view, (<b>d</b>) side view.</p>
Full article ">Figure 17
<p>Bearing for the study of eccentricity.</p>
Full article ">Figure 18
<p>Production of a dynamic eccentricity of 0.3 mm in the PMSM.</p>
Full article ">Figure 19
<p>(<b>a</b>) Rotor bushings and (<b>b</b>) stator bushings producing a dynamic eccentricity of 0.3 mm.</p>
Full article ">Figure 20
<p>PMSM with a 0.3 mm dynamic eccentricity fault.</p>
Full article ">Figure 21
<p>Block diagram of the experiment carried out.</p>
Full article ">Figure 22
<p>PMSM speed during the experiment carried out.</p>
Full article ">Figure 23
<p>Measured rotor angular position and rotor angular position estimated by the proposed model.</p>
Full article ">Figure 24
<p>Comparison between the static torque measured experimentally and the static torque obtained from the model proposed.</p>
Full article ">Figure 25
<p>Measured static torque and estimated static torque by the proposed model.</p>
Full article ">
Back to TopTop