CN115296542A - Active clamping three-tube push-pull full-bridge bidirectional DC-DC converter modulation strategy - Google Patents
Active clamping three-tube push-pull full-bridge bidirectional DC-DC converter modulation strategy Download PDFInfo
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- 238000004804 winding Methods 0.000 description 10
- 238000004146 energy storage Methods 0.000 description 4
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33584—Bidirectional converters
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a modulation strategy of an active clamping three-tube push-pull full-bridge bidirectional DC-DC converter, and the active clamping three-tube push-pull full-bridge bidirectional DC-DC converter related by the method comprises a primary side support capacitor C i A clamp capacitor C a Three-tube push-pull circuit and 2 auxiliary inductors L k1 、L k2 Secondary side supported capacitor C o The full-bridge circuit, the power inductor L and the high-frequency transformer T; the primary side three-tube push-pull circuit comprises a switch tube S 1 、S 2 、S 3 The secondary side full bridge circuit comprises a switch tube S 4 、S 5 、S 6 、S 7 Transformer turn ratio 1:1: n, switching frequency of f s . In the invention, ZVS switching-on of all power tubes can be realized in the whole power transmission range, the power tubes in the push-pull circuit are clamped by the input power supply and the clamping capacitor together, and the power tubes in the full-bridge circuit are output by the output powerThe source clamping has no voltage peak, is suitable for medium and high power bidirectional energy transmission occasions, and has the advantages of low loss, high efficiency, low voltage stress of a switching tube and the like.
Description
Technical Field
The invention relates to the technical field of power electronic change, in particular to a modulation strategy of an active clamping three-tube push-pull full-bridge bidirectional DC-DC converter.
Background
In an energy storage system, an energy storage end and a bus are generally connected by an isolated bidirectional DC-DC converter to meet the requirement of bidirectional electric energy conversion of charging and discharging. The traditional isolated bidirectional DC-DC converter takes a double-active bridge bidirectional DC-DC converter (DAB) as an example, has the advantages of symmetrical structure, simple control, easy realization of soft switching for heavy load and the like, but when input and output voltages are not matched, the circuit is difficult to realize soft switching at the moment of light load, the circulating current in the circuit is increased, and finally the working efficiency of the converter is lower. When the Voltage of the Energy Storage terminal is low, a push-pull circuit is suitable for the occasion, an article named as 'Analysis of a Novel Zero-Voltage-Switching Bidirectional DC/DC Converter for Energy Storage System' in IEEE Transaction on Industrial Electronics in the power Electronics journal introduces a three-tube push-pull full-bridge Bidirectional DC-DC Converter topology, so that the problem of large circulating current when the Voltage is not matched can be reduced, but the problem that a power tube is difficult to realize ZVS when the Voltage is light is still existed, and due to the influence of transformer leakage inductance, a Voltage peak can appear when the power tube in the push-pull circuit is turned off; an article named as "a two-stage dc-dc converter for the fuel cell-super capacitor hybrid system" in the IEEE Energy Conversion convergence and expansion of the power electronics international conference applies a push-pull forward converter to the low-voltage side and adds a coupling inductor, and the voltage spike of the power tube in the structure can be absorbed by a clamping capacitor, but the structure also has the defects of narrow ZVS range and the like.
Disclosure of Invention
The invention aims to provide a variable duty ratio and phase shift modulation strategy aiming at the defects of the prior art and aiming at an active clamping three-tube push-pull full-bridge bidirectional DC-DC converter, which is mainly characterized in that: all power tubes can realize ZVS (zero voltage switching) opening in the whole power transmission range, the power tubes in the push-pull circuit are clamped by an input power supply and a clamping capacitor together, the power tubes in the full-bridge circuit are clamped by an output power supply, and no voltage peak exists. The method is suitable for medium and high power bidirectional energy transmission occasions, and has the advantages of small loss, high efficiency, low voltage stress of the switching tube and the like.
The invention adopts the following technical scheme for realizing the aim of the invention:
an active clamping three-tube push-pull full-bridge bidirectional DC-DC converter modulation strategy comprises that the active clamping three-tube push-pull full-bridge bidirectional DC-DC converter comprises a primary side support capacitor C i A clamp capacitor C a Three-tube push-pull circuit and 2 auxiliary inductors L k1 、L k2 Secondary side support capacitor C o The full-bridge circuit, the power inductor L and the high-frequency transformer T; the primary side three-tube push-pull circuit comprises a switch tube S 1 、S 2 、S 3 The secondary side full bridge circuit comprises a switch tube S 4 、S 5 、S 6 、S 7 Transformer turn ratio 1:1: n, switching frequency of f s ；
Power tube S in primary side push-pull circuit 1 And S 2 The drive signal of (A) is a square wave signal with a phase difference of 180 DEG and a duty ratio of more than or equal to 0.5, and the power tube S 3 The driving signal of is a power tube S 1 And S 2 Complementary drive signals of (a); power tube S in secondary side full bridge circuit 4 And S 5 The driving signals are complementary square wave signals with the duty ratio equal to 0.5, and the power tube S 6 And S 7 Respectively with the power transistor S 5 And S 4 The driving signals of (2) are the same;
power tube S 3 Duty ratio of driving signal is D, power tube S 4 、S 5 、S 6 、S 7 Driving signal and power tube S 1 、S 2 And S 3 With phase shift angle between drive signals
According to the phase shift angle
The voltage of the secondary side of the transformer can be divided into two working conditions, namely a condition 1 and a condition 2, wherein the condition 1 works in a light load situation, the secondary side voltage of the transformer is a four-level square wave, and when the transformer runs under a light load, the four-level square wave can increase the peak value of an inductive current so as to ensure that a secondary side power tube realizes ZVS (zero voltage switching) switching-on; case 2 works in a heavy-load situation, the secondary side voltage of the transformer is a six-level square wave, and when the converter runs in a heavy load, the six-level square wave can reduce the effective value of current on the premise that the converter can transmit a high-power load, so that the circuit loss is reduced.
Preferably, all power tubes can realize ZVS turn-on in the whole power transmission range, and the voltage across all power tubes is clamped when the power tubes are turned off, and no voltage spike exists.
Preferably, the transmission power when the circuit is operating in forward and reverse directions can be obtained:
forward direction:
and (3) reversing:
wherein the power reference is:
compared with the prior art, the invention adopting the technical scheme has the following beneficial effects:
1. the invention provides an active clamping three-tube push-pull full-bridge bidirectional DC-DC converter modulation strategy, wherein ZVS (zero voltage switching) opening can be realized in the whole power transmission range of all power tubes, the power tubes in a push-pull circuit are clamped by an input power supply and a clamping capacitor together, the power tubes in a full-bridge circuit are clamped by an output power supply, and no voltage spike exists.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the embodiments or the prior art descriptions will be briefly described below, and it is obvious that the drawings in the following description are some embodiments of the present invention, and other drawings can be obtained by those skilled in the art without creative efforts.
FIG. 1 is a schematic diagram of a topological structure of an active clamping three-tube push-pull full-bridge bidirectional DC-DC converter;
FIGS. 2 and 3 are schematic diagrams of main waveforms of a modulation strategy when the active clamp three-tube push-pull full-bridge bidirectional DC-DC converter transmits power in forward and reverse directions;
FIG. 4 is a boundary diagram of the working conditions;
FIG. 5 is a schematic diagram of the operation mode of the converter in the operation condition 1;
FIG. 6 is a schematic diagram of the operation mode of the converter in the operation condition 2;
FIG. 7 is a three-dimensional graph of transmission power under the modulation strategy of the active clamp three-tube push-pull full-bridge bidirectional DC-DC converter.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
FIG. 1 is a schematic diagram of a topological structure of an active clamping three-tube push-pull full-bridge bidirectional DC-DC converter, and a capacitor C is supported by a primary side i A clamp capacitor C a Three-tube push-pull circuit and 2 auxiliary inductors L k1 、L k2 Secondary side support capacitor C o The full-bridge circuit, the power inductor L and the high-frequency transformer T; wherein the primary side three-tube push-pull circuit comprises a switching tube S 1 、S 2 、S 3 The secondary side full-bridge circuit comprises a switching tube S 4 、S 5 、S 6 、S 7 Transformer turn ratio 1:1: n, switching frequency of f s . Providing a modulation strategy according to the structure composition of a converter, and providing a power tube S in a primary side push-pull circuit 1 And S 2 The drive signal of (A) is a square wave signal with a phase difference of 180 DEG and a duty ratio of more than or equal to 0.5, and the power tube S 3 The driving signal of is a power tube S 1 And S 2 Complementary drive signals of (a); power tube S in secondary side full bridge circuit 4 And S 5 The driving signal of (A) is a complementary square wave signal with a duty ratio equal to 0.5, and the power tube S 6 And S 7 Respectively with the power transistor S 5 And S 4 The same, and furthermore, a certain dead time is added between the complementary drive signals.
Fig. 2 and fig. 3 are schematic diagrams of main waveforms of modulation strategies during forward and reverse power transmission of the active clamp three-tube push-pull full-bridge bidirectional DC-DC converter. Wherein v is ab And v cd Respectively represents the secondary side voltage of the transformer and the midpoint voltage of a bridge arm of a full-bridge circuit, i L 、i Lk1 、i Lk2 Respectively representing power inductor current, upper end auxiliary inductor current and lower end auxiliary inductor current, D representing power tube S 3 Duty ratio of the driving signal of (D) 1 Denotes a power tube S 3 And a power tube S 4 The phase shift angle of the drive signal. For ease of analysis, an out-shifted phase angle is introduced
The expression is as follows:
at the moment, the phase shift angle is added through the variable duty ratio D
The modulation strategy can realize the forward and reverse transmission of power and the buck-boost function of the converter.
FIG. 4 is a boundary diagram of the operating conditions according to the power transistor S 3 And a power tube S 4 The relative position of the driving signal between the two driving signals, when the converter transmits power in the forward and reverse directions, the two working conditions can be divided into a condition 1 and a condition 2, wherein the condition 1 generally works in a light load situation, and the condition 2 generally works in a heavy load situation.
FIG. 5 is a schematic diagram of the working mode of the forward transmission power time converter in working condition 1, and the circuit works symmetrically in the front half period and the back half period, so that the forward transmission power time converter mainly works on [ t [ t ] ] 0 ～t 0 ']、[t 0 '～t 1 ]、[t 1 ～t 1 ']、[t 1 '～t 2 ]、[t 2 ～t 2 ']、[t 2 '～t 3 ]Half-cycle analysis was performed for 6 working modes.
For convenience, the following assumptions can be made before analysis: 1) The power tube, the transformer and the inductor are all ideal devices, and the junction capacitances of the power tube at the high-voltage side and the low-voltage side are respectively equal and are kept unchanged; 2) Primary side auxiliary inductor L k1 ＝L k2 ＝L k (ii) a 3) The clamp capacitance can be considered as a constant voltage source; 4) The voltage of the primary winding and the secondary winding of the transformer is equal to S 3 Duty cycle D of the drive signal is coupled, and v is assumed during analysis ab High level equal to output voltage V o
1. Modal 1[t 0 ～t 0 ']
At t 0 Time of day off S 3 Due to the presence of junction capacitance, S 3 Is turned off at zero voltage, and simultaneously an auxiliary inductor and an inductor L/n reduced to the primary side 2 Resonance with junction capacitanceThe period is large, the auxiliary inductor current is considered to be constant in the dead time, and the input voltage source, the clamping capacitor and the S are at the moment 1 、S 3 In series relation between junction capacitances, current i LK2 To S is given 1 Simultaneous discharge of junction capacitance and supply of S 3 The junction capacitor charges, and both are equal in size. At t 0 ' time, S 3 The voltage at both ends rises to V i +U ca ，S 1 The reverse diode is naturally conducted after the voltage at the two ends is reduced to 0, and S 3 The voltage across is clamped at V i +U ca To suppress the off-voltage spike.
2. Modal 2[t 0 '～t 1 ]
At t 0 ' time, S 1 On and current from S 1 Flows through the anti-parallel diode of (S), so that 1 And realizing zero voltage switching-on. Assume that the secondary winding voltage of the transformer is nu 1 Then inductor L, auxiliary inductor L k1 And L k2 The voltages born at the two ends are nu respectively 1 -V o 、u 1 -U Ca And- (U) Ca +u 1 ) At this time, the current of the inductor and the current of the auxiliary inductor will change linearly, and the slope is respectively:
in this mode, the primary side auxiliary inductor current is in a circulating state, and the change rate is simultaneously controlled by the clamp capacitor C a And an output power supply V o The secondary side inductance current is gradually reduced to 0 from the positive direction and continuously reduced to the negative direction as the power tube S 5 、S 6 Zero voltage turn-on creates conditions.
3. Modal 3[t 1 ～t 1 ']
At t 1 Is turned off at a moment S 4 And S 7 Due to the presence of junction capacitance, S 4 And S 7 For zero voltage turn-off, inductor current i L To give S 4 And S 7 Charging junction capacitor while simultaneously providing S 5 And S 6 The junction capacitance discharges and both are equal in magnitude. In thatt 1 ' time, S 4 、S 7 The voltage at both ends rises to V o ，S 5 、S 6 The voltage at the two ends is reduced to 0, and then the diode is turned on naturally.
4. Modal 4[t 1 '～t 2 ]
At t 1 ' time, S 5 、S 6 When the power tube is switched on, the current flows through the reverse diode of the power tube, so S 5 、S 6 And realizing zero voltage switching-on. Assume that the secondary winding voltage of the transformer is nu 2 An inductor L and an auxiliary inductor L k1 And L k2 The voltages borne by the two ends are nu respectively 2 +V o 、u 2 -U Ca And- (U) Ca +u 2 ) At this time, the current of the inductor and the current of the auxiliary inductor will change linearly, and the slope is respectively:
in this mode, the primary side auxiliary inductor current is still in a circulating current state, and the change rate is simultaneously controlled by the clamping capacitor C a And an output power supply V o Influence of the secondary inductor current from S 5 、S 6 The anti-parallel diode flows through, delivering power to the output.
5. Modal 5[t 2 ～t 2 ']
At t 2 Is turned off at a moment S 2 Due to the presence of junction capacitance, S 2 Is turned off at zero voltage, and the input voltage source, the clamping capacitor and S are turned off at this time 2 、S 3 The junction capacitors are connected in series to assist the inductor current i LK1 To give S 3 Simultaneous discharge of junction capacitance and supply of S 2 The junction capacitor charges, and both are equal in size. At t 2 ' time, S 2 The voltage at both ends rises to V i +U ca S3, the voltage at two ends is reduced to 0, then the reverse parallel diode is naturally conducted, and S 2 The voltage across is clamped at V i +U ca To suppress the off-voltage spike.
6. Modal 6[t 2 '～t 3 ]
At t 2 ' time, S 3 On and current from S 3 Flows through the anti-parallel diode of (S), so that 3 And realizing zero voltage switching-on. Assume that the secondary winding voltage of the transformer is nu 3 An inductor L and an auxiliary inductor L k1 And L k2 The voltages born at the two ends are nu respectively 3 +V o 、-(V i +u 3 ) And- (U) Ca +u 3 ) At this time, the current of the inductor and the current of the auxiliary inductor will change linearly, and the slope is respectively:
in this mode, the input power supply begins to transfer power, and the primary side auxiliary inductor current is simultaneously subjected to the clamp capacitor C a Input power supply V i And an output power supply V o Influence of (2), secondary side inductor current from S 5 、S 6 The anti-parallel diode flows through and delivers power to the output.
FIG. 6 is a schematic diagram of the working mode of the forward transmission power time converter in working condition 2, and the circuit works symmetrically in the front half period and the back half period, so that the forward transmission power time converter mainly comprises a pair of [ t [ t ] ] 0 ～t 0 ']、[t 0 '～t 1 ]、[t 1 ～t 1 ']、[t 1 '～t 2 ]、[t 2 ～t 2 ']、[t 2 '～t 3 ]Half-cycle analysis was performed for 6 working modes.
1. Modal 1[t 0 ～t 0 ']
At t 0 Time of day off S 3 Due to the presence of junction capacitance, S 3 The auxiliary inductor and the inductor L/n which is converted to the primary side of the transformer are turned off at zero voltage 2 And Q 1 、Q 3 The junction capacitance produces resonance, i can be considered in the dead time due to the larger resonance period LK1 、i LK2 Keeping constant, assisting the inductor current i LK2 To Q 1 Discharging junction capacitance while supplying Q 3 The junction capacitor charges, and both are equal in size. At t 0 ' time, S 3 Voltage acrossIs raised to V i +U ca ，Q 1 The reverse diode is naturally conducted after the voltage at the two ends is reduced to 0, and S 3 The voltage across is clamped at V i +U ca To suppress off-voltage spikes.
2. Modal 2[t 0 '～t 1 ]
At t 0 ' time, S 1 On and current from S 1 Flows through the anti-parallel diode, so that S 1 And realizing zero voltage switching-on. Assume that the secondary winding voltage of the transformer is nu 1 An inductor L and an auxiliary inductor L k1 And L k2 The voltages born at the two ends are nu respectively 1 -V o 、u 1 -U Ca And- (U) Ca +u 1 ) At this time, the current of the inductor and the current of the auxiliary inductor will change linearly, and the slope is respectively:
in this mode, the primary side auxiliary inductor current is in a circulating current state, and the change rate is simultaneously controlled by the clamping capacitor C a And an output power supply V o Influence, secondary side inductor current S 4 、S 7 The anti-parallel diode of (a) flows through and delivers power to the output.
3. Modal 3[t 1 ～t 1 ']
At t 1 Time of day off S 2 Due to the presence of junction capacitance, S 2 Auxiliary inductor current i for zero voltage turn-off LK1 To Q 3 Simultaneous Q supply while discharging junction capacitance 2 The junction capacitor charges, and both are equal in magnitude. At t 1 ' time, S 2 The voltage at both ends rises to V i +U ca ，S 3 The reverse diode is naturally conducted after the voltage at the two ends is reduced to 0, and S 2 The voltage across is clamped at V i +U ca To suppress the off-voltage spike.
4. Modal 4[t 1 '～t 2 ]
At t 1 ' time, S 3 On and current from S 3 Flows through the anti-parallel diode, so that S 3 And realizing zero voltage switching-on. Assume that the secondary winding voltage of the transformer is nu 2 Then inductor L, auxiliary inductor L k1 And L k2 The voltages borne by the two ends are nu respectively 2 -V o 、V i +u 2 And- (U) Ca +u 2 ) At this time, the current of the inductor and the current of the auxiliary inductor will change linearly, and the slopes are respectively as follows:
in this mode, the input power supply begins to deliver power, and the primary side auxiliary inductor current is simultaneously subjected to the clamp capacitor C o Input power supply V i And an output power supply V o The secondary side inductance current is gradually reduced to 0 from the positive direction and continuously reduced to the negative direction, and the secondary side inductance current is the power tube S 5 、S 6 Zero voltage turn-on creates conditions.
5. Modal 5[t 2 ～t 2 ']
At t 2 Is turned off at a moment S 4 And S 7 Due to the presence of junction capacitance, S 4 And S 7 For zero voltage turn-off, inductor current i L To S is given 4 And S 7 Charging junction capacitor while simultaneously providing S 5 And S 6 The junction capacitance discharges and both are equal in magnitude. At t 2 ' time, S 4 、S 7 The voltage at both ends rises to V o ，S 5 、S 6 After the voltage at the two ends is reduced to 0, the diode is reversely connected and naturally conducted.
6. Modal 6[t 2 '～t 3 ]
At t 2 ' time, S 5 、S 6 When the power tube is switched on, the current flows through the inverse parallel diode of the power tube, so that S 5 、S 6 And realizing zero voltage switching-on. Assume that the secondary winding voltage of the transformer is nu 3 Then inductor L, auxiliary inductor L k1 And L k2 The voltages born at the two ends are nu respectively 3 +V o 、V i +u 2 And- (U) Ca +u 2 ) At this time, the inductorAnd the auxiliary inductor current will change linearly, the slope is:
in this mode, the input power source still participates in power transfer, and the primary side leakage inductance current is simultaneously subjected to the clamping capacitor C o Input power supply V o And an output power supply V o Influence of (2), secondary side inductor current from S o 、S o The anti-parallel diode flows through, delivering power to the output.
According to the working principle of the circuits shown in the accompanying figures 5 and 6, the voltage of the clamping capacitor can be obtained:
according to the attached fig. 5 and fig. 6 and the voltage of the clamping capacitor, the voltage of each level of the secondary winding of the transformer can be obtained in sequence as follows:
case 1:
case 2:
according to the following figures 5 and 6 and the voltage of the secondary winding of the transformer, the transmission power of the circuit in forward operation can be obtained:
circuit transmission power in reverse operation:
wherein the power reference is:
fig. 7 is a three-dimensional graph of transmission power under the modulation strategy of the active clamp three-tube push-pull full-bridge bidirectional DC-DC converter of the invention, and it can be seen that the forward and reverse transmission power of the converter under the modulation strategy is completely symmetrical.
Finally, it should be noted that: the above embodiments are only used to illustrate the technical solution of the present invention, and not to limit the same; while the invention has been described in detail and with reference to the foregoing embodiments, it will be understood by those skilled in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some or all of the technical features may be equivalently replaced; and the modifications or the substitutions do not make the essence of the corresponding technical solutions depart from the scope of the technical solutions of the embodiments of the present invention.
Claims (3)
1. An active clamping three-tube push-pull full-bridge bidirectional DC-DC converter modulation strategy comprises that the active clamping three-tube push-pull full-bridge bidirectional DC-DC converter comprises a primary side support capacitor C i A clamp capacitor C a Three-tube push-pull circuit and 2 auxiliary inductors L k1 、L k2 Secondary side supported capacitor C o The power supply comprises a full-bridge circuit, a power inductor L and a high-frequency transformer T; the primary side three-tube push-pull circuit comprises a switch tube S 1 、S 2 、S 3 The secondary side full bridge circuit comprises a switch tube S 4 、S 5 、S 6 、S 7 Transformer turn ratio 1:1: n, switching frequency of f s The method is characterized in that:
power tube S in primary side push-pull circuit 1 And S 2 The drive signal of (A) is a square wave signal with a phase difference of 180 DEG and a duty ratio of more than or equal to 0.5, and the power tube S 3 The driving signal of (2) is a power tube S 1 And S 2 Complementary drive signals of (a); secondary side full bridge circuitMedium power tube S 4 And S 5 The driving signal of (A) is a complementary square wave signal with a duty ratio equal to 0.5, and the power tube S 6 And S 7 Respectively with the power transistor S 5 And S 4 The driving signals of the two driving circuits are the same;
power tube S 3 Duty ratio of driving signal is D, power tube S 4 、S 5 、S 6 、S 7 Driving signal and power tube S 1 、S 2 And S 3 With phase shift angle between drive signals
According to the phase shift angle
The voltage of the secondary side of the transformer can be divided into two working conditions, namely a condition 1 and a condition 2, wherein the condition 1 works in a light load situation, the secondary side voltage of the transformer is a four-level square wave, and when the transformer runs under a light load, the four-level square wave can increase the peak value of an inductive current so as to ensure that a secondary side power tube realizes ZVS (zero voltage switching) switching-on; case 2 works in a heavy-load situation, the secondary side voltage of the transformer is a six-level square wave, and when the converter runs in a heavy load, the six-level square wave can reduce the effective value of current on the premise that the converter can transmit a high-power load, so that the circuit loss is reduced.
2. The modulation strategy of claim 1, wherein all power transistors can achieve ZVS on-state in the whole power transmission range, and the voltage across all power transistors is clamped and there is no voltage spike when the power transistors are turned off.
3. The modulation strategy of an active clamp three-tube push-pull full-bridge bidirectional DC-DC converter according to claim 1, characterized in that the transmission power when the circuit is operated in forward and reverse directions can be obtained respectively:
forward direction:
and (3) reversing:
wherein the power reference is:
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