CN101431297A - Synchronous rectifier - Google Patents
Synchronous rectifier Download PDFInfo
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- CN101431297A CN101431297A CNA2008102194684A CN200810219468A CN101431297A CN 101431297 A CN101431297 A CN 101431297A CN A2008102194684 A CNA2008102194684 A CN A2008102194684A CN 200810219468 A CN200810219468 A CN 200810219468A CN 101431297 A CN101431297 A CN 101431297A
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Abstract
The invention relates to a switching power field, which particularly relates to a circuit used for driving N channel MOSFETs that are used for replacing rectifier diodes at the secondary side of a switching power high-frequency transformer to realize synchronous rectification. The synchronous rectification circuit comprises a signal detecting circuit module, a control circuit module, an auxiliary supply circuit module and a biasing circuit module; the control circuit module comprises a voltage-stabilized circuit, a constant flow source, an invert comparator and an output drive circuit that are connected with each other by signals. The invention has the advantages of simple circuit and broad application range; the circuit of the invention can drive the N channel MOSFETs used for replacing the rectifier diodes to realize synchronous rectification when the switching power has light load, thus reducing the power consumption when in light load; the dead time kept between the breakover time of the N channel MOSFETs and the breakover time of a primary switching tube is reduced to the utmost extent, thus reducing the consumption of the breakover time, improving the efficiency of the power supply and achieving the energy-consumption requirement.
Description
Technical field
The present invention relates to field of switch power, specifically be meant a kind of circuit of the N channel field-effect pipe realization synchronous rectification of the alternative rectifier diode that is used for driving switch power supply high frequency transformer primary side.
Background technology
The technology that realizes Switching Power Supply high frequency transformer secondary side synchronous rectifier at present mainly contains: 1. driven synchronous rectification; 2. electric current self-device synchronous rectification; 3. detect the rising edge and the trailing edge of voltage swing between the D (drain electrode) of synchronous rectification field effect transistor and the S (source electrode) or voltage waveform with special-purpose synchronous rectification integrated circuit, after IC interior is handled, output signal goes to control opening or closing of field effect transistor, realize field effect transistor open or close with the switching mode power supply transformer secondary voltage synchronously.1. mode can only be always square wave in transformer-secondary voltage, and use in the circuit of voltage and current homophase, if transformer-secondary voltage is square wave not necessarily, perhaps voltage and current homophase not, then synchronous rectification can not be realized, for example driven synchronous rectification can not be used in flyback power supply or the resonant mode soft switching power.2. mode can be applied in all types power supply, but the current transformer that needs to detect electric current detects the electric current that flows through secondary synchronization rectification field effect transistor, the patent disclosure of application number 02121622.3 a kind of synchronous rectifier that uses current driving method, but current transformer has 4 windings, the current transformer coiling is difficulty relatively, circuit is more complicated also, the cost height, be unfavorable for producing, when the Switching Power Supply of the different output voltages of design, need to use the current transformer of different umber of turns, manufacture difficulty increases; Mode is 3. except the out of phase power supply of the voltage and current of transformer secondary output can not be used, other can realize synchronous rectification, but there is partly integrated circuit can only be applied in discontinuous mode of operation (DCM pattern) or quasi-resonance pattern (QR pattern), there is partly integrated circuit to work down at discontinuous mode of operation (DCM pattern), quasi-resonance pattern (QR pattern), continuous operation mode (CCM pattern), but the control circuit module more complicated.The static working current when the power supply supply power voltage is 12V of integrated circuit is generally greater than 5mA, and quiescent dissipation might make the quiescent dissipation of whole power supply exceed the requirement of energy conservation standard greater than 60mW.The ON time of the ON time of synchronous rectification field effect transistor and primary switch pipe must be stopped enough Dead Times, the Dead Time that will surpass 500nS, otherwise disturbed easily, cause synchronous rectification to lose efficacy, power supply output is undesired, when the Dead Time that stays oversize, then the parasitic fast recovery diode ON time of field effect transistor will be long, and because of the conduction voltage drop of fast recovery diode generally reaches more than the 1V, so loss is very high, efficient reduces, and the temperature of field effect transistor can be than higher.In addition, the connection of synchronous rectification field effect transistor must can not arbitrarily be changed the position at ad-hoc location, otherwise, do not realize synchronous rectification.
Summary of the invention
The technical problem that the present invention need solve is:
1, when the Switching Power Supply underload, can drive the N channel field-effect pipe that substitutes rectifier diode and realize synchronous rectification, but can not increase too much excess loss, raise the efficiency, the control circuit module output voltage reduces and makes the synchronous rectifier can not conducting when unloaded, utilize the rectification of N channel field-effect body endoparasitism fast recovery diode, make the requirement of standby energy consumption conformance with standard;
2, detect the CCM and the DCM mode of operation of inverse-excitation type switch power-supply with the simplest Method and circuits, be implemented in the synchronous rectification under CCM and the DCM mode of operation;
3, want to reduce to greatest extent the Dead Time that stays between the ON time of the ON time of synchronous rectification N channel field-effect pipe and primary switch pipe, or the Dead Time that stays between two synchronous rectification N channel field-effect pipe ON time of the secondary alternation of Switching Power Supply, loss when reducing conducting, improve the efficient of power supply, reach energy-conservation requirement;
4, the secondary commutation diode of all types of Switching Power Supplies is all wanted and can be substituted by enough circuit of synchronous rectification of the present invention;
5 otherwise be subjected to the position limit of the secondary commutation diode in the original power supply topologies, promptly as long as the rectifier diode that former design is used removes, this novel synchronous rectified circuit is received the corresponding position of rectifier diode just can realize unilateal conduction as rectifier diode, and need not increase other extra circuit, the circuit of synchronous rectification device reduces circuit complexity just as a module device with two link opennings is easy to connect use;
6, when adopting current transformer detection electric current to realize synchronous rectification, current transformer will be oversimplified as far as possible, is easy to make, and saves raw material.
For solving the problems of the technologies described above the technical scheme that the present invention takes be:
The circuit of the N channel field-effect pipe realization synchronous rectification of the alternative rectifier diode that is used for driving switch power supply high frequency transformer primary side in a kind of Switching Power Supply is provided, and this circuit comprises signal deteching circuit module, control circuit module, auxiliary power circuit module and biasing circuit module.
The origin or beginning pin 1 of described Switching Power Supply high frequency transformer secondary winding Ns connects the power supply output negative pole, and terminal leads 2 connects the source S of N raceway groove field effect transistor Q1; Described control circuit module comprises six ports, is respectively Gate, Vcc, Vin, Bias, Vz, Vss, and port Vss is connected with Switching Power Supply high frequency transformer secondary winding Ns terminal leads 2; Described signal deteching circuit module comprises A, B, four ports of C, D, its input port A connects the drain D of Q1, detect and be transported to control circuit module Vin port by output port C after the Q1 drain current is handled, give the Q1 grid G by the output port Gate output control signal of control circuit module at last, realize synchronous rectification; Signal deteching circuit module port D is connected with Switching Power Supply high frequency transformer secondary winding Ns terminal leads 2, and another output port B connects the power supply output cathode; Described auxiliary power circuit module comprises four port E, F, G, H, its output port G is connected with control circuit module Vcc port, for control circuit module provides working power, port H is connected with the biasing circuit module, port F is connected with field effect transistor Q1 drain electrode, and port E is connected with Switching Power Supply high frequency transformer secondary winding Ns terminal leads 2; Described biasing circuit module comprises three port I, K, J, and its output port J connects control circuit module port Bias, and for control circuit module provides bias voltage, port K is connected with control circuit module port Vz.
A kind of concrete scheme is: described control circuit module comprises voltage-stabilized power supply circuit, constant-current source, anti-phase comparator, output driving circuit.Described voltage-stabilized power supply circuit comprises triode Q8, resistance R C, voltage stabilizing didoe ZD1, triode Q8 collector electrode is as the port Vcc of control circuit module, emitter is as the port Vz of control circuit module, base stage connects voltage stabilizing didoe ZD1 negative electrode, described resistance R C is connected between triode Q8 base stage and the collector electrode, and voltage stabilizing didoe ZD1 anode connects control circuit module port Vss; Described constant-current source comprises triode Q6 and Q7, resistance R A and RB, triode Q7 emitter is connected to the Vz port of control circuit module, triode Q7 base stage, Q6 emitter and resistance R A one end are connected, the end of the collector electrode of Q7, the base stage of Q6 and resistance R B is connected, the resistance R A other end connects control circuit module Vz port, the other end of resistance R B connects control circuit module Vss pin, and triode Q6 collector electrode connects triode Q5 collector electrode; Described anti-phase comparator comprises two triode Q4, the Q5 that base stage links to each other, triode Q4 emitter connects control circuit module Vss pin, collector electrode is connected to control circuit module BiaS pin, and triode Q5 collector electrode is connected with base stage, and emitter is as control circuit module Vin port; Described output driving circuit comprises triode Q2, Q3, Q2, Q3 base stage connect the BiaS pin of control circuit module simultaneously, emitter links to each other the back as control circuit module Gate port, triode Q2 collector electrode connects control circuit module Vz port, and the Q3 collector electrode connects the Vss pin of control circuit module.
Another kind of concrete scheme is: described signal deteching circuit module comprises switching diode D4, speed-up capacitor C7, detects resistance R 3, and described switching diode D4 negative electrode, speed-up capacitor C7 one end and detection resistance R 3 one ends are connected as signal deteching circuit module port A; Switching diode D4 anode, the speed-up capacitor C7 other end and detection resistance R 3 other ends are connected as signal deteching circuit module port C, and signal deteching circuit module port B and port A link together, and port D is unsettled.
Described signal deteching circuit module can also realize in the following way: comprise switching diode D5, speed-up capacitor C8, detect resistance R 4, resistance R 5 and capacitor C 9, switching diode D5 anode, speed-up capacitor C8 one end and detection resistance R 4 one ends are connected as the port C of signal deteching circuit module, voltage stabilizing didoe ZD2 negative electrode is connected with switching diode D5 negative electrode, voltage stabilizing didoe ZD2 anode, the speed-up capacitor C8 other end, detect resistance R 4 other ends, capacitor C 9 one ends and resistance R 5 one ends are connected, the R5 other end is as signal deteching circuit module port D, and the C9 other end is as signal deteching circuit module port A; Signal deteching circuit module port A and B link together.
Described signal deteching circuit module can also realize in the following way: described signal deteching circuit module comprises switching diode D6, switching diode D7, switching diode D8, speed-up capacitor C10, absorbs capacitor C 11, detects resistance R 6, demagnetizing resistance R7, current transformer T2, and switching diode D6 anode, speed-up capacitor C10 one end and detection resistance R 6 one ends are connected as signal deteching circuit module port C; 3 pin of the Ns2 winding of switching diode D6 negative electrode, the speed-up capacitor C10 other end, detection resistance R 6 other ends, demagnetizing resistance R7 one end, switching diode D8 negative electrode, absorption capacitor C 11 1 ends, current transformer T2 link together; The other end of demagnetizing resistance R7, switching diode D7 anode are connected, and 4 pin of the Ns2 winding of switching diode D7 negative electrode, switching diode D8 anode, the other end that absorbs capacitor C 11, current transformer T1 are connected as the port D of signal deteching circuit module; 1 pin of the Np2 winding of current transformer T2 is as the port A of signal deteching circuit module; 2 pin of the Np2 winding of current transformer T2 are as signal deteching circuit module port B.
A kind of preferable embodiment is: described auxiliary power circuit module comprises secondary auxiliary power supply winding Nf, rectifier diode D1, the filter capacitor C1 of Switching Power Supply high frequency transformer; The end 4 of described secondary auxiliary power supply winding Nf links to each other as auxiliary power circuit module port H with the anode of rectifier diode D1, the end 3 of secondary auxiliary power supply winding Nf links to each other as auxiliary power circuit module port E with the end of filter capacitor C1, the negative electrode of described rectifier diode D1 links to each other as auxiliary power circuit module port G with the other end of filter capacitor C1, and F is unsettled for the auxiliary power circuit module port.Simultaneously described biasing circuit module adopts the series circuit of current-limiting resistance R1 and coupling capacitance C3, the other end of current-limiting resistance R1 is as biasing circuit module port I, the other end of coupling capacitance C3 is as the port J of biasing circuit module, and K is unsettled for the biasing circuit module port.
Another kind of preferable embodiment is: described auxiliary power circuit module comprises coupling capacitance C6, rectifier diode D2, sustained diode 3, filter capacitor C5, described coupling capacitance C6 one end is as the port F of auxiliary power circuit module, the anode of the other end of coupling capacitance C6 and rectifier diode D2, sustained diode 3 negative electrodes link to each other as auxiliary power circuit module port H, described rectifier diode D2 negative electrode links to each other as auxiliary power circuit module port G with filter capacitor C5 one end, and described sustained diode 3 anodes link to each other as auxiliary power circuit module port E with the filter capacitor C5 other end.Simultaneously described biasing circuit module adopts current-limiting resistance R2, and described current-limiting resistance R2 one end is as biasing circuit module port J, and the R2 other end is as biasing circuit module port K, and I is unsettled for the biasing circuit module port.
With respect to prior art, beneficial effect of the present invention is: described circuit of synchronous rectification applied range, use flexibly, conveniently, promptly the secondary commutation diode of all types of Switching Power Supplies all can substitute by enough circuit of synchronous rectification, not influenced by link position; The operating rate of control circuit module is fast in the described circuit of synchronous rectification, and control can not produce very big delay, and Dead Time is short, the power-efficient height, and quiescent dissipation is little; Circuit of the present invention is succinct simultaneously, is easy to realize.
Description of drawings
Fig. 1 is that the present invention forms the structural principle schematic block diagram;
Fig. 2 is execution mode one schematic diagram of auxiliary power circuit module of the present invention and biasing circuit module;
Fig. 3 is execution mode two schematic diagrams of auxiliary power circuit module of the present invention and biasing circuit module;
Fig. 4 is the schematic diagram of signal deteching circuit module execution mode one of the present invention;
Fig. 5 is the schematic diagram of signal deteching circuit module execution mode two of the present invention;
Fig. 6 is the schematic diagram of signal deteching circuit module execution mode three of the present invention;
Fig. 7 is control circuit module embodiment circuit theory diagrams of the present invention;
Fig. 8 is that the present invention's equivalence is the connection diagram with diode of unilateal conduction characteristic;
Fig. 9 (a) is that the present invention is operated in flyback power supply DCM pattern field effect transistor of following time Q1 drain electrode, voltage between source electrodes V
DSWaveform;
Fig. 9 (b) is the Gate port driver waveform that the present invention is operated in flyback power supply DCM pattern control circuit module of following time;
Figure 10 (a) is that the present invention is operated in V under the flyback power supply CCM pattern
DSVoltage waveform;
Figure 10 (b) is that the present invention is operated in Gate port driver waveform under the flyback power supply CCM pattern;
Figure 11 (a) is the present invention V under the flyback power supply DCM pattern that increases after differential circuit detects
DSVoltage waveform;
Figure 11 (b) is the present invention's Gate port driver waveform under the flyback power supply DCM pattern that increases after differential circuit detects;
Figure 12 (a) is the present invention V under the flyback power supply CCM pattern that increases after differential circuit detects
DSVoltage waveform;
Figure 12 (b) is the present invention's Gate port driver waveform under the flyback power supply CCM pattern that increases after differential circuit detects;
Figure 13 (a) is V under the flyback power supply DCM pattern of the present invention after the belt current instrument transformer detects
DSVoltage waveform;
Figure 13 (b) is the Ns2 winding waveform of current transformer T2 under the flyback power supply DCM pattern of the present invention after the belt current instrument transformer detects;
Figure 13 (c) is a Gate port driver waveform under the flyback power supply DCM pattern of the present invention after the belt current instrument transformer detects.
Embodiment
For the ease of those skilled in the art's understanding, structural principle of the present invention is described in further detail below in conjunction with the embodiment accompanying drawing:
Shown in accompanying drawing 1, the N channel field-effect pipe that is used to drive the alternative rectifier diode of high frequency transformer primary side in the Switching Power Supply of the present invention realizes that the circuit of synchronous rectification comprises signal deteching circuit module, control circuit module, auxiliary power circuit module and biasing circuit module.
The operation principle of described novel synchronous rectified circuit arrangement is: when the source S pin voltage of synchronous rectification N channel field-effect pipe Q1 is higher than drain D voltage, the endobiosis fast recovery diode of field effect transistor Q1 begins conducting, field effect transistor Q1 drain D voltage is negative voltage with respect to field effect transistor Q1 source S voltage, field effect transistor Q1 drain D, the difference of voltage is exactly that the conducting voltage of field effect transistor Q1 endobiosis fast recovery diode is fallen or the conducting voltage of field effect transistor Q1 is fallen between source S, the signal deteching circuit module detects this negative voltage, be input to the Vin port of control circuit module, this negative voltage is lower than the in-phase end voltage of control circuit module internal inverted comparator, inverter output high level, output port Gate output high level, then the field effect transistor Q1 conducting of control circuit module; When the source S voltage of synchronous rectification N channel field-effect pipe Q1 is lower than drain D voltage, field effect transistor Q1 drain D voltage is positive voltage with respect to source S voltage, this positive voltage is higher than control circuit module internal inverted comparator in-phase end voltage, anti-phase comparator output low level, the output port Gate output low level of control circuit module, then field effect transistor Q1 turn-offs.The turn-on and turn-off of field effect transistor Q1 can be followed field effect transistor Q1 drain D, source S change in voltage and be changed, and have realized synchronous rectification.The auxiliary power circuit module provides power supply for control circuit module, the output voltage of auxiliary power circuit is constant-current source, output driving circuit and the biasing circuit module for power supply of control circuit module inside after the voltage-stabilized power supply circuit voltage stabilizing of control circuit module inside, filter capacitor C2 filtering.
Described auxiliary power circuit module can have two kinds of execution modes.
Execution mode is just like accompanying drawing 2, its operation principle is that the 2 port voltage phase places of secondary winding Ns of 4 ports of secondary auxiliary power supply winding Nf of high frequency transformer T1 and high frequency transformer T1 are identical, when 2 port voltages of secondary winding Ns are timing, 4 port voltages of secondary auxiliary power supply winding Nf also for just, are exported to the control circuit module power supply by port D after rectifier diode D1 rectification, filter capacitor C1 filtering.
When Switching Power Supply output is in zero load or underloading, the primary switch pipe duty ratio of Switching Power Supply is very little, the energy that the secondary auxiliary power supply winding Nf of high frequency transformer T1 is obtained is very little, the internal resistance of this part energy Be Controlled circuit module will consume, make that auxiliary power circuit module output voltage is very low, the output voltage of the port Gate of control circuit module is also just very low, deficiency is so that field effect transistor Q1 conducting, at this moment, just the conducting of field effect transistor Q1 endobiosis fast recovery diode realizes rectification, because of the operating current of control circuit module smaller, under this pattern, the energy that whole circuit of synchronous rectification consumes is also smaller, can ignore substantially, so the present invention has lower quiescent dissipation.Increase along with load, the primary switch pipe duty ratio of Switching Power Supply increases gradually, the energy that the secondary auxiliary power supply winding Nf of high frequency transformer T1 is obtained is also more and more, auxiliary power circuit module output voltage is more and more higher, gives control circuit module inner other circuit supplies after the voltage stabilizing of control circuit module interior voltage-stabilized power supply circuit, filter capacitor C2 filtering.
When switch power supply no-load or underloading, primary switch pipe duty ratio is very little, it is very little to flow through coupling capacitance C6 electric current, makes that auxiliary power circuit module output voltage is very low, and the output voltage of the port Gate of control circuit module is also very low, deficiency is so that field effect transistor Q1 conducting, at this moment, just the conducting of field effect transistor Q1 endobiosis fast recovery diode realizes rectification, with execution mode one, the energy of total consumption of the present invention is smaller, can ignore substantially; Increase along with load, the primary switch pipe duty ratio of Switching Power Supply increases gradually, flowing through coupling capacitance C6 electric current increases gradually, auxiliary power circuit module output voltage is more and more higher, gives control circuit module inner other circuit supplies after the voltage stabilizing of control circuit module interior voltage-stabilized power supply circuit, filter capacitor C2 filtering.
Described biasing circuit module also has two kinds of execution modes.
Described biasing circuit module execution mode one also as shown in Figure 2, its operation principle is: when 2 ports of secondary winding Ns are timing, 4 ports of secondary auxiliary power supply winding Nf are also for just, after biasing circuit inside modules current-limiting resistance R1, the coupling capacitance C3 current limliting of connecting, be coupled to the BiaS pin of control circuit module with R1, for the output driving circuit of control circuit module provides forward bias voltage, the output driving circuit of control circuit module output forward voltage drives field effect transistor Q1 conducting; When the port 2 of secondary winding Ns when negative, 4 ports of secondary auxiliary power supply winding Nf are also for negative, behind current-limiting resistance R1 and coupling capacitance C3 and the output driving circuit of control circuit module the electric charge that the grid G port of field effect transistor Q1 stores is taken away, turn-off field effect transistor Q1.
It is because the output driving circuit of control circuit module has adopted the emitter-base bandgap grading output buffer that biasing circuit module execution mode one and auxiliary power circuit module execution mode 1 are used, during work, the output driving circuit of biasing circuit module and control circuit module all can have pressure drop, loss will increase, the auxiliary electric power supply utilance is just low, influential to efficient, under auxiliary power supply winding situation, provide forward bias voltage from 4 ports of auxiliary power supply winding Nf for the emitter-base bandgap grading output buffer of the output driving circuit of control circuit module, can make the NPN triode Q2 of emitter-base bandgap grading output buffer enter saturation condition, improve output voltage to greatest extent, can reduce the conducting resistance of field effect transistor Q1, reduce the loss of control circuit module, raise the efficiency.
Biasing circuit module execution mode two as shown in Figure 3, its operation principle is: the direct voltage of the Vz port of control circuit module provides positive dc offset voltage through current-limiting resistance R2 for the output driving circuit of control circuit module, go to drive field effect transistor Q1 conducting, and the shutoff of field effect transistor Q1 is controlled by the anti-phase comparator of control circuit module.The benefit of this mode is can be without the auxiliary power supply winding, circuit of synchronous rectification of the present invention just can not be subjected to the restriction of link position, be not subjected to the restriction of output voltage height, really accomplish in all switch power supply secondaries, to substitute fully diode and realized rectification function, circuit is succinct, and wiring is simple.
Described control circuit module comprises voltage-stabilized power supply circuit, constant-current source, anti-phase comparator, output driving circuit shown in accompanying drawing 1,2,3.
The side circuit schematic diagram of described control circuit module as shown in Figure 7, its operation principle is: the direct voltage of the Vcc port input of control circuit module is behind voltage-stabilized power supply circuit, after the control circuit module inter-process,, be the biasing circuit module for power supply of constant-current source, output driving circuit, outside by the stable voltage of Vz port output.Constant-current source output constant current flows to base stage and the collector electrode of NPN triode Q5, except that a small part offers the base stage of NPN triode Q4, most of Vin port from control circuit module flows out, grounded emitter current potential because of Q4, the base stage of Q4 and Q5 is connected together, and the base stage of Q5 and collector electrode are connected together, Q5 resembles a diode, therefore, the input Vin port of the control circuit module that the emitter of Q5 connects just becomes virtual earth, what the Vin port of control circuit module connected is the switching diode of signal deteching circuit module, low capacity speed-up capacitor and detection resistance, therefore at switching diode, the parallel network two-port of speed-up capacitor and detection resistance produces substantially invariable voltage, when the input port A of signal deteching circuit module change in voltage, the Vin port of control circuit module is just followed variation synchronously, when the input port A of signal deteching circuit voltage when negative, the Vin port of control circuit module is just for negative, through Q4, behind the anti-phase comparator that Q5 constitutes, Q4 exports high level, and Q2 and Q3 constitute output driving circuit output high level and drive field effect transistor Q1 conducting; When the input port A of testing circuit voltage is timing, the port Vin of control circuit module is just for just, behind the anti-phase comparator that Q4, Q5 constitute, and the Q4 output low level, Q2 and Q3 constitute output driving circuit output low level shutoff field effect transistor Q1.
Described signal deteching circuit module has three kinds of execution modes.
Described signal deteching circuit module execution mode one as shown in Figure 4, its operation principle is in conjunction with the accompanying drawings 1, accompanying drawing 9 and accompanying drawing 10 illustrate that accompanying drawing 9 is field effect transistor drain electrode, voltage between source electrodes V under the inverse-excitation type switch power-supply DCM pattern
DSWaveform and control circuit module Gate port driver waveform, in accompanying drawing 9, from 0 to T1 constantly, elementary switching tube is conducting, turn-off fully at T1 moment primary switch pipe, this moment, 2 port voltages of switch power supply secondary winding Ns were just transferred to by negative, endobiosis two utmost points of synchronous rectification this moment field effect transistor Q1 begin conducting, in T2 conducting fully constantly, conduction voltage drop is V3, V3 with respect to the level of the source S of field effect transistor Q1 is-V3, this-V3 voltage drags down the Vin port voltage of control circuit module fast by the switching diode D4 and the speed-up capacitor C7 of synchronous rectification signal testing circuit module, through control circuit module anti-phase comparator and output driving circuit after export high level, drive field effect transistor Q1 in T3 conducting constantly, the T2 moment and T3 are the time that the voltage waveform of the output driving Gate port of control circuit module rises to field effect transistor Q1 conducting threshold values VG constantly, and the Q1 conduction voltage drop is V2, and V2 with respect to the level of the source S of field effect transistor Q1 is-V2; When the switch transformer storage power exhausts soon, the voltage of the relative source S of drain D of field effect transistor Q1 begins to rise at this moment, when rise to-during V1, behind the speed-up capacitor C7 and 3 detections of detection resistance R of synchronous rectification signal testing circuit module, because of the voltage of R3 two-port is constant, this constant voltage equals the constant-current source output current and detects the product of resistance, therefore, the Vin port voltage of control circuit module is raised fast, output low level behind the anti-phase comparator of control circuit module and output driving circuit, turn-off field effect transistor Q1 constantly at T4,-V1 be provided with must 0V and-set between the V2, otherwise, ringing waveform when being subjected to the DCM pattern is easily disturbed and is made work undesired, ringing waveform be T5 constantly and the waveform .T5 of T6 between constantly be that 2 port voltages of transformer secondary output winding Ns are by just changeing the negative moment constantly, T6 is the moment that the primary switch pipe begins conducting constantly, T5 constantly before, must turn-off field effect transistor Q1, otherwise can there be circulation, increase loss, T7 is the time started following one-period constantly.Accompanying drawing 10 is V under the inverse-excitation type switch power-supply CCM pattern
DSVoltage waveform and Gate port driver waveform, under the DCM pattern of 0 to T4 moment operation principle and accompanying drawing 9 is the same, because of under the CCM pattern, ringing waveform can not appear, if make-V1 is set in-V2 and 0V between, the output driving circuit of control circuit module begins to turn-off field effect transistor Q1 in T4 moment output low level, T5 constantly turn-off fully field effect transistor Q1 can guarantee the primary switch pipe begin conducting before individual Dead Time is arranged, be T5 and the T6 time between the moment, the T6 moment and the time of T7 between the moment are the time that the primary switch pipe begins conducting.
Described synchronous rectification signal testing circuit module execution mode two as shown in Figure 5, operation principle in conjunction with the accompanying drawings 11 and accompanying drawing 12 illustrate.In accompanying drawing 11 and accompanying drawing 12, after adding the resistance R 5 and capacitor C 9 of differential circuit, (V2) voltage is approximately equal to output voltage to 0V-,-V3 and-ring spike between the V2 is eliminated, simultaneously, when detecting between field effect transistor Q1 drain D and the source S voltage, it no longer has been the conduction voltage drop of field effect transistor Q1, but be approximately equal to output voltage, thereby increased detection range, increased detecting reliability, the voltage stabilizing value of voltage stabilizing didoe ZD2 is approximately equal to output voltage, and the voltage stabilizing value of ZD2 adds that the forward voltage drop of diode D5 is used for detecting minimum voltage-V3 between field effect transistor Q1 drain D and the source S, speed-up capacitor C8 is used to quicken the conducting of voltage stabilizing didoe ZD2 and diode D5, detect resistance R 4 and be used for detection-V1 ,-V1 is arranged on close-V2 as far as possible, and the value of R4 is approximately equal to the output current of switch power source output voltage divided by constant-current source.Except that above difference, the operating state in each moment in accompanying drawing 11 and accompanying drawing 12 and the operating state of signal deteching circuit module execution mode 1 are similar.
Described synchronous rectification signal testing circuit module execution mode three as shown in Figure 6, operation principle 13 is described as follows in conjunction with the accompanying drawings, the V between field effect transistor Q1 drain D and the source S
DSVoltage waveform, the Gate port driver waveform of the secondary winding Ns2 voltage waveform of current transformer T2 and control circuit module as shown in Figure 13, the electric current that flows through field effect transistor Q1 drain D and the source S elementary winding Np2 of current transformer T2 that flows through, the voltage waveform of 4 pin of the relative secondary winding Ns2 of 3 pin that inducts at the secondary winding Ns2 of current transformer T2 as shown in Figure 13, from 0 to T1 constantly, elementary switching tube is conducting, turn-off fully at T1 elementary switching tube of the moment, this moment, 2 port voltages of switch power supply secondary winding Ns were just transferred to by negative, the endobiosis diode of synchronous rectification field effect transistor Q1 begins conducting, in T2 conducting fully constantly, the flow through elementary winding Np2 of current transformer T2 of electric current, in the secondary winding Ns2 of current transformer T2, induce 4 pin for just, 3 pin are negative voltage, through switching diode D8 clamper, after absorbing capacitor C 11 absorption clutters, as detected voltage-V6, the voltage that opens that surpasses switching diode D6 as-V6, then D6 begins conducting, because the acceleration of speed-up capacitor C10 is arranged, therefore, the quick conducting of diode D6, the Vin port voltage of control circuit module is dragged down, the anti-phase comparator output high level of control circuit module, the Gate port output high level of control circuit module drives field effect transistor Q1 in T3 conducting constantly; At T4 constantly, the electrorheological of elementary winding Np2 of current transformer T2 of flowing through begins to reduce, in the secondary winding Ns2 of current transformer T2, induce 4 pin for negative, 3 pin are positive voltage, after switching diode D7 rectification, be added in demagnetizing resistance R7 two-port, T2 is consumed to the magnetic energy that T4 is stored among the current transformer T2 constantly, magnetic core is resetted.After absorbing capacitor C 11 absorption clutters, absorb capacitor C 11 two-port ceiling voltages and be V4, rise to the process of V4 from-V6 at voltage, when voltage is higher than by detecting voltage-V5 that resistance R 6 is provided with,-V5 the value of setting is approaching-V6, the Vin port voltage of control circuit module is elevated, the anti-phase comparator output low level of control circuit module, the Gate port output low level of control circuit module drives field effect transistor Q1 and begins constantly to turn-off at T4, turn-off fully constantly at T5, be carved into T6 constantly when T5, field effect transistor Q1 no current flows through, and has only still conducting of fast recovery diode in the field effect transistor Q1 body this moment, fast recovery diode ends at T6 constantly in the field effect transistor Q1 body, the T6 moment-T7 is primary switch pipe ON time constantly, and T7 repeats following one-period after the moment.Demagnetizing resistance R7 has the effect of the Dead Time of the Gate port driver waveform trailing edge of adjusting control circuit module.When the resistance value ratio of demagnetizing resistance R7 hour, because of the current transformer energy storage less, at T4 constantly, in the process that electric current sharply reduces, switching diode D7 conduction ratio is very fast, the voltage of relative 4 pin of 3 pin of the secondary winding Ns2 of current transformer T2 rises to the forward voltage of switching diode D7 very soon, by diode D7 clamper, rise at the voltage of relative 4 pin of 3 pin of Ns2 surpass-during V5, control circuit module is with regard to output low level, close port synchronous rectification field effect transistor Q1, T5 is that 2 port voltages of transformer secondary output winding Ns are by just changeing the negative moment constantly, be the Dead Time of the Gate port driver waveform trailing edge of control circuit module to T5 interval constantly at T4, this time is long; When the resistance value ratio of demagnetizing resistance R7 is big, switching diode D7 conducting is slow, the voltage of relative 4 pin of 3 pin of the secondary winding Ns2 of current transformer T2 slowly rises, through postponing after a while, reach-during V5, just begin to turn-off synchronous rectification field effect transistor Q1, it is shorter to be carved into T5 interval constantly during T4, and promptly the Dead Time of the Gate port driver waveform trailing edge of control circuit module is shorter.
In the described signal deteching circuit module execution mode three is the Current Transformer sensed current signal, so signal deteching circuit module execution mode three is the same in the DCM of Switching Power Supply pattern with operation principle under the CCM pattern.
In sum, the present invention has applied range, uses flexibly, characteristics easily, and can make Switching Power Supply have higher efficient, less quiescent dissipation.
Need to prove; the above execution mode only is the preferable embodiment of the present invention; it can not be interpreted as limiting the scope of the invention, conceive under the prerequisite not breaking away from the present invention that any impartial the variation with modifying all belonged to protection scope of the present invention to the present invention does.
Claims (12)
1, a kind of circuit of synchronous rectification, the N channel field-effect pipe that is used for the alternative rectifier diode of driving switch power supply high frequency transformer primary side is realized synchronous rectification, this circuit comprises signal deteching circuit module, control circuit module, auxiliary power circuit module and biasing circuit module, the origin or beginning pin 1 of described Switching Power Supply high frequency transformer secondary winding Ns connects the power supply output negative pole, terminal leads 2 connects the source S of N raceway groove field effect transistor Q1, it is characterized in that:
Described control circuit module comprises six ports, is respectively Gate, Vcc, Vin, Bias, Vz, Vss, and port Vss is connected with Switching Power Supply high frequency transformer secondary winding Ns terminal leads 2;
Described signal deteching circuit module comprises A, B, four ports of C, D, its input port A connects the drain D of Q1, detect and be transported to control circuit module Vin port by output port C after the Q1 drain current is handled, give the Q1 grid G by the output port Gate output control signal of control circuit module at last, realize synchronous rectification; Signal deteching circuit module port D is connected with Switching Power Supply high frequency transformer secondary winding Ns terminal leads 2, and another output port B connects the power supply output cathode;
Described auxiliary power circuit module comprises four port E, F, G, H, its output port G is connected with control circuit module Vcc port, for control circuit module provides working power, port H is connected with the biasing circuit module, port F is connected with field effect transistor Q1 drain electrode, and port E is connected with Switching Power Supply high frequency transformer secondary winding Ns terminal leads 2;
Described biasing circuit module comprises three port I, K, J, and its output port J connects control circuit module port Bias, and for control circuit module provides bias voltage, port K is connected with control circuit module port Vz.
2, circuit of synchronous rectification according to claim 1 is characterized in that: signal connected between described control circuit module comprised mutually voltage-stabilized power supply circuit, constant-current source, anti-phase comparator, output driving circuit.
3, circuit of synchronous rectification according to claim 2, it is characterized in that: described voltage-stabilized power supply circuit comprises triode Q8, resistance R C, voltage stabilizing didoe ZD1, triode Q8 collector electrode is as the port Vcc of control circuit module, emitter is as the port Vz of control circuit module, base stage connects voltage stabilizing didoe ZD1 negative electrode, described resistance R C is connected between triode Q8 base stage and the collector electrode, and voltage stabilizing didoe ZD1 anode connects control-circuit module port Vss; Described constant-current source comprises triode Q6 and Q7, resistance R A and RB, triode Q7 emitter is connected to the Vz port of control circuit module, triode Q7 base stage, Q6 emitter and resistance R A one end are connected, the end of the collector electrode of Q7, the base stage of Q6 and resistance R B is connected, the resistance R A other end connects control circuit module Vz port, the other end of resistance R B connects control circuit module Vss pin, and triode Q6 collector electrode connects triode Q5 collector electrode; Described anti-phase comparator comprises two triode Q4, the Q5 that base stage links to each other, triode Q4 emitter connects control circuit module Vss pin, collector electrode is connected to control circuit module BiaS pin, and triode Q5 collector electrode is connected with base stage, and emitter is as control circuit module Vin port; Described output driving circuit comprises triode Q2, Q3, Q2, Q3 base stage connect the BiaS pin of control circuit module simultaneously, emitter links to each other the back as control circuit module Gate port, triode Q2 collector electrode connects control circuit module Vz port, and the Q3 collector electrode connects the Vss pin of control circuit module.
4, circuit of synchronous rectification according to claim 1, it is characterized in that: described signal deteching circuit module comprises switching diode D4, speed-up capacitor C7, detects resistance R 3, and described switching diode D4 negative electrode, speed-up capacitor C7 one end and detection resistance R 3 one ends are connected as signal deteching circuit module port A; Switching diode D4 anode, the speed-up capacitor C7 other end and detection resistance R 3 other ends are connected as signal deteching circuit module port C, and signal deteching circuit module port B and port A link together, and port D is unsettled.
5, circuit of synchronous rectification according to claim 1, it is characterized in that: described signal deteching circuit module comprises switching diode D5, speed-up capacitor C8, detect resistance R 4, resistance R 5 and capacitor C 9, switching diode D5 anode, speed-up capacitor C8 one end and detection resistance R 4 one ends are connected as the port C of signal deteching circuit module, voltage stabilizing didoe ZD2 negative electrode is connected with switching diode D5 negative electrode, voltage stabilizing didoe ZD2 anode, the speed-up capacitor C8 other end, detect resistance R 4 other ends, capacitor C 9 one ends and resistance R 5 one ends are connected, the R5 other end is as signal deteching circuit module port D, and the C9 other end is as signal deteching circuit module port A; Signal deteching circuit module port A and B link together.
6, circuit of synchronous rectification according to claim 1, it is characterized in that: described signal deteching circuit module comprises switching diode D6, switching diode D7, switching diode D8, speed-up capacitor C10, absorbs capacitor C 11, detects resistance R 6, demagnetizing resistance R7, current transformer T2, and switching diode D6 anode, speed-up capacitor C10 one end and detection resistance R 6 one ends are connected as signal deteching circuit module port C; 3 pin of the Ns2 winding of switching diode D6 negative electrode, the speed-up capacitor C10 other end, detection resistance R 6 other ends, demagnetizing resistance R7 one end, switching diode D8 negative electrode, absorption capacitor C 11 1 ends, current transformer T2 link together; The other end of demagnetizing resistance R7, switching diode D7 anode are connected, and 4 pin of the Ns2 winding of switching diode D7 negative electrode, switching diode D8 anode, the other end that absorbs capacitor C 11, current transformer T1 are connected as the port D of signal deteching circuit module; 1 pin of the Np2 winding of current transformer T2 is as the port A of signal deteching circuit module; 2 pin of the Np2 winding of current transformer T2 are as signal deteching circuit module port B.
7, according to claim 4 or 5 or 6 described circuit of synchronous rectification, it is characterized in that: described auxiliary power circuit module comprises secondary auxiliary power supply winding Nf, rectifier diode D1, the filter capacitor C1 of Switching Power Supply high frequency transformer; The end 4 of described secondary auxiliary power supply winding Nf links to each other as auxiliary power circuit module port H with the anode of rectifier diode D1, the end 3 of secondary auxiliary power supply winding Nf links to each other as auxiliary power circuit module port E with the end of filter capacitor C1, the negative electrode of described rectifier diode D1 links to each other as auxiliary power circuit module port G with the other end of filter capacitor C1, and F is unsettled for the auxiliary power circuit module port.
8, circuit of synchronous rectification according to claim 7, it is characterized in that: described biasing circuit module comprises current-limiting resistance R1 and coupling capacitance C3, described current-limiting resistance R1 one end is as biasing circuit module port I, the current-limiting resistance R1 other end is connected with coupling capacitance C3 one end, the other end of coupling capacitance C3 is as the port J of biasing circuit module, and K is unsettled for the biasing circuit module port.
9, circuit of synchronous rectification according to claim 7, it is characterized in that: described biasing circuit module comprises current-limiting resistance R2, described current-limiting resistance R2 one end is as biasing circuit module port J, and the R2 other end is as biasing circuit module port K, and I is unsettled for the biasing circuit module port.
10, according to claim 4 or 5 or 6 described circuit of synchronous rectification, it is characterized in that: described auxiliary power circuit module comprises coupling capacitance C6, rectifier diode D2, sustained diode 3, filter capacitor C5, described coupling capacitance C6 one end is as the port F of auxiliary power circuit module, the anode of the other end of coupling capacitance C6 and rectifier diode D2, sustained diode 3 negative electrodes link to each other as auxiliary power circuit module port H, described rectifier diode D2 negative electrode links to each other as auxiliary power circuit module port G with filter capacitor C5 one end, and described sustained diode 3 anodes link to each other as auxiliary power circuit module port E with the filter capacitor C5 other end.
11, circuit of synchronous rectification according to claim 10, it is characterized in that: described biasing circuit module comprises current-limiting resistance R1 and coupling capacitance C3, described current-limiting resistance R1 one end is as biasing circuit module port I, the current-limiting resistance R1 other end is connected with coupling capacitance C3 one end, the other end of coupling capacitance C3 is as the port J of biasing circuit module, and K is unsettled for the biasing circuit module port.
12, circuit of synchronous rectification according to claim 10, it is characterized in that: described biasing circuit module comprises current-limiting resistance R2, described current-limiting resistance R2 one end is as biasing circuit module port J, and the R2 other end is as biasing circuit module port K, and I is unsettled for the biasing circuit module port.
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