MXPA99010403A - A subscriber unit and method for use in a wireless communication system - Google Patents

Abstract

A set of individually gain adjusted subscriber channels (402, 404, 411, 415) are formed via the use of a set of orthogonal subchannel codes (Wc, Ws, Wf) having a small number of PN spreading chips per orthogonal waveform period. Data to be transmitted via one of the transmit channels is low code rate error correction encoded and sequence repeated before being modulated with one of the subchannel codes, gain adjusted, and summed with data modulated using the other subchannel codes. The resulting summed data (410, 420) is modulated using a user long code and a pseudorandom spreading code (PN code) and upconverted for transmission. The use of the short orthogonal codes provides interference suppression while still allowing extensive error correction coding and repetition for time diversity to overcome the Raleigh fading commonly experienced in terrestrial wireless systems. The set of sub-channel codes may comprise four Walsh codes, each orthogonal to the remaining codes of the set. The use of four sub-channels is preferred as it allows shorter orthogonal codes to be used, however, the use of a greater number of channels and therefore longer codes is acceptable. Preferably, pilot data is transmitted via a first one of the transmit channels and power control data transmitted via a second transmit channel. The length, or number of chips, in each channel code may be different to further reduce the peak-to-average transmit power for higher rate data transmission.

Description

A SUBSCRIBER UNIT AND METHOD TO BE USED IN A WIRELESS COMMUNICATION SYSTEM BACKGROUND OF THE INVENTION I. Field of the Invention The present invention relates to a subscriber unit and to a method for use in a wireless communication system. II. Description of Related Art Wireless communication systems, including cellular, satellite and point-to-point communication systems, use a wireless link comprised of a modulated radio frequency (RF) signal to transmit data between two systems. The use of a wireless link is desirable for several reasons, including the requirements of increased mobility and reduced infrastructure compared to wired communication systems. A disadvantage of using a wireless link is the limited amount of communication capacity that results from the limited amount of available RF bandwidth. This limited communication capacity is in contrast to cable communication systems where additional capacity can be added when installing additional cable connections. Since the limited nature of the RF bandwidth is recognized, various signal processing techniques have been developed to increase the efficiency with which wireless communication systems utilize the available RF bandwidth. A widely accepted example of such an efficient bandwidth signal processing technique is the IS-95 over the air interface standard and its derivatives such as IS-95-A and ANSI J-STD-008 (collectively referred to herein). forward as the IS-95 standard) promulgated by the Telecommunications Industry Association (TIA) and used basically within cellular telecommunications systems.

The IS-95 standard incorporates multiple access signal modulation techniques by code distribution (CDMA) to conduct multiple communications simultaneously over the same RF bandwidth. When combined with total energy control, driving multiple communications over the same bandwidth increases the total number of calls and other communications that can be conducted in a wireless communication system to, among other things, increase the repeated use of the frequency compared to other wireless telecommunication technologies. In the U.S. Patent No. 4,901,307, entitled "Diffused Spectrum Communication System Using Satellite or Terrestrial Repeaters", and the U.S. Patent. No. 5,103,459, entitled "System and Method for Generating Signal Wave Forms in a CDMA Cell Phone System", both assigned to the assignee of the present invention and incorporated herein by reference, describes the use of CDMA techniques in a multiple access communication system. Figure 1 provides a highly simplified illustration of a cell phone system configured in accordance with the use of the IS-95 standard. During operation, a set of subscriber units lOa-d conducts wireless communication by establishing one or more RF interfaces with one or more base stations 12a-d through the use of RF signals modulated by CDMA. Each RF interface between a base station 12 and a subscriber unit 10 is comprised of a forward link signal transmitted from the base station 12, and a reverse link signal transmitted from the subscriber unit. Generally, a communication is conducted with another user by means of a mobile telephone switching office (MTSO) 14 and the public switched telephone network (PSTN) 16, by using these RF interfaces. The links between the base stations 12, the MTSO 14 and the PSTN 16 are usually formed through wired connections, although the use of additional microwave or RF links is also known. According to IS-95, each subscriber unit 10 transmits user data through a reverse link signal, incoherent, single channel at a maximum data rate of 9.6 or 14.4 kbits / sec, depending on the speed set that is selected from a set of speed sets. An incoherent link is one in which the phase information is not used by the received system. The coherent link is one in which the receiver exploits the knowledge of the carrier signal phase during processing. Typically, the phase information takes the form of a pilot signal, but can also be estimated from the transmitted data. The IS-95 standard invokes a set of sixty-four Walsh codes, each * one of which comprises sixty-four platelets, in order to be used for the forward link. The use of an incoherent, single-channel reverse link signal, having a maximum data transmission rate of 9.6 or 14.4 kbits / sec, as specified by IS-95, is very suitable for a telephone system wireless cellular in which typical communication involves the transmission of digitized voice or slower digital data, such as a facsimile. An incoherent reverse link was selected because, in a system in which up to 80 subscriber units 10 can be communicated with a base station 12 for each assigned 1.2888 MHz of bandwidth, the proportion of the pilot data needed in the transmission from each subscriber unit 10, would substantially increase the degree to which a set of subscriber units 10 interfere with each other. Also, at the data transmission rates of 9.6 or 14.4 kbits / sec, the proportion of the transmission power of any pilot data for the user data and consequently, the interference to the interior of the - Subscriber unit. The use of a single-channel reverse link signal was chosen because the connection of only one type of communication at a time is compatible with the use of cable-connected telephones, the paradigm on which wireless cellular communications are based. current Also, the complexity of single channel processing is less than that associated with processing multiple channels. As digital communications progress, it is anticipated that the demand for wireless data transmission for applications such as interactive file review and video teleconferencing will increase substantially. This increase will transform the way in which the wireless communication systems are used and the conditions under which the associated RF interfaces are conducted. In particular, the data will be transmitted at higher maximum speeds and with a greater variety of possible speeds. Also, a more reliable transmission may be necessary since errors in data transmission are less tolerable than errors in the transmission of audio information. Additionally, the increasing number of data types will create the need to transmit multiple types of data simultaneously. For example, it may be necessary to exchange a data file while maintaining an audio or video interface. Also, as the transmission rate of a subscriber unit increases, the number of subscriber units 10 communicating with a base station 12 per amount of RF bandwidth will decrease, since the higher data transmission rates they will cause the data processing capacity of the base station to be reached with fewer subscriber units 10. In some cases, the current IS-95 reverse link may not be the most suitable for all of these changes. Accordingly, the present invention relates to the proportion of a CDMA interface, of efficient bandwidth, of higher data transmission rate, over which multiple types of communication can be carried out. SUMMARY OF THE INVENTION In one aspect, the invention provides a subscriber unit or other transmitter for use in a wireless communication system, the subscriber unit comprising: plural information information data sources; an encoder for encoding the information data; plural control sources of control data; and a modulator for modulating encoded information data and control data from one or more plural control sources with different respective modulation codes for transmission on a carrier signal, wherein the modulator is arranged to combine the data from encoded information from an information source, with the control data encoded before they are issued for transmission. In another aspect, the invention provides a base station or other receiver for use in a wireless communication system, the base station comprising: a receiver for receiving a carrier signal and removing encoded information data from plural information sources modulated therewith; different respective modulation codes and control data from plural control sources, the one or more control data being modulated with a respective different modulation code and the encoded information data of an information source being combined with the coded control data; a demodulator for demodulating the information data and the control data, coded, from their respective modulation codes, respectively; and a decoder for decoding the encoded information and control data.

In a further aspect, the invention provides a method for transmitting control data, fundamental data, and complementary data from a first subscriber unit in a set of subscriber units to a base station in communication with the set of subscriber units, comprising: a ) Modulate the complementary data with a first Walsh code; b) modulate the fundamental data with a second Walsh code; and c) modulating the control data with a third Walsh code, wherein said first Walsh code is shorter than said second Walsh code and said second Walsh code is shorter than said third Walsh code. In another aspect, the invention provides a method for transmitting data from a subscriber unit for use in a wireless communication system, the method comprising: acquiring information data from plural information sources; encode the information data; acquire control data from plural control sources; and modulating the encoded information data and the control data from one or more of the plural control sources with the different modulation codes, respective for their transmission on a carrier signal, wherein the encoded information data, coming from a source of information, are combined with the encoded control data before they are issued for transmission. According to one embodiment of the invention, a set of subscriber channels adjusted for gain is formed individually, through the use of a set of subchannel orthogonal codes that have a small number of PN broadcast platelets per period of form. of orthogonal wave. The data to be transmitted through one of the transmission channels is coded by correction of the low code error rate and repeated by sequence - before modulating with one of the subchannel codes, adjust for gain and add to the modulated data by using the other subchannel codes. The resulting summed data is modulated by the use of a long user code and a pseudorandom (PN) broadcast code, and they are overconverted for transmission. The use of short orthogonal codes provides for the suppression of inteference while still allowing extensive correction coding and repetition in the diversity of time to overcome the Raleigh fading commonly experienced in terrestrial wireless systems. In the exemplary embodiment of the invention provided, the set of sub-channel codes is comprised of four Walsh codes, each orthogonal to the remaining set and four platelets of duration. The use of a small number (for example, four) of sub-channels is preferred since it allows shorter codes to be used, however, the use of a greater number of channels and consequently of longer codes is consistent with the invention. In another embodiment of the invention, the length or number of platelets in each channel code is different to still reduce - plus peak-to-average transmission power. In a preferred exemplary embodiment of the invention, the pilot data is transmitted through the first of the transmission channels and the energy control data is transmitted through a second transmission channel. The two remaining transmission channels are used to transmit non-specific digital data that includes user data or signaling data, or both. In an exemplary embodiment, one of the two unspecified transmission channels is configured for BPSK modulation and transmission over the quadrature channel. BRIEF DESCRIPTION OF THE DRAWINGS The features, objects and advantages of the present invention will become more apparent from the detailed description set forth below of an embodiment of the invention, when taken in conjunction with the drawings, in which the reference characters similar are identified correspondingly throughout and where: Figure 1 is a block diagram of the cellular telephone system; Figure 2 is a block diagram of a subscriber unit and base station configured in accordance with an exemplary embodiment of the invention; Figure 3 is a block diagram of a BPSK channel encoder and a QPSK channel encoder configured in accordance with the exemplary embodiment of the invention; Figure 4 is a block diagram of a transmission signal processing system, configured in accordance with the exemplary embodiment of the invention; Figure 5 is a block diagram of a reception processing system, configured in accordance with the exemplary embodiment of the invention; Figure 6 is a block diagram of a finger processing system, configured according to an embodiment of the invention; Figure 7 is a block diagram of a BPSK channel decoder and a QPSK channel decoder, configured in accordance with the exemplary embodiment of the invention; and Figure 8 is a block diagram of a transmission signal processing system, configured in accordance with a second exemplary embodiment of the invention; Figure 9 is a block diagram of a finger processing system, configured according to one embodiment of the invention; Figure 10 is a block diagram of a transmission signal processing system, configured according to another embodiment of the invention; Figure 11 is a block diagram of the coding carried out for the fundamental channel when configured in accordance with an embodiment of the invention; Figure 12 is a block diagram of the coding carried out for the fundamental channel when configured in accordance with an embodiment of the invention; Figure 13 is a block diagram of the coding carried out for the complementary channel when configured in accordance with an embodiment of the invention; and Figure 14 is a block diagram of the coding carried out for the control channel when configured in accordance with an embodiment of the invention.

DETAILED DESCRIPTION OF THE PREFERRED MODALITIES In the context of the reverse link transmission portion of a cellular telecommunications system, a novel method and apparatus for high-speed CDMA wireless communication is described. Although the invention may be adapted to be used within the point-to-point muI t reverse link transition of a cellular telephone system, the present invention is equally applicable to forward link transmissions. In addition, many other wireless communication systems will benefit by incorporating the invention, including satellite based wireless communication systems, wireless point-to-point communication systems, and systems that transmit radio frequency signals through the use of co-axial or other broadband cables. Figure 2 is a block diagram of reception and transmission systems, configured as a subscriber unit 100 and a base station 120. A first data set (BPSK data) is received by the channel encoder of BPSK 103, which generates a stream of code symbols configured to carry out the modulation of BPSK that is received by the modulator 104. A second data set (QPSK) is received by the channel encoder of QPSK 102, which generates a stream of symbols code configured to perform the QPSK modulation which is also received by the modulator 104. The modulator 104 also receives power control data and pilot data, which are modulated together with the encoded data of BPSK and QPSK in accordance with multiple code distribution access (CDMA) techniques in order to generate a set of modulation symbols received by the RF processing system 106. The RF processing system 1 06 filters and overconverts the set of modulation symbols to a carrier frequency for transmission to the base station 120 through the use of an antenna 108. Although only the subscriber unit 100 is shown, multiple subscriber units can communicate with the base station 120. Within the base station 120, the RF processing system 122 receives the RF signals transmitted by means of the antenna 121 and performs bandpass filtering, - baseband downconversion and digitization. The demodulator 124 receives the digitized signals and carries out the demodulation according to CDMA techniques in order to produce energy control, selective decision data of BPSK, and QPSK. The BPSK channel decoder 128 decodes the BPSK selective decision data received from the demodulator 124 in order to produce a better estimate of the BPSK data, and the QPSK 126 channel decoder decodes the QPSK selective decision data. received by the demodulator 124 in order to produce a better estimate of the QPSK data. The best estimate of the first and second data sets is then available for further processing or advance to a next destination, and the received energy control data is used, either directly or after decoding, to adjust the energy of the transmission of the forward link channel used to transmit data to the subscriber unit 100. FIG. 3 is a block diagram of the BPSK channel encoder 103 and the QPSK channel encoder 102 when configured in accordance with the exemplary embodiment of the - invention. Within the BPSK 103 channel encoder, the BPSK data is received by the CRC verification total generator 130, which generates a verification total for each 20 ms frame of the first data set. The data frame together with the CRC verification total is received by the final bit generator 132, which attaches final bits comprised of eight logical zeros at the end of each frame to provide a known state at the end of the decoding process. The frame that includes the final bits of code and the CRC verification total, is then received by the convolutional encoder 134, which carries out the convolutional coding at 1/4 speed (R), of constraint length (K) 9, thus generating the code symbols at a speed that is four times the input speed to the encoder (ER). In an alternative, other coding speeds are carried out, including 1/2 speed, but the use of 1/4 speed is preferred due to its optimum complexity-performance characteristics. The block interleaver 136 performs the interleaving of bits in the symbol codes in order to provide time diversity for more reliable transmission in fast fading environments. The resulting interleaved symbols are received by the variable start point repeater 138, which repeats the sequence of interleaved symbols a sufficient number of times NR in order to provide a stream of constant velocity symbols, which corresponds to the emission of frames that have a constant number of symbols. The repetition of the symbol sequence also increases the time diversity of the data to overcome the fading. In the exemplary embodiment, the constant number of symbols is equal to 6,144 symbols for each frame that makes up the symbol rate of 307.2 kilograms per second (ksps). Also, the repeater 138 uses a different starting point, to begin the repetition of each symbol sequence. When the value of NR needed to generate 6,144 symbols per frame is not an integer, the final repetition is only carried out for a portion of the symbol sequence. The resulting set of repeated symbols is received by the BPSK mapper 139, which generates a stream of BPSK code symbols (BPSK) of values +1 and -1 to carry out BPSK modulation. In an alternative, the repeater 138 is placed before the block interleaver 136 so that the block interleaver 136 receives the same number of symbols for each frame. Within the QPSK 102 channel encoder, the QPSK data is received by the CRC 140 verification total generator, which generates a verification total for each 20 ms frame. The frame including the CRC verification total is received by the code 142 final bit generator, which attaches a set of eight final bits of logical zeros to the end of the frame. The frame, which now includes the final code bits and the CRC verification total, is received by the convolutional encoder 144, which carries out the convslutional coding of R = l / 4, K = 9, thereby generating symbols at a speed that is four times the input speed to the encoder (ER). The block interleaver 146 performs the interleaving of bits in the symbols and the resulting interleaved symbols are received by the variable start point repeater 148. The variable start point repeater 148 repeats the sequence of interleaved symbols a sufficient number of times. times NR by using a different starting point within the symbol sequence so that each repetition generates 12,288 symbols for each frame that makes up the code symbol speed of 614.4 kilograms per second (ksps). When NR is not an integer, the final repetition is carried out only for a portion of the symbol sequence. The resulting repeated symbols are received by the mapper 149, which generates a stream of QPSK code symbols configured to perform the QPSK modulation comprised of a QPSK code symbol stream in +1 value phase and - 1 (QPSKi) and a code symbol stream of QPSK of quadrature of phase of values +1 and -1 (QPSKQ) In an alternative, the repeater 148 is placed before the block interleaver 146 so that the block interleaver 146 receives the same number of symbols for each frame. Figure 4 is a block diagram of the modulator 104 of Figure 2, configured in accordance with the exemplary embodiment of the invention. The BPSK symbols from the BPSK 103 channel encoder are each modulated by Walsh code W2 by using a multiplier 150b, and the QPSK symbols? and QPSKQ from the channel encoder of QPSK 102 are each modulated with Walsh W3 code by using multipliers 150c and 154d. The energy control (PC) data is modulated by Walsh code i through the use of the 150a multiplier. The gain setting 152 receives pilot data (PILOT), which preferably is comprised of the logic level associated with the positive voltage, and adjusts the amplitude according to a gain adjustment factor A0. The PILOT signal does not provide any user data but rather provides phase and amplitude information to the base station so that it can coherently demodulate the data contained in the remaining subchannels, and classifies the selective decision emission values for their combination. The gain adjustment 154 adjusts the amplitude of the power control data modulated by Walsh code i according to the gain adjustment factor Ai, and the gain adjustment 156 adjusts the amplitude of the BPSK channel data modulated by Walsh code W2 according to the amplification variable A2. The gain settings 158a and b adjust the amplitude of the QPSK symbols modulated by Walsh code W3, in phase and quadrature phase, respectively, according to the gain adjustment factor A3. The four Walsh codes used in the preferred embodiment of the invention are shown in Table I.

Table I. It will be apparent to a person skilled in the art that the W0 code is not effectively modulation of the whole, which is consistent with the processing of the pilot data shown. The energy control data is modulated with the Wi code, the BPSK data with the W2 code and the QPSK data with the W3 code. Once they are modulated with the appropriate Walsh code, the pilot, the energy control data and the BPSK data are transmitted according to BPSK techniques, and the QPSK data (QPSKi and QPSKQ) according to the techniques of QPSK as described below. It should also be understood that it is not necessary that each orthogonal channel be used and that the use of only three of the four Walsh codes where only one user channel is provided is employed in an alternative embodiment of the invention. The use of short orthogonal codes generates fewer platelets per symbol and therefore allows for more extensive coding and repetition compared to systems that incorporate the use of longer Walsh codes. This more extensive coding and repetition provides protection against Raleigh fading, which is the main source of errors in terrestrial communication systems. The use of other code numbers and code lengths is consistent with the present invention, however, the use of a larger set of longer Walsh codes reduces this enhanced protection against fading. The use of four plate codes is considered optimal because the four channels provide substantial flexibility to the transmission of various types of data, as illustrated below, while also maintaining a code length - short . The analog adder 160 adds the resultant amplitude-modulated modulation symbols of the gain settings 152, 154, 156 and 158a to generate summing modulation symbols 161. The PN, PNS and PNQ broadcast codes are broadcast through of its multiplication with the long code 180, by using multipliers 162a and b. The resulting pseudorandom code provided by the multipliers 162a and 162b is used to modulate the modulation symbols summed 161 and to adjust for gain the square quadrature symbols QPSKQ 163, through a complex multiplication through the use of multiplier 164a-dy and analog adders 166a and b. The resulting in-phase term Xt and quadrature term XQ are then filtered (filtration not shown) and overconverted to the carrier frequency within the RF processing system 106 shown in a highly simplified form by the use of multipliers. 168 and a sine wave in phase and quadrature phase. An overconversion of displacement QPSK could also be used in an alternative embodiment of the invention. The resulting phase overcurrent and quadrature signals are summed by the use of the analog adder 170 and amplified by the main amplifier 172 according to the main gain setting AM to generate the signal s (t) which is transmitted to the base station 120. In the preferred embodiment of the invention, the signal is broadcast and filtered at a bandwidth of 1.2288 MHz to remain compatible with the bandwidth of the existing CDMA channels. By providing multiple orthogonal channels on which data can be transmitted, as well as by the use of variable speed repeaters that reduce the amount of NR repetition carried out in response to high data transmission rates of input, the system and method for Transmission signal processing, described above, allows a single subscriber unit or other transmission system to transmit data at a variety of data rates. In particular, by decreasing the repetition rate NR carried out by the variable start point repeaters 138 or 148 of FIG. 3, an encoder input speed - increasingly higher ER can be maintained. In an alternative embodiment of the invention, a convolutional coding at 1/2 speed is carried out with the repetition rate NR increased by two. Tables II and III show, respectively, a set of encoder speeds eg ERs supported by various NR repetition rates and R encoding rates equal to 1/4 and 1/2 for the BPSK channel and the QPSK channel.

Table II. BPSK channel - Table III QPSK Channel Tables II and III show that by adjusting the number of sequence repetitions NR, a wide variety of data transmission rates can be supported, including high data transmission rates, since the input speed to the ER encoder corresponds to the data transmission rate minus a constant required for CRC transmission, final code bits and any other higher information. As also shown in Tables II and III, the QPSK modulation can also be used to increase the data transmission rate. At the speeds that are expected to be commonly used, labels such as "High Speed-72" and "High Speed-32" are provided. Those speeds noted as High Speed-72. High Speed-64 and High Speed-32 have traffic speeds of 72, 64 and 32 kbps, respectively, plus multiplexing in signaling and other control data with speeds of 3.6, 5.2 and 5.2 kbps, respectively. The RS2 Total Speed and RS2 Total Speed speeds correspond to speeds used in communication systems that comply with IS-95 and, therefore, are also expected to receive substantial use for compatibility purposes. The zero speed is the transmission of a single bit and is used to indicate a frame erasure, which is also part of the IS-95 standard. The data transmission speed can also be increased by simultaneously transmitting data over two or more of the multiple orthogonal channels, carried out in addition to, or instead of, increasing the transmission rate through the reduction of the speed of the transmission. repeat NR. For example, a multiplexer (not shown) could divide a single data source into multiple data sources by being transmitted over multiple sub-data channels. In this way, the total transmission speed can be increased either through the transmission on a particular channel at higher speeds, or of the multiple transmission carried out simultaneously on multiple channels, or both, until the capacity is exceeded. of signal processing of the receiver system and the error rate becomes unacceptable or the maximum transmission power of the power of the transmission system is reached. The multi-channel ratio also improves flexibility in the transmission of different types of data. For example, the BPSK channel can be designated for the voice information and the QPSK channel can be designated for the transmission of digital data. This modality could be more generalized by designating a channel for the transmission of time-sensitive data, such as voice, at a lower data transmission rate, and by designating the other channel for the - - transmission of data less sensitive to time, such as digital files. In this modality, intercalation could be carried out in larger blocks for less time-sensitive data in order to further increase the time diversity. In another embodiment of the invention, the BPSK channel carries out the primary data transmission and the QPSK channel carries out the overflow transmission. The use of orthogonal Walsh codes eliminates or substantially reduces any interference between the set of channels transmitted from a subscriber unit and thus minimizes the transmission energy necessary for its successful reception at the base station. In order to increase the processing capacity in the reception system and thereby increase the degree to which the highest transmission capacity of the subscriber unit can be used, the pilot data is also transmitted through one of the orthogonal channels. By using the pilot data, coherent processing can be carried out in the reception system when determining and removing the phase shift of the link signal - reverse. Also, the pilot data can be used to optimally weight the multipath signals received with different time delays before being combined in an incidence receiver. Once the phase shift is removed and the multipath signals are appropriately weighted, the multipath signals can be combined, decreasing the energy at which the reverse link signal must be received for proper processing. This decrease in the required reception energy allows higher transmission rates to be processed successfully or, conversely, the interference between a set of reverse link signals is decreased. Although some additional transmission energy is necessary for the transmission of the pilot signal, in the context of higher transmission rates, the ratio of the energy of the pilot channel to the energy of the reverse link signal is substantially lower than that associated with systems Cellular digital voice data transmission with lower data transmission speed. Thus, within a high data rate CDMA system, the Eb / N0 gains achieved by the use of a coherent reverse link exceed the additional energy needed to transmit pilot data from each subscriber unit. The use of gain settings 152-158, as well as the main amplifier 172, further increases the degree to which the high transmission capacity of the system described above can be used by allowing the transmission system to adapt to the various conditions of the transmission. radio channel, transmission speeds and data types. In particular, the transmission energy of a channel that is necessary for proper reception may change over time and with the changing conditions in a certain way that is independent of the other orthogonal channels. For example, during the initial acquisition of the reverse link signal, it may be necessary to increase the power of the pilot channel in order to facilitate detection and synchronization at the base station. However, once the reverse link signal is acquired, the necessary transmit power of the pilot channel will decrease substantially and will vary depending on various factors, including the speed of movement of the subscriber units. According to the above, the value of the gain adjustment factor A0 would increase during the signal acquisition and would be reduced later during a communication in process. In another example, when information more tolerable to the error is transmitted through the forward link, or the environment in which the forward link transmission takes place is not prone to fading conditions, the gain adjustment factor Ai may be reduced according to the need to transmit energy control data with low decrements of the error rate. Preferably, as long as the power control setting is not necessary, the gain adjustment factor Ai is reduced to zero. In another embodiment of the invention, the ability to adjust for gain each orthogonal channel or the reverse link signal entirely is further exploited by allowing the base station 120 or other receiver system to alter the gain setting of a channel or the completely reverse link signal, through the use of power control commands transmitted through the forward link signal. In particular, the base station can transmit power control information that requires the transmission power of a particular channel or the reverse link signal to be adjusted in its entirety. This is advantageous in many cases, including when two types of data having different sensitivity to error, such as digitized voice and digital data, are transmitted through the BPSK and QPSK channels. In this case, the base station 120 would set different target error rates for the two associated channels. If the actual error rate of a channel exceeds the target error rate, the base station would indicate to the subscribing unit to reduce the gain adjustment of that channel until the actual error rate will reach the target error rate. This would eventually lead to the gain adjustment factor of one channel being increased relative to the other - that is, the gain adjustment factor associated with the data more sensitive to error would be increased in relation to the gain adjustment factor associated with the least sensitive data In other cases, the transmission energy of the reverse link in its entirety may require adjustment due to fading conditions or movement of the subscriber unit 100. In these cases, the Base station 120 can do that through the transmission of a single energy control command. In this way, by allowing the gain of the four orthogonal channels to be adjusted independently, as well as in conjunction with another, the total transmission energy of the reverse link signal can be kept to the minimum necessary for the successful transmission of each type of data, be it pilot data, energy control data, signaling data or different types of user data. In addition, successful transmission can be defined differently for each type of data. The transmission with the minimum amount of energy required allows the largest amount of data to be transmitted to the base station given the finite power transmission capacity of a subscriber unit, and also reduces the interference between the subscriber units. This reduction in interference increases the total communication capacity of the entire CDMA wireless cellular system. The energy control channel used in the reverse link signal allows the subscriber unit to transmit control information of - power to the base station at a variety of speeds, including an 800-bit rate of energy control per second. In the preferred embodiment of the invention, an energy control bit indicates to the base station to increase or decrease the transmission energy of the forward link traffic channel which is used to transmit information to the subscriber unit. Although it is generally useful to have rapid energy control within a CDMA system, this is especially useful in the context of higher data rate communications, which involve data transmission, because digital data is more sensitive errors and high transmission causes substantial amounts of data to be lost during brief fading conditions. Since it is likely that a high-speed reverse link transmission is accompanied by a high-speed forward link transmission, the proportion of a fast transmission of power control over the reverse link further facilitates high-speed communications within CDMA wireless telecommunications systems - In an alternate exemplary embodiment of the invention, a set of input rates to the ER decoder defined by the particular NR is used to transmit a particular data type. That is, the data can be transmitted at an input speed to the maximum encoder ER or to a set of lower decoder input rates ER, with the associated NR, adjusted according to the above. In the preferred implementation of this mode the maximum speeds correspond to the maximum speeds used in the wireless communication system according to IS-95, referred to above with respect to Tables II and III as Total Speed RSl and Total Speed RS2, and each lower speed is approximately half of the next higher speed, creating a set of speeds comprised of a total speed, a half speed, a quarter speed and an eighth speed. Lower data transmission rates are preferably generated by increasing the repetition rate of symbols NR with the value of NR for the set of speeds one and the set of speeds two in a BPSK channel provided in Table IV.

Table IV. RSL and RS2 Velocity Sets in the BPSK Channel The repetition rates for a QPSK channel are twice that of the BPSK channel. According to the exemplary embodiment of the invention, when the data transmission rate of a frame changes with respect to the previous frame, the transmission power of the frame is adjusted according to the change in the transmission speed. That is, when a lower speed frame is transmitted after a higher speed frame, the transmission energy of the transmission channel on which the frame is transmitted is reduced for the lower speed frame in proportion to the speed reduction and vice versa. For example, if the transmission energy of a channel during the transmission of a frame at full speed is transmission energy T, the transmission energy during the subsequent transmission of a frame at half speed is transmission energy T / 2. The reduction of the transmission energy is preferably carried out by reducing the transmission energy by the total duration of the frame, but it can also be carried out by reducing the transmission work factor in such a way as to "eliminate" certain information redundant. In any case, the transmission power settings take place in combination with a closed-cycle power control mechanism by which the transmission energy is further adjusted in response to energy control data transmitted from the base station. Figure 5 is a block diagram of the RF processing system 122 and the demodulator 124 of Figure 2 configured in accordance with the exemplary embodiment of the invention. The multipliers 180a and 180b subvert the signals received from the antenna 121 with a sine wave in phase and a sine wave in quadrature phase, producing reception samples in phase Rt and reception samples in quadrature phase RQ, respectively. It should be understood that the RF processing system 122 is shown in a highly simplified form and that the signals are also filtered and digitized by comparison (not shown) according to widely known techniques. The reception samples Rt and RQ are then applied to finger demodulators 182 within the demodulator 124. Each finger 182 demodulator processes an instance of the reverse link signal transmitted by the subscriber unit 100, if such instance is available, where each instance of the reverse link signal is generated through a multiple path phenomenon. Although three finger demodulators are shown, the use of alternative numbers of finger processors is consistent with the invention, including the use of a single finger 182 demodulator. Each finger 182 demodulator produces a set of selective decision data comprised of energy control data , BPSK data and QPSKi data and QPSKQ data. Each selective decision data set is also adjusted by time within the corresponding finger 182 demodulator, although the time setting may be carried out within the combiner 184 in an alternative embodiment of the invention. The combiner 184 then adds the selective decision data sets received from the finger demodulators 182 in order to produce a single energy control instance, BPSK, selective decision data of QPSKi and QPSKQ. Figure 6 is a block diagram of a finger demodulator 182 of Figure 5 configured in accordance with the exemplary embodiment of the invention. The reception samples Rt and RQ are first adjusted in time by the use of time adjustment 190 according to the amount of delay introduced by the transmission path of the particular instance that the reverse link signal is processed. The long code 200 is mixed with pseudo-random broadcast codes PNS and PNQ by the use of multipliers 201 and the full conjugate of the PS and PNQ broadcast codes modulated by long code, resulting, multiply in a complex manner with the reception samples Rj and RQ adjusted by time by the use of multipliers 202 and analog adders 204, yielding the terms XS and XQ. Three separate instances of the terms Xi and XQ are then demodulated by the use of the Walsh Wir W2 and W3 codes, respectively, and the resulting Walsh demodulated data is summed over four demodulation plates by the use of 4 to 1 analog adders 212. A fourth instance of the Xi and XQ data is added four demodulation platelets by the use of analog adders 208 and then filtered using the pilot filters 214. In the preferred embodiment of the invention, the pilot filter 214 carries out its average over a series of sums carried out by the analog adders 208, but other filtering techniques will be apparent to those skilled in the art. Pilot signals filtered in phase and quadrature phase are used to rotate by phase and classify the demodulated data by Walsh i and W2 code, according to BPSK modulated data through a complex conjugate multiplication by using 216 multipliers and add-ons 217, producing data from BPSK and from - Selective decision energy control. The data modulated by Walsh W3 code is rotated by phase by using the pilot signals filtered in phase and in quadrature phase, according to QPSK modulated data by using multipliers 218 and addiners 220, producing decision QPSK data selective The data modulated by Walsh W2 code rotated by phase, the data modulated by Walsh W3 code and the selective decision data of energy control are available for their combination. In an alternative embodiment of the invention, the coding and decoding is also carried out in the energy control data. In addition to providing phase information, the pilot can also be used within the reception system to facilitate time tracking. The time tracking is carried out by also processing the received data in a previous sample time (before) and a subsequent sample time (after), the current reception sample being processed. In order to determine the time that corresponds more accurately to the actual arrival time, the amplitude of the pilot channel in the previous and posterior sample time can be compared with the amplitude in the current sample time in order to determine which is greater. If the signal at one of the adjacent sample times is greater than the current sample time, synchronization can be adjusted so that the best demodulation results are obtained. Figure 7 is a block diagram of the BPSK channel decoder 128 and the QPSK channel decoder 126 (Figure 2), configured in accordance with the exemplary embodiment of the invention. The BPSK selective decision data from the combiner 184 (Figure 5) is received by the accumulator 240, which stores the first sequence of 6.144 / NR demodulation symbols in the received frame, where NR depends on the transmission speed of the BPSK selective decision data as described above, and adds each subsequent set of 6,144 / NR demodulated symbols contained in the frame with the corresponding accumulated, stored symbols. The block deinterleaver 242 deinterleaves the accumulated selective decision data of the variable start point analog adder 240 and the Viterbi decoder 244 decodes the deinterleaved selective decision data in order to produce inflexible decision data as well as the results of the total check CRC Within the QPSK decoder 126, the selective decision data of QPSKi and QPSKQ from the combiner 184 (FIG. 5) are demuxed in a single selective decision data stream by the demultiplexer 246 and the single selective decision data stream. it is received by the accumulator 248, which accumulates every 6.144 / NR demodulation symbols, where NR depends on the transmission speed of the QPSK data. In block deinterleaver 250 deinterleaves the selective decision data from the variable start point analog adder 248, and the Viterbi decoder 242 decodes the deinterleaved modulation symbols in order to produce inflexible decision data as well as the results of the total check CRC In the alternate exemplary embodiment, described above with respect to Figure 3, in which the repetition of symbols is carried out before interleaving, the accumulators 240 and 248 are placed after the block deinterleavers 242 and 250. In the embodiment of the invention that incorporates the use of speed sets and therefore, in which the speed of a particular frame is not known, multiple decoders are employed, each operating at a different transmission speed and then the frame associated with The transmission rate most likely to have been used is selected based on the results of the CRC verification total. The use of other error verification methods is consistent with the practice of the present invention. Figure 8 is a block diagram of the modulator 104 (figure 2), configured in an alternative embodiment of the invention in which a single BPSK data channel is used. The pilot data is adjusted by gain by adjusting gain 452 according to the gain adjustment factor A0. The energy control data is modulated with the Walsh code Wi by the multiplier 150a and adjusted by gain 454 according to the gain adjustment factor Ai. The pilot adjusted data by gain and the energy control data are summed by the analog adder 460, producing summed data 461. The BPSK data is modulated with the Walsh code W2 - by multiplier 150b and then adjusted by gain by using gain adjustment 456 according to the gain adjustment factor A2. The pseudorandom in-phase diffusion code (PNi) and the phase quadrature pseudo-random diffusion code (PNQ) are both modulated with long codes 480. The PNS and PNQ codes modulated by resulting long code multiply in a complex manner with the summed data 461 and BPSK data adjusted for gain from gain adjustment 456 by using 464a-d multipliers and analog adders 466a-b, yielding the terms Xi and XQ. The terms i and XQ are then overconverted with phase and phase quadrature sine waves by the use of multipliers 468 and the resulting over converted signals are summed by the analog adders 470, respectively, and amplified by the amplifier 472 in accordance with the amplitude factor AM, generating the signal s (t). The modality shown in figure 8 differs from the other modalities described here since the BPSK data are placed in the channel in - quadrature of phase while the pilot data and energy control data are placed in the in-phase channel. In the prior embodiments of the invention described herein, the BPSK data is placed in the in-phase channel together with the pilot data and the energy control data. The placement of the BPSK data in the phase quadrature channel and the pilot and power control data in the in-phase channel reduces the peak-to-average energy ratio of the reverse link signal, causing the phases of the orthogonal channels that the magnitude of the sum of the two channels varies less in response to the data change. This reduces the peak energy required to maintain a given average energy and thus reduces the proportion of peak-to-average energy characteristic of the reverse link signal. This reduction in the peak-to-average energy ratio decreases the peak energy at which a reverse link signal must be received at the base station in order to sustain a given transmission rate and therefore increases the distance at which it can be located a subscriber unit having a maximum transmit power, starting from the base station, before it is unable to transmit a signal that can be received at the base station with the necessary peak power. This increases the range in which the subscriber unit can successfully conduct the communication at any given data transmission rate or alternatively allows higher data rates to be maintained at a given distance. Fig. 9 is a block diagram of the finger demodulator 182 when configured in accordance with the embodiment of the invention shown in Fig. 8. The reception samples Rx and RQ are adjusted by time by synchronization adjustment 290 and codes of PNi and PNQ are multiplied by the long code 200 by the use of multipliers 201. The reception samples adjusted by time are then multiplied by the complex conjugate of the PNS and PNQ codes by the use of multipliers 302 and analog adders 304, producing the terms Xt and XQ. A first and second instance of the terms Xx and XQ are demodulated by the use of the Walsh Wx code and the Walsh W2 code, by using multipliers 310 and the resulting demodulation symbols are added in sets of four by the use of analog adders 312. A third instance of the terms Xt and XQ is summed over four demodulation symbols by the analog adders 308 in order to generate the pilot reference data. The pilot reference data is filtered by 314 pilot filters and used to rotate by phase and classify the data modulated with Walsh code, summed, by means of the use of multipliers 316 and addiners 320, producing selective decision data of BPSK., and after adding over 384 symbols per 384: 1 of analog adder 322, selective decision energy control data. Figure 10 is a block diagram of a transmission system, configured according to yet another embodiment of the invention. The channel gain 400 adjusts the pilot channel 402 by gain based on the gain variable A0 - The fundamental channel symbols 404 are correlated in values of +1 and -1 by the mapper 405 and each symbol is modulated with Walsh code WF equal to +, +, -, - (where + = +1 and - = -1). The data modulated by WF is adjusted by gain based on the gain variable Ai by gain adjustment 406. The emissions of the gain settings 400 and 406 are summed by the analog adder 408, producing data in phase 410. The symbols of complementary channels 411 are correlated with values + and by means of mapper 412 and each symbol is modulated with a Walsh code Ws equal to +, -. The gain adjustment 414 adjusts the gain of the modulated data Ws. The data of the control channel 415 is correlated with values + and - by the mapper 416. Each symbol is modulated with a Walsh code Wc equal to +, +, +, +, -, -, -, -. The symbols modulated by Wc are adjusted by gain by the gain adjustment 418 based on the gain variable A3 and the output of the gain settings 414 and 418 are summed by the analog adder to produce phase quadrature data 420. it should be apparent that, since the Walsh codes WF and Ws are different lengths and are generated at the same platelet rate, the fundamental channel transmits data symbols at a speed that is half that of the complementary channel. For similar reasons, it should be apparent that the control channel transmits data symbols at half the channel speed -fundamental The data in phase 410 and the quadrature data of phase 420 are multiplied in a complex manner by the diffusion codes PN] -. and PNQ as shown, yielding a term in phase Xt and a term in quadrature of phase XQ. The quadrature term of phase XQ is delayed by half the duration of a PN broadcast code platelet to carry out the displacement QPSK broadcast, and then the term Xt and the term XQ are overconverted according to the RF processing system 106 shown in Figure 4 and described above. By using Walsh WP, Ws and Wc codes that have different lengths as described above, this alternative provides a set of communication channels that have a greater variety of speeds. Additionally, the use of a shorter, two-plate Walsh Ws code for the complementary channel provides an orthogonal complementary channel of higher data transmission rate with a peak-to-average transmission power ratio that is less than that associated with the use of two channels based on Walsh codes of 4 platelets. This further improves the performance of the transmission system since a given amplifier will be able to sustain a higher speed or transmit with a greater range by using the lower peak-to-average transmission energy waveform. The Walsh code assignment scheme described with respect to Figure 10 can also be observed as the Walsh space allocation of eight platelets, according to Table VI.

Table VI In addition to reducing the ratio of peak to average transmission energy, the allocation of eight-platelet Walsh channel sets by using a single shorter Walsh code decreases the complexity of the transmission system. For example, modulation with four Walsh codes of eight platelets and the sum of the results requires additional circuitry and therefore would be more complex. It is further contemplated that the transmission system shown in Figure 10 can operate at different diffusion band amplitudes and consequently with the Walsh codes and diffusion codes generated at various speeds other than 1.2288 Ms / second. In particular, a broadcast bandwidth of 3.6864 MHz is contemplated, with a corresponding Walsh and diffusion code rate of 3.6864 Mplates / second. Figures 11-14 illustrate the decoding carried out for the control, fundamental and complementary channels according to the use of a broadcast bandwidth of 3.6864 MHz. Typically, to adjust the decoding for use with a bandwidth diffusion of 1.2288 MHz, the number of symbol repetitions is reduced. This principle of adjusting the number of symbol repetitions can be applied more generally to increases in the diffusion bandwidth including, for example, the use of an amplitude of - MHz diffusion band. The adjustments made to the coding for a diffusion bandwidth system of 1.2288 MHz other than the reduction in the number of symbol repeats are particularly observed in the description of Figures 11-14. below provided. Figure 11 shows the coding carried out for the four speeds (ie, total, average, one quarter and one eighth of speed) that make up the set of speeds of the IS-95 1 when it is carried out in accordance with a embodiment of the invention. Data is supplied in a 20 ms frame that has the number of bits displayed for each speed, and the total CRC check bits and the final eight bits are aggregated by CRC 500a-d check total generators and the generators of final bits 502a-d. Additionally, convolutional coding at 1/4 speed is carried out for each speed by the convolutional encoders 504a-d, generating four code symbols for each data bit, CRC bit or final bit. The resulting frame of the code symbols is inserted per block by the use of block interleavers 506a-d, generating the indicated number of symbols. For the three lower speeds, the symbols are transmitted repeatedly by means of transmission repeaters 508a-c, as indicated, causing 768 codes to be generated for each frame. The 768 code symbols for each speed are then repeated 24 times by the symbol repeaters 510a-d, generating 18,432 code symbols per frame for each speed. As discussed above, each code symbol in the fundamental channel is modulated with a Walsh WF code of four bits, generated at 3,686,400 platelets per second (3.6864 Mplates / second). In this way, for a time interval of 20 ms (1 / 50th of a second), the number of Walsh and diffusion platelets is 73,728, which corresponds to 4 Walsh platelets for each of the 18,432 symbols. code in the frame. For a system that operates at 1.2288 Platelets / second, the number of symbol repetitions carried out by the symbol repeaters 510a-d is reduced to eight (8). Additionally, the transmit repeater 508b repeats the sequence of symbols in the frame three (3) times, plus 120 of the symbols are transmitted a fourth time, and the transmit repeater 508c repeats the sequence of symbols in the frame six ( 6) times, plus 48 of the symbols are repeated a seventh time. Additionally, a fourth transmission repeater (or fourth transmission repetition stage) is included for the total rate (not shown) that transmits 384 of the symbol sequence contained in the frame a second time. These repeated transmissions provide all 368 data symbols which, when repeated eight times by the symbol repeaters 510a-d, correspond to 6,144 symbols, which is the number of platelets in a frame of 20 ms at 1.2288 Mplates / second. Figure 12 shows the coding carried out for the four speeds that make up the set of speeds of IS-95 2, when it is carried out according to an embodiment of the invention. The data is supplied in frames of 20 ms having the number of bits shown for each speed and a reserve bit is added by the backup bit raters 521 a-d for each speed. The CRC verification bits and the final eight bits also - they are aggregated by the CRC verification totals generators 520a-d and the final bit generators 522a-d. Additionally, convolutional coding at 1/4 speed is carried out for each speed by convolutional encoders 524a-d, generating four code symbols for each data, CRC or final bit. The resulting frame of code symbols is inserted per block by the use of block interleavers 526a-d, generating the indicated number of symbols. For the three lower speeds, the symbols are transmitted repeatedly by transmit repeaters 528a-c as indicated, causing 768 code symbols to be generated for each frame. The 768 code symbols for each speed are then repeated 24 times by symbol repeaters 530a-d, generating 18,432 code symbols per frame for each speed For a system operating at 1.2288 MHz of diffusion bandwidth, the number of repetitions of symbols carried out by the symbol repeaters 530a-d is reduced to four (4). Additionally, the transmit repeater 528a transmits the sequence of symbols - in the frame two (2) times, plus 384 of the symbols are transmitted a third time. The transmit repeater 528b repeats the sequence of symbols in the frame five (5) times, in addition 96 of the symbols are transmitted a sixth time. The transmit repeater 528c repeats the sequence of symbols in the frame ten (10) times, in addition 96 of the symbols are repeated one eleventh time. Additionally, a fourth transmission repeater (or fourth transmission repetition stage) is included for the total speed (not shown), which transmits 384 of the sequence of symbols contained in the frame a second time. All of these repeated transmissions provide 1,536 data symbols which, when repeated four times by the symbol repeaters 530a-d, correspond to 6,144 symbols. Figure 13 illustrates the coding carried out for the complementary channel when carried according to one embodiment of the invention. Data frames are supplied at any of the eleven indicated speeds and the CRC 540 check total generator adds 16 data bits of the total CRC verification. The final bit generator 542 adds 8 bits of encoder end data which results in frames having the known data transmission rates. The convolutional encoder 544 carries out a coding at a quarter speed, of constriction length K = 9, which generates four code symbols for each data, CRC or received final bit, and block interleaver 546 performs the interleaving of blocks in each frame and outputs the number of code symbols shown for each frame according to the size of input frame. The symbol repeater 548 repeats the frames N times, depending on the size of the input frame, as indicated. The coding is shown for an additional twelfth speed, which is carried out in a manner similar to the eleven speeds, with the exception that the coding at half speed is carried out instead of a quarter speed. Additionally, no symbol repetition is performed. Table VII provides a list of frame sizes, encoder input rates, code rates and N symbol repetition factors for various plate velocities that can be applied to Figure 13 to adjust the different plate velocities which corresponds to the diffusion band amplitudes).

Table VII - Figure 14 is a block diagram of the processing carried out for the control channel for a broadcast bandwidth system of 3.6864 MHz. The processing is substantially similar to that associated with other channels, except for the addition of a multiplexer 560 and a repeater of symbols 562, which operate to input non-encoded energy control bits into the stream of code symbols. The energy control bits are generated at a rate of 16 per frame and are repeated 18 times per symbol repeater 562 resulting in 288 energy control bits per frame. The 288 energy control bits are multiplexed in the code symbol frame at a ratio of three energy control bits per encoded data symbol, generating 384 total symbols per frame. The symbol repeater 564 repeats the 384 bits 24 times, generating 9,216 symbols per frame for an effective data transmission rate of 500 Kbi t s / second for the control data and 800 Kbi ts / second for the energy control bits. The preferred processing carried out for a 1.2288 MHz bandwidth system simply reduces the number of symbol repetitions carried out from 24 to 8. In this way, a high speed CDMA wireless communication system has been described. , of multiple channels. The description is provided to allow any person skilled in the art to make or use the present invention. The various modifications to these modalities will be readily apparent to those skilled in the art and the generic principles defined herein may be applied to other modalities without the use of the inventive faculty. In this way, the present invention does not intend to be limited to the modalities shown herein, but to be in accordance with the broadest scope consistent with the principles and novel features set forth herein.

Claims (15)

1. - NOVELTY OF THE INVENTION Having described the present invention, it is considered as a novelty and therefore the property described in the following claims is claimed as property. A subscriber unit or other transmitter for use in a wireless communication system, characterized in that the subscriber unit comprises: plural information sources of information information, - an encoder for encoding the information data; plural control sources of control data; and a modulator for modulating encoded information data and control data from one or more of the plural control sources with the respective different modulation codes for transmission on a carrier signal, wherein the modulator is arranged to combine data from encoded information from an information source with the encoded control data before they are transmitted for transmission.
2. 2. A subscriber unit according to claim 1, characterized in that the control data comprises energy control data and pilot data.
3. 3. A subscriber unit according to claim 2, characterized in that the modulator is operable to modulate the energy control data with a modulation code.
4. 4. A subscriber unit according to any of the preceding claims, characterized in that the modulation codes are Walsh codes.
5. 5. A subscriber unit according to claim 4, characterized in that the Walsh code used to modulate the information data from the first of the information sources is longer than the Walsh code used to modulate the information data from the second one. the sources of information.
6. 6. A subscriber unit according to claim 5, characterized in that the Walsh code used to modulate the encoded control is longer than the Walsh code used to modulate the data information data from the second of the information sources.
7. 7. A subscriber unit according to claim 6, characterized in that the Walsh code used to modulate the encoded control data comprises eight chips, the Walsh code used to modulate the information data from the first of the information sources comprises four chips, and the Walsh code used to modulate the information data from the second of the information sources comprises two chips.
8. 8. A subscriber unit according to any of the preceding claims, characterized in that it further comprises a combiner for combining the modulated data coming from the modulator with each other and with a diffusion code for its transmission on a carrier signal.
9. 9. A subscriber unit according to claim 8, characterized in that it further comprises a transmitter circuit for transmitting the carrier signal containing the modulated, combined, broadcast data.
10. 10. A subscriber unit according to any of the preceding claims, characterized in that the encoder is arranged to perform a low code error correction and a sequence repetition for the information data.
11. 11. A base station or other receiver for use in a wireless communication system, characterized in that the base station comprises: a receiver for receiving a carrier signal and removing from it the coded information data from plural information sources, modulated with different respective modulation codes and control data from plural control sources, modulating the one or more of the control data with the respective different modulation code and with the encoded information data, coming from an information source, combining with the encoded control data, - a demodulator to demodulate the data of * encoded information and control data from their respective modulation codes; and a decoder for decoding the encoded information and control data.
12. 12. A method for transmitting control data, fundamental data and supplementary data from a first subscriber unit in a set of subscriber units to one - base station in communication with the set of subscriber units, characterized in that it comprises: a) modulating the complementary data with a first Walsh code; b) modulate the fundamental data with a second Walsh code; and c) modulating the control data with a third Walsh code, where the first Walsh code is shorter than the second Walsh code and the second Walsh code is shorter than the third Walsh code.
13. The method according to claim 12, characterized in that the first Walsh code is comprised of two chips, the second Walsh code is comprised of four chips and the third Walsh code is comprised of eight chips.
14. 14. The method according to claim 12 or 13, characterized in that it also comprises a pilot channel, wherein the pilot channel is summed with the fundamental data, the complementary data are added with the control data.
15. 15. A method for transmitting data from a subscriber unit for use in a wireless communication system, characterized in that it comprises: acquiring information data from plural information sources; encode the information data; acquire control data from plural control sources; and modulating the encoded information and control data from one or more of the plural control sources with the respective different modulation codes for transmission over a carrier signal, wherein the encoded information data from a source of information are combined with the encoded control data before they are issued for transmission. SUMMARY A set of individually adjusted gain subscriber channels (402, 404, 411, 415) is formed through the use of a set of orthogonal sub-channel codes (Wc, Ws, Wf) that have a small number of chips of PN diffusion by orthogonal waveform period. The data to be transmitted through one of the transmission channels is coded by correction of the low code error rate and repeated by sequence before being modulated with one of the subchannel codes, adjusted for gain and summed with modulated data by means of the use of the other subchannel codes. The resulting summed data (410, 420) are modulated by the use of a long user code and a pseudo-random broadcast code (PN code) and are overconverted for transmission. The use of short orthogonal codes provides suppression of interference while still allowing coding for extensive error correction and repetition in a variety of time to overcome the Raleigh fading commonly experienced in wireless terrestrial systems. The set of sub-channel codes may comprise four Walsh codes, each orthogonal to the remaining codes of the set. The use of four sub-channels is preferred since it allows shorter orthogonal codes to be used, however, the use of a greater number of channels and therefore of longer codes is acceptable. Preferably, the pilot data is transmitted through the first of the transmission channels and the energy control data is transmitted through a second transmission channel. The length, or number of chips in each channel code may be different to further reduce the peak-to-average transmission power for a higher data rate.