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26 pages, 1166 KiB  
Article
Preamble-Based Signal-to-Noise Ratio Estimation for Adaptive Modulation in Space–Time Block Coding-Assisted Multiple-Input Multiple-Output Orthogonal Frequency Division Multiplexing System
by Shahid Manzoor, Noor Shamsiah Othman and Mohammed W. Muhieldeen
Algorithms 2025, 18(2), 97; https://doi.org/10.3390/a18020097 - 9 Feb 2025
Viewed by 338
Abstract
This paper presents algorithms to estimate the signal-to-noise ratio (SNR) in the time domain and frequency domain that employ a modified Constant Amplitude Zero Autocorrelation (CAZAC) synchronization preamble, denoted as CAZAC-TD and CAZAC-FD SNR estimators, respectively. These SNR estimators are invoked in a [...] Read more.
This paper presents algorithms to estimate the signal-to-noise ratio (SNR) in the time domain and frequency domain that employ a modified Constant Amplitude Zero Autocorrelation (CAZAC) synchronization preamble, denoted as CAZAC-TD and CAZAC-FD SNR estimators, respectively. These SNR estimators are invoked in a space–time block coding (STBC)-assisted multiple-input multiple-output (MIMO) orthogonal frequency division multiplexing (OFDM) system. These SNR estimators are compared to the benchmark frequency domain preamble-based SNR estimator referred to as the Milan-FD SNR estimator when used in a non-adaptive 2×2 STBC-assisted MIMO-OFDM system. The performance of the CAZAC-TD and CAZAC-FD SNR estimators is further investigated in the non-adaptive 4×4 STBC-assisted MIMO-OFDM system, which shows improved bit error rate (BER) and normalized mean square error (NMSE) performance. It is evident that the non-adaptive 2×2 and 4×4 STBC-assisted MIMO-OFDM systems that invoke the CAZAC-TD SNR estimator exhibit superior performance and approach closer to the normalized Cramer–Rao bound (NCRB). Subsequently, the CAZAC-TD SNR estimator is invoked in an adaptive modulation scheme for a 2×2 STBC-assisted MIMO-OFDM system employing M-PSK, denoted as the AM-CAZAC-TD-MIMO system. The AM-CAZAC-TD-MIMO system outperformed the non-adaptive STBC-assisted MIMO-OFDM system using 8-PSK by about 2 dB at BER = 104. Moreover, the AM-CAZAC-TD-MIMO system demonstrated an SNR gain of about 4 dB when compared with an adaptive single-input single-output (SISO)-OFDM system with M-PSK. Therefore, it was shown that the spatial diversity of the MIMO-OFDM system is key for the AM-CAZAC-TD-MIMO system’s improved performance. Full article
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Figure 1

Figure 1
<p>STBC-assisted MIMO-OFDM system with adaptive modulation block diagram.</p>
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<p>Suparna preamble structure proposed for time synchronization [<a href="#B32-algorithms-18-00097" class="html-bibr">32</a>].</p>
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<p>Proposed modified preamble structure for CAZAC-TD and CAZAC-FD SNR estimators.</p>
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<p>Proposed modified preamble structure with cyclic prefix.</p>
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<p>Preamble structure used in Milan SNR estimator in [<a href="#B18-algorithms-18-00097" class="html-bibr">18</a>].</p>
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<p>Flowchart of CAZAC-TD SNR estimation algorithm.</p>
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<p>At <math display="inline"><semantics> <mrow> <mi>S</mi> <mi>N</mi> <mi>R</mi> <mo>=</mo> <mn>12</mn> </mrow> </semantics></math> dB, the autocorrelation plots of (<b>a</b>) the transmitted OFDM signal and (<b>b</b>) the received STBC-decoded signal.</p>
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<p>The non-adaptive STBC-assisted MIMO-OFDM system’s BER performance when employing <span class="html-italic">M</span>-PSK modulation for transmission over the SUI-5 channel.</p>
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<p>Autocorrelation plots of OFDM received signal, transmitted over AWGN channel: (<b>a</b>) the Suparna preamble structure; (<b>b</b>) the modified CAZAC preamble structure.</p>
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<p>The NMSE performance invoking Suparna preamble structure and the modified CAZAC preamble structure for the AWGN channel.</p>
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<p>The estimated SNR performance for the AWGN channel with a zoomed-in view in the inset.</p>
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<p>The estimated SNR performance for the SUI-5 channel with a zoomed-in view in the inset.</p>
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<p>The NMSE performance of the non-adaptive STBC-assisted MIMO-OFDM system for the AWGN channel.</p>
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<p>The NMSE performance of the non-adaptive STBC-assisted MIMO-OFDM system for the SUI-5 channel.</p>
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<p>The BER performance of the non-adaptive STBC-assisted MIMO-OFDM system for the AWGN channel.</p>
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<p>The BER performance of the non-adaptive STBC-MIMO-OFDM system for the SUI-5 channel.</p>
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<p>The proposed AM-CAZAC-TD-MIMO system’s BER performance for the SUI-5 channel.</p>
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<p>The proposed AM-CAZAC-TD-MIMO system’s channel capacity performance for the SUI-5 channel.</p>
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<p>A comparison of the BER performance of the AM-CAZAC-TD-MIMO system and AM-CAZAC-TD-SISO system employing <span class="html-italic">M</span>-PSK for the SUI-5 channel.</p>
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<p>A comparison of the channel capacity performance of the AM-CAZAC-TD-MIMO system and AM-CAZAC-TD-SISO system employing <span class="html-italic">M</span>-PSK for SUI-5 channel.</p>
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15 pages, 419 KiB  
Technical Note
Elevation Angle Estimation in a Multipath Environment Using MIMO-OFDM Signals
by Yeo-Sun Yoon
Remote Sens. 2024, 16(23), 4490; https://doi.org/10.3390/rs16234490 - 29 Nov 2024
Viewed by 540
Abstract
It is challenging to estimate the elevation angle of low-altitude targets due to the multipath effect. Various signal processing techniques have been proposed to mitigate these effects, including the use of multi-frequency signals as opposed to single narrowband signals. However, the optimal type [...] Read more.
It is challenging to estimate the elevation angle of low-altitude targets due to the multipath effect. Various signal processing techniques have been proposed to mitigate these effects, including the use of multi-frequency signals as opposed to single narrowband signals. However, the optimal type of multi-frequency signals and their effective utilization have not been thoroughly explored. Compressive sensing was also proposed as a high-resolution angle estimation method. But, that was conducted with narrowband signals. In this paper, we employ MIMO-OFDM signals along with a block sparse Bayesian learning fast marginalized (BSBL-FM) method. This combination allows for the effective processing of multi-frequency signals and provides high resolution estimates. The MIMO-OFDM approach represents radar signals in a block-sparse matrix form, and the BSBL-FM method leverages this sparsity to achieve high-resolution angle estimates. Simulation results demonstrate that our method can accurately estimate angles at extremely low altitudes where the elevation angle is less than 1 degree. Full article
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Graphical abstract

Graphical abstract
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<p>Multipath geometry.</p>
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<p>Flowchart for the proposed elevation angle estimation method.</p>
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<p>Elevation angles of the target and the reflected signal according to the ground range from the radar. The elevation angle is less than 0.5 degree and the difference between the two angles is very small.</p>
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<p>Power gain of the received signal. For a single-frequency signal, when the direct signal and the reflected signal are in phase, its magnitude becomes almost two, resulting in a 6 dB power gain. However, at some range, it becomes out of phase. Then, its power is significantly lower. On the other hand, the power of the OFDM signal is relatively stable. This is another advantage of using multi-frequency signals.</p>
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<p>Estimation results of Liu’s algorithm [<a href="#B7-remotesensing-16-04490" class="html-bibr">7</a>] for SNR = 10 dB and 100 trials. (<b>a</b>) Estimation results; Dots indicate the target signal and the reflected signal. Triangles and crosses are estimated values. Where it could not resolve two values, no mark is plotted. (<b>b</b>) Probability resolution; It never reached 100% and at some range, it was 0%.</p>
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<p><math display="inline"><semantics> <mrow> <mi>δ</mi> <mi>R</mi> <mo>/</mo> <msub> <mi>λ</mi> <mrow> <mo>Δ</mo> <mi>f</mi> </mrow> </msub> </mrow> </semantics></math> value for various height differences between the target and the antenna. When the difference is large and the target is close, the value is large. However, for the cases of low altitude and a far-range target, where the elevation angle is small, its value is much less than 0.5.</p>
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<p>Elevation angles and their estimates obtained using the BSBL-FM algorithm with MIMO-OFDM signals. Solid lines represent the ground truth, dotted lines correspond to the no-noise case, and dashed lines indicate the 10 dB SNR case. Blue lines are for the target and red lines are for the reflected signal.</p>
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<p>RMSE of elevation angle of the target for various SNRs (200 simulations per each SNR). The solid lines represent the proposed method and the dotted lines represent Liu’s method.</p>
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20 pages, 1627 KiB  
Article
Dynamic Spectrum Co-Access in Multicarrier-Based Cognitive Radio Using Graph Theory Through Practical Channel
by Ehab F. Badran, Amr A. Bashir, Hassan Nadir Kheirallah and Hania H. Farag
Appl. Sci. 2024, 14(23), 10868; https://doi.org/10.3390/app142310868 - 23 Nov 2024
Viewed by 983
Abstract
In this paper, we propose an underlay cognitive radio (CR) system that includes subscribers, termed secondary users (SUs), which are designed to coexist with the spectrum owners, termed primary users (PUs). The suggested network includes the PUs system and the SUs system. The [...] Read more.
In this paper, we propose an underlay cognitive radio (CR) system that includes subscribers, termed secondary users (SUs), which are designed to coexist with the spectrum owners, termed primary users (PUs). The suggested network includes the PUs system and the SUs system. The coexistence between them is achieved by using a novel dynamic spectrum co-access multicarrier-based cognitive radio (DSCA-MC-CR) technique. The proposal uses a quadrature phase shift keying (QPSK) modulation technique within the orthogonal frequency-division multiplexing (OFDM) scheme that maximizes the system data rate and prevents data inter-symbol interference (ISI). The proposed CR transmitter station (TX) and the CR receiver node (RX) can use an advanced smart antenna system, i.e., a multiple-input and multiple-output (MIMO) system that provides high immunity against channel impairments and provides a high data rate through its different combining techniques. The proposed CR system is applicable to coexist within different existing communication applications like fifth-generation (5G) applications, emergence applications like the Internet of Things (IoT), narrow-band (NB) applications, and wide-band (WB) applications. The coexistence between the PUs system and the SUs system is based on using power donation from the SUs system to improve the quality of the PU signal-to-interference-and-noise ratios (SINRs). The green communication concept achieved in this proposal is compared with similar DSCA proposals from the literature. The simulations of the proposed technique show enhancement in the PUs system throughput and data rate along with the better performance of the SUs system. Full article
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Figure 1
<p>Cognitive radio capability characteristics.</p>
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<p>The classification of the DSA management models. (<b>a</b>) Interweave model (<b>b</b>) Underlay Model (<b>c</b>) Overlay Model.</p>
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<p>Topology and spectrum representation of model 1. (<b>a</b>) Model 1 topology of the proposed DSCA-MC-CR using OMNeT. (<b>b</b>) Spectrum representation of model 1.</p>
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<p>Topology and spectrum representation of model 2. (<b>a</b>) Model 2 topology of the proposed DSCA-MC-CR using OMNeT. (<b>b</b>) Spectrum representation of model 2.</p>
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<p>The block diagram design of the proposed DSCA-MC-CR SU-TX tower.</p>
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<p>The proposed correlator receiver design of the SU-RX.</p>
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<p>Simple <math display="inline"><semantics> <mrow> <mi>M</mi> <mo>×</mo> <mi>N</mi> </mrow> </semantics></math> MIMO system diagram.</p>
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<p>The proposed topology classification using conventional DSP and GSP. (<b>a</b>) The proposed topology using conventional DSP. (<b>b</b>) The proposed topology classification using GSP.</p>
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<p>BER of the PU and SU in model 1 over AWGN with <math display="inline"><semantics> <mrow> <mi>γ</mi> <mo>=</mo> <mn>3</mn> <mo>%</mo> </mrow> </semantics></math>. (<b>a</b>) BER of the PU in model 1. (<b>b</b>) BER of the SU in model 1.</p>
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<p>BER of the PU and SU in model 1 under fading channel with <math display="inline"><semantics> <mrow> <mi>γ</mi> <mo>=</mo> <mn>3</mn> <mo>%</mo> </mrow> </semantics></math>. (<b>a</b>) BER of the PU in model 1. (<b>b</b>) BER of the SU in model 1.</p>
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<p>OMNeT proposed network for model 1 with practical medium parameters. (<b>a</b>) OMNeT network of model 1. (<b>b</b>) PU system and SU system in OSA mode.</p>
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<p><math display="inline"><semantics> <msub> <mrow> <mi>P</mi> <mi>U</mi> </mrow> <mn>1</mn> </msub> </semantics></math> and <math display="inline"><semantics> <msub> <mrow> <mi>S</mi> <mi>U</mi> </mrow> <mn>1</mn> </msub> </semantics></math> BER vs. SINR with <math display="inline"><semantics> <mrow> <mi>γ</mi> <mo>=</mo> <mn>10</mn> <mo>%</mo> </mrow> </semantics></math>. (<b>a</b>) <math display="inline"><semantics> <msub> <mrow> <mi>P</mi> <mi>U</mi> </mrow> <mn>1</mn> </msub> </semantics></math> BER vs. SINR with <math display="inline"><semantics> <mrow> <mi>γ</mi> <mo>=</mo> <mn>10</mn> <mo>%</mo> </mrow> </semantics></math>. (<b>b</b>) <math display="inline"><semantics> <msub> <mrow> <mi>S</mi> <mi>U</mi> </mrow> <mn>1</mn> </msub> </semantics></math> BER vs. SINR with <math display="inline"><semantics> <mrow> <mi>γ</mi> <mo>=</mo> <mn>10</mn> <mo>%</mo> </mrow> </semantics></math>.</p>
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<p>PU and SU capacities using different techniques versus SNR. (<b>a</b>) PU capacity versus SNR. (<b>b</b>) SU capacity versus SNR.</p>
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<p>PU and SU BERs of model 2 using Gaussian channel with <math display="inline"><semantics> <mrow> <mi>γ</mi> <mo>=</mo> <mn>3</mn> <mo>%</mo> </mrow> </semantics></math>. (<b>a</b>) PU BER of model 2. (<b>b</b>) SU BER of model 2.</p>
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<p>PU and SU BERs of model 2 using fading channel with <math display="inline"><semantics> <mrow> <mi>γ</mi> <mo>=</mo> <mn>3</mn> <mo>%</mo> </mrow> </semantics></math>. (<b>a</b>) PU BER of model 2. (<b>b</b>) SU BER of model 2.</p>
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<p>Systems packet interarrival analysis of LTE using the OSA, DSCA, OC-DSA, and DSCA-MC-CR techniques. (<b>a</b>) PU systems packet interarrival analysis of LTE. (<b>b</b>) SU systems packet interarrival analysis of LTE.</p>
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<p>System packet interarrival analysis for 5G using the OSA, DSCA, OC-DSA, and DSCA-MC-CR techniques. (<b>a</b>) PU system packet interarrival analysis of 5G. (<b>b</b>) SU system packet interarrival analysis of 5G.</p>
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24 pages, 3486 KiB  
Article
Multi-Cluster Approaches to Radio Sensor Array Channel Modeling and Simulation
by Xin Li, Torbjörn Ekman and Kun Yang
Sensors 2024, 24(18), 6037; https://doi.org/10.3390/s24186037 - 18 Sep 2024
Viewed by 705
Abstract
In this paper, we explore the physical propagation environment of radio waves by describing it in terms of distant scattering clusters. Each cluster consists of numerous scattering objects that may exhibit certain statistical properties. By utilizing geometry-based methods, we can study the channel [...] Read more.
In this paper, we explore the physical propagation environment of radio waves by describing it in terms of distant scattering clusters. Each cluster consists of numerous scattering objects that may exhibit certain statistical properties. By utilizing geometry-based methods, we can study the channel second-order statistics (CSOS), where each distant scattering cluster corresponds to a CSOS, contributes a portion to the Doppler spectrum, and is associated with a state-space multiple-input and multiple-output (MIMO) radio channel model. Consequently, the physical propagation environment of radio waves can be modeled by summing multiple state-space MIMO radio channel models. This approach offers three key advantages: simplicity, the ability to construct the entire Doppler power spectrum from multiple uncorrelated distant scattering clusters, and the capability to obtain the channels contributed by these clusters by summing the individual channels. This methodology enables the reconstruction of the radio wave propagation environment in a simulated manner and is crucial for developing massive MIMO channel models. Full article
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Figure 1

Figure 1
<p>A typical mobile radio scenario for multi-path propagation in a terrestrial radio propagation environment.</p>
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<p>A distant cluster with an <math display="inline"><semantics> <mrow> <msub> <mi>M</mi> <mi>r</mi> </msub> <mo>×</mo> <msub> <mi>M</mi> <mi>t</mi> </msub> </mrow> </semantics></math> MIMO antenna array, <math display="inline"><semantics> <msub> <mi>l</mi> <mi>k</mi> </msub> </semantics></math> is the distance between the scattering object <math display="inline"><semantics> <msub> <mi mathvariant="normal">S</mi> <mi mathvariant="normal">k</mi> </msub> </semantics></math> and the cluster center O.</p>
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<p>Laplace PDF and Cauchy PDF, special case of parametrization. (<b>a</b>) Laplace PDF <math display="inline"><semantics> <mrow> <msub> <mi>g</mi> <mi>x</mi> </msub> <mrow> <mo>(</mo> <mi>x</mi> <mo>)</mo> </mrow> <mspace width="3.33333pt"/> <mo>=</mo> <mspace width="3.33333pt"/> <mstyle scriptlevel="0" displaystyle="true"> <mfrac> <mn>1</mn> <mn>2</mn> </mfrac> </mstyle> <msup> <mi>e</mi> <mrow> <mo>−</mo> <mo>|</mo> <mi>x</mi> <mo>|</mo> </mrow> </msup> </mrow> </semantics></math>. (<b>b</b>) Cauchy PDF <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mi>x</mi> </msub> <mrow> <mo>(</mo> <mi>x</mi> <mo>)</mo> </mrow> <mo>=</mo> <mstyle scriptlevel="0" displaystyle="true"> <mfrac> <mn>1</mn> <mi>π</mi> </mfrac> </mstyle> <mstyle scriptlevel="0" displaystyle="true"> <mfrac> <mi>η</mi> <mrow> <msup> <mi>η</mi> <mn>2</mn> </msup> <mo>+</mo> <msup> <mi>x</mi> <mn>2</mn> </msup> </mrow> </mfrac> </mstyle> </mrow> </semantics></math>, where <math display="inline"><semantics> <mrow> <mi>η</mi> <mo>=</mo> <mn>0.634</mn> </mrow> </semantics></math>.</p>
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<p>The motion vector is decomposed into a phase change on OA and a damping change on AW, where AB and EF denote the antenna arrays, and A, B, E, and F are antenna sensors.</p>
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<p>K distant scattering clusters, cluster no. 1 to cluster no. K, in a radio wave propagation environment, each of which is broken down into many resolvable multi-path components.</p>
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<p>Block diagram of the AR(p)-based state-space SISO channel model.</p>
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<p>Block diagram of the AR(p)-based state space MIMO channel model, where <math display="inline"><semantics> <mrow> <msub> <mi>h</mi> <mi>k</mi> </msub> <mrow> <mo>[</mo> <mi>m</mi> <mo>]</mo> </mrow> </mrow> </semantics></math>, <span class="html-italic">m</span> denotes channel index.</p>
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<p>Block diagram of the MIMO-OFDM channel model, where <math display="inline"><semantics> <mrow> <msub> <mi>h</mi> <mi>k</mi> </msub> <mrow> <mo>[</mo> <mi>m</mi> <mo>,</mo> <mi>n</mi> <mo>]</mo> </mrow> </mrow> </semantics></math>, <span class="html-italic">m</span> and <span class="html-italic">n</span> denote channel index.</p>
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<p>Block diagram of a <span class="html-italic">K</span>-cluster MIMO-OFDM channel model, where the input noise vector <math display="inline"><semantics> <mrow> <msub> <mi mathvariant="bold">w</mi> <mi>k</mi> </msub> <mo>∈</mo> <msup> <mi mathvariant="double-struck">C</mi> <mrow> <msub> <mi>KM</mi> <mi mathvariant="normal">f</mi> </msub> <msub> <mi mathvariant="normal">M</mi> <mi mathvariant="normal">r</mi> </msub> <msub> <mi mathvariant="normal">M</mi> <mi mathvariant="normal">t</mi> </msub> </mrow> </msup> </mrow> </semantics></math>, the output channel vector <math display="inline"><semantics> <mrow> <mi mathvariant="bold">h</mi> <mo>[</mo> <mi>k</mi> <mo>,</mo> <mn>0</mn> <mo>:</mo> <msub> <mi>M</mi> <mi>f</mi> </msub> <mo>−</mo> <mn>1</mn> <mo>]</mo> </mrow> </semantics></math> means that there are <math display="inline"><semantics> <msub> <mi>M</mi> <mi>f</mi> </msub> </semantics></math> sub-carriers from <math display="inline"><semantics> <mrow> <msub> <mi>m</mi> <mi>f</mi> </msub> <mo>=</mo> <mn>0</mn> </mrow> </semantics></math> to <math display="inline"><semantics> <mrow> <msub> <mi>m</mi> <mi>f</mi> </msub> <mo>=</mo> <msub> <mi>M</mi> <mi>f</mi> </msub> <mo>−</mo> <mn>1</mn> </mrow> </semantics></math>.</p>
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<p>Angular-delay spectrum and power azimuth spectrum of the clusters. (<b>a</b>) Angular-delay spectrum of the clusters. (<b>b</b>) Power azimuth spectrum of the clusters.</p>
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<p>The power of AOA and power delay profile of the clusters. (<b>a</b>) The PDP of the clusters, where <math display="inline"><semantics> <mrow> <msub> <mover> <mi>τ</mi> <mo>¯</mo> </mover> <mn>1</mn> </msub> <mo>=</mo> <mn>11.24</mn> <mspace width="3.33333pt"/> <mi mathvariant="sans-serif">μ</mi> <mi mathvariant="normal">s</mi> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mover> <mi>τ</mi> <mo>¯</mo> </mover> <mn>2</mn> </msub> <mo>=</mo> <mn>10.64</mn> <mspace width="3.33333pt"/> <mi mathvariant="sans-serif">μ</mi> <mi mathvariant="normal">s</mi> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mover> <mi>τ</mi> <mo>¯</mo> </mover> <mn>3</mn> </msub> <mo>=</mo> <mn>10.27</mn> <mspace width="3.33333pt"/> <mi mathvariant="sans-serif">μ</mi> <mi mathvariant="normal">s</mi> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mover> <mi>τ</mi> <mo>¯</mo> </mover> <mn>4</mn> </msub> <mo>=</mo> <mn>13.5</mn> <mspace width="3.33333pt"/> <mi mathvariant="sans-serif">μ</mi> <mi mathvariant="normal">s</mi> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mover> <mi>τ</mi> <mo>¯</mo> </mover> <mn>5</mn> </msub> <mo>=</mo> <mn>12.65</mn> <mspace width="3.33333pt"/> <mi mathvariant="sans-serif">μ</mi> <mi mathvariant="normal">s</mi> </mrow> </semantics></math>. (<b>b</b>) The power of AOA of the clusters, where <math display="inline"><semantics> <mrow> <msub> <mi>α</mi> <msub> <mn>0</mn> <mn>1</mn> </msub> </msub> <mo>=</mo> <mn>162.35</mn> </mrow> </semantics></math><math display="inline"><semantics> <mo>°</mo> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>α</mi> <msub> <mn>0</mn> <mn>2</mn> </msub> </msub> <mo>=</mo> <mn>143.13</mn> </mrow> </semantics></math><math display="inline"><semantics> <mo>°</mo> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>α</mi> <msub> <mn>0</mn> <mn>3</mn> </msub> </msub> <mo>=</mo> <mo>−</mo> <mn>166.87</mn> </mrow> </semantics></math><math display="inline"><semantics> <mo>°</mo> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>α</mi> <msub> <mn>0</mn> <mn>4</mn> </msub> </msub> <mo>=</mo> <mo>−</mo> <mn>148.24</mn> </mrow> </semantics></math><math display="inline"><semantics> <mo>°</mo> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>α</mi> <msub> <mn>0</mn> <mn>5</mn> </msub> </msub> <mo>=</mo> <mo>−</mo> <mn>108.43</mn> </mrow> </semantics></math><math display="inline"><semantics> <mo>°</mo> </semantics></math>.</p>
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<p>Channel correlation estimation of cluster No. 1, characterized as a Rayleigh cluster. The sequence is generated from the state-space MIMO-OFDM channel model. (<b>a</b>) The real part of the STCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>. (<b>b</b>) The real part of the STSCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <msub> <mi>m</mi> <mi>f</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mo>Δ</mo> <mi>f</mi> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math> MHz.</p>
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<p>Channel correlation estimation of cluster No. 2, characterized as a Rayleigh cluster. The sequence is generated from the state-space MIMO-OFDM channel model. (<b>a</b>) The real part of the STCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>. (<b>b</b>) The real part of the STSCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <msub> <mi>m</mi> <mi>f</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mo>Δ</mo> <mi>f</mi> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math> MHz.</p>
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<p>Channel correlation estimation of cluster No. 3, characterized as a Cauchy–Rayleigh cluster. The sequence is generated from the state-space MIMO-OFDM channel model. (<b>a</b>) The real part of the STCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>. (<b>b</b>) The real part of the STSCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <msub> <mi>m</mi> <mi>f</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mo>Δ</mo> <mi>f</mi> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math> MHz.</p>
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<p>Channel correlation estimation of cluster No. 4, characterized as a Cauchy–Rayleigh cluster. The sequence is generated from the state-space MIMO-OFDM channel model. (<b>a</b>) The real part of the STCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>. (<b>b</b>) The real part of the STSCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <msub> <mi>m</mi> <mi>f</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mo>Δ</mo> <mi>f</mi> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math> MHz.</p>
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<p>Channel correlation estimation of cluster No. 5, characterized as a Rayleigh cluster. The sequence is generated from the state-space MIMO-OFDM channel model. (<b>a</b>) The real part of the STCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>. (<b>b</b>) The real part of the STSCF, where <math display="inline"><semantics> <mrow> <msub> <mi>d</mi> <mi>t</mi> </msub> <mo>=</mo> <msub> <mi>d</mi> <mi>r</mi> </msub> <mo>=</mo> <msub> <mi>m</mi> <mi>f</mi> </msub> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mo>Δ</mo> <mi>f</mi> <mo>=</mo> <mn>1</mn> </mrow> </semantics></math> MHz.</p>
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<p>SISO channel sequence with its corresponding correlation function. (<b>a</b>) The SISO channel sequence (real part) generated by this 5-cluster state-space MIMO-OFDM channel model. (<b>b</b>) The SISO channel correlation function (real part), estimation is from this 5-cluster state-space MIMO-OFDM channel model.</p>
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<p>Channel correlation estimation based on the sequence generated from this 5-cluster state-space MIMO-OFDM channel model. (<b>a</b>) The SIMO channel correlation function (real part). (<b>b</b>) The MISO channel correlation function (real part).</p>
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<p>Channel correlation estimation based on the sequence generated from this 5-cluster state-space MIMO-OFDM channel model. (<b>a</b>) The MIMO channel correlation function (real part). (<b>b</b>) The MIMO-OFDM channel correlation function (real part).</p>
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15 pages, 539 KiB  
Article
A Novel Waveform Optimization Method for Orthogonal-Frequency Multiple-Input Multiple-Output Radar Based on Dual-Channel Neural Networks
by Meng Xia, Wenrong Gong and Lichao Yang
Sensors 2024, 24(17), 5471; https://doi.org/10.3390/s24175471 - 23 Aug 2024
Viewed by 798
Abstract
The orthogonal frequency-division multiplexing (OFDM) mode with a linear frequency modulation (LFM) signal as the baseband waveform has been widely studied and applied in multiple-input multiple-output (MIMO) radar systems. However, its high sidelobe levels after pulse compression affect the target detection of radar [...] Read more.
The orthogonal frequency-division multiplexing (OFDM) mode with a linear frequency modulation (LFM) signal as the baseband waveform has been widely studied and applied in multiple-input multiple-output (MIMO) radar systems. However, its high sidelobe levels after pulse compression affect the target detection of radar systems. For this paper, theoretical analysis was performed, to investigate the causes of high sidelobe levels in OFDM-LFM waveforms, and a novel waveform optimization design method based on deep neural networks is proposed. This method utilizes the classic ResNeXt network to construct dual-channel neural networks, and a new loss function is employed to design the phase and bandwidth of the OFDM-LFM waveforms. Meanwhile, the optimization factor is exploited, to address the optimization problem of the peak sidelobe levels (PSLs) and integral sidelobe levels (ISLs). Our numerical results verified the correctness of the theoretical analysis and the effectiveness of the proposed method. The designed OFDM-LFM waveforms exhibited outstanding performance in pulse compression and improved the detection performance of the radar. Full article
(This article belongs to the Section Radar Sensors)
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<p>Mathematical analysis of <math display="inline"><semantics> <mrow> <mi>F</mi> <mo>(</mo> <mi>τ</mi> <mo>)</mo> </mrow> </semantics></math>: (<b>a</b>) Main function and periodic sampling function with <span class="html-italic">N</span> = 25. (<b>b</b>) Correlation result of MIMO-LFM with <span class="html-italic">N</span> = 25.</p>
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<p>Mathematical analysis of <math display="inline"><semantics> <mrow> <mi>R</mi> <mo>(</mo> <mi>τ</mi> <mo>)</mo> </mrow> </semantics></math>: (<b>a</b>) Main function and periodic sampling function of <math display="inline"><semantics> <mrow> <mi>R</mi> <mo>(</mo> <mi>τ</mi> <mo>)</mo> </mrow> </semantics></math>. (<b>b</b>) Results of <math display="inline"><semantics> <mrow> <mi>R</mi> <mo>(</mo> <mi>τ</mi> <mo>)</mo> </mrow> </semantics></math> and <math display="inline"><semantics> <mrow> <mi>L</mi> <mo>(</mo> <mi>τ</mi> <mo>)</mo> </mrow> </semantics></math>.</p>
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<p>Dual-channel CNNs for OFDM-LFM waveform design. In the figure, “Conv” represents convolution layer; “BN” represents batch normalization; “Pooling” represents max-pooling; “FC” represents fully connected layer; “Residual block” represents residual mapping based on group convolution; “phase activation function” and “bandwidth activation function” are the phase and bandwidth activation functions proposed in this paper for OFDM-LFM waveform design; “side lobe loss function” represents the objective function based on the sidelobe properties optimization represented by Equation (<a href="#FD22-sensors-24-05471" class="html-disp-formula">22</a>).</p>
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<p>Sidelobe properties of the initial OFDM-LFM waveforms.</p>
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<p>Optimization with the PSL as the objective (<math display="inline"><semantics> <mi>ε</mi> </semantics></math> = 1): (<b>a</b>) Optimized results with the PSL. (<b>b</b>) The descent of the loss function during iterations with the PSL.</p>
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<p>Optimization with the ISL as the objective (<math display="inline"><semantics> <mi>ε</mi> </semantics></math> = 0): (<b>a</b>) Optimized results with the ISL. (<b>b</b>) The descent of the loss function during iterations with the ISL.</p>
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<p>Results of different optimization factors.</p>
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19 pages, 1137 KiB  
Article
A Bayesian Tensor Decomposition Method for Joint Estimation of Channel and Interference Parameters
by Yuzhe Sun, Wei Wang, Yufan Wang and Yuanfeng He
Sensors 2024, 24(16), 5284; https://doi.org/10.3390/s24165284 - 15 Aug 2024
Cited by 2 | Viewed by 1130
Abstract
Bayesian tensor decomposition has been widely applied in channel parameter estimations, particularly in cases with the presence of interference. However, the types of interference are not considered in Bayesian tensor decomposition, making it difficult to accurately estimate the interference parameters. In this paper, [...] Read more.
Bayesian tensor decomposition has been widely applied in channel parameter estimations, particularly in cases with the presence of interference. However, the types of interference are not considered in Bayesian tensor decomposition, making it difficult to accurately estimate the interference parameters. In this paper, we present a robust tensor variational method using a CANDECOMP/PARAFAC (CP)-based additive interference model for multiple input–multiple output (MIMO) with orthogonal frequency division multiplexing (OFDM) systems. A more realistic interference model compared to traditional colored noise is considered in terms of co-channel interference (CCI) and front-end interference (FEI). In contrast to conventional algorithms that filter out interference, the proposed method jointly estimates the channel and interference parameters in the time–frequency domain. Simulation results validate the correctness of the proposed method by the evidence lower bound (ELBO) and reveal the fact that the proposed method outperforms traditional information-theoretic methods, tensor decomposition models, and robust model based on CP (RCP) in terms of estimation accuracy. Further, the interference parameter estimation technique has profound implications for anti-interference applications and dynamic spectrum allocation. Full article
(This article belongs to the Special Issue Integrated Localization and Communication: Advances and Challenges)
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<p>A typical traffic scenario.</p>
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<p>The power composition of the received tensor.</p>
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<p>Probabilistic graphical model.</p>
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<p>(<b>a</b>) The changes in the number of paths and the three variations of ELBO for RCP-APH. (<b>b</b>) The probability density function (PDF) of the interference item power distribution and other estimated parameters for RCP and RCP-APH.</p>
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<p>For different interference item ratios, a comparison of rank and parameter estimation performance is conducted for interference powers of <math display="inline"><semantics> <mrow> <mn>5</mn> <msubsup> <mi>σ</mi> <mrow> <mi>N</mi> <mi>o</mi> <mi>i</mi> <mi>s</mi> <mi>e</mi> </mrow> <mn>2</mn> </msubsup> </mrow> </semantics></math> and <math display="inline"><semantics> <mrow> <mn>10</mn> <msubsup> <mi>σ</mi> <mrow> <mi>N</mi> <mi>o</mi> <mi>i</mi> <mi>s</mi> <mi>e</mi> </mrow> <mn>2</mn> </msubsup> </mrow> </semantics></math>. (<b>a</b>) Rank estimation. (<b>b</b>) Angle estimation. (<b>c</b>) Delay estimation. Here, (<b>b</b>,<b>c</b>) share a common legend.</p>
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<p>Study on the performance of interference estimation for the RCP-APH. Green indicates accurately estimated interference positions, while blue represents unestimated interference positions. (<b>a</b>) True interference; (<b>b</b>) matrix unfolding of true interference; (<b>c</b>) estimated interference; (<b>d</b>) matrix unfolding of estimated interference.</p>
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<p>The estimations of the interference positions are compared between two variational algorithms under different interference ratios. To clearly depict the performance differences between the algorithms, coordinate annotations for all subplots are omitted. The first row illustrates the estimated noise precision and PDF of the interference item power for both the RCP-APH and RCP algorithms. The coordinate scales are consistent with <a href="#sensors-24-05284-f004" class="html-fig">Figure 4</a>b. The second row represents the actual interference, while the third and fourth rows depict the estimations of the interference positions for both algorithms. The coordinate scales align with those in <a href="#sensors-24-05284-f006" class="html-fig">Figure 6</a>b.</p>
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<p>Under different interference item ratios, a comparison of interference estimation is conducted for interference powers of <math display="inline"><semantics> <mrow> <mn>5</mn> <msubsup> <mi>σ</mi> <mrow> <mi>N</mi> <mi>o</mi> <mi>i</mi> <mi>s</mi> <mi>e</mi> </mrow> <mn>2</mn> </msubsup> </mrow> </semantics></math> and <math display="inline"><semantics> <mrow> <mn>10</mn> <msubsup> <mi>σ</mi> <mrow> <mi>N</mi> <mi>o</mi> <mi>i</mi> <mi>s</mi> <mi>e</mi> </mrow> <mn>2</mn> </msubsup> </mrow> </semantics></math>. (<b>a</b>) Recall. (<b>b</b>) Precision. (<b>c</b>) F1 Score. Here, all subplots share a common legend.</p>
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<p>Interference estimation performance is compared for different interference item ratios for both 10 dB and 20 dB of <math display="inline"><semantics> <mi>ρ</mi> </semantics></math>. (<b>a</b>) Recall. (<b>b</b>) Precision. (<b>c</b>) F1 Score. Here, all subplots share a common legend.</p>
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<p>Performance metrics for interference estimation for different spatial structures and interference characteristics. (<b>a</b>) Different sampling K. (<b>b</b>) Different ratio of CCI. (<b>c</b>) Different bandwidth of FEI. All subplots share a common legend.</p>
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18 pages, 1618 KiB  
Article
MIMO Signal Detection Based on IM-LSTMNet Model
by Xiaoli Huang, Yumiao Yuan and Jingyu Li
Electronics 2024, 13(16), 3153; https://doi.org/10.3390/electronics13163153 - 9 Aug 2024
Cited by 2 | Viewed by 1338
Abstract
Signal detection is crucial in multi-input multi-output orthogonal frequency division multiplexing (MIMO-OFDM) systems, yet classical detection methods often struggle with nonlinear issues in wireless channels. To handle this challenge, we propose a novel signal detection method for MIMO-OFDM system based on the fractional [...] Read more.
Signal detection is crucial in multi-input multi-output orthogonal frequency division multiplexing (MIMO-OFDM) systems, yet classical detection methods often struggle with nonlinear issues in wireless channels. To handle this challenge, we propose a novel signal detection method for MIMO-OFDM system based on the fractional Fourier transform (FrFT), leveraging the robust time series processing capabilities of long short-term memory (LSTM) networks. Our innovative approach, termed IM-LSTMNet, integrates LSTM with convolutional neural networks (CNNs) and incorporates a Squeeze and Excitation Network to emphasize critical information, enhancing neural network performance. The proposed IM-LSTMNet is applied to the FrFT-based MIMO-OFDM system to improve signal detection performance. We compare the detection results of IM-LSTMNet with zero forcing (ZF), minimum mean square error (MMSE), simple LSTM neural network, and CNN–LSTM network by evaluating the bit error rate. Experimental results demonstrate that IM-LSTMNet outperforms ZF, MMSE, LSTM, and other methods, significantly enhancing system signal detection performance. This work offers a promising advancement in MIMO-OFDM signal detection, presenting a deep learning-based solution that effectively improves the system signal detection performance. Full article
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<p>MIMO system structure diagram.</p>
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<p>Flow chart of the IM-LSTMNet model detecting the MIMO-OFDM signal based on FrFT.</p>
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<p>Block diagram of the FrFT-based MIMO-OFDM system.</p>
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<p>IM-LSTMNet frame diagram.</p>
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<p>Convolutional neural network module diagram.</p>
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<p>Squeeze-and-Excitation Network.</p>
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<p>LSTM structure diagram.</p>
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<p>Framework diagram for the detection of the MIMO-OFDM signal by a neural network.</p>
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<p>SNR = 10 dB; IM-LSTMNet model training diagram.</p>
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<p>SNR = 10 dB; IM-LSTMNet model loss diagram.</p>
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<p>The MIMO-OFDM system’s BER with FrFT order of 1.</p>
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<p>The BER of IM-LSTMNet and traditional algorithms under different orders.</p>
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<p>The BER of IM-LSTMNet and other neural network algorithms at different orders.</p>
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<p>The BER of IM-LSTMNet and the traditional algorithms under different subcarrier numbers.</p>
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<p>The BER of IM-LSTMNet and other neural network algorithms under different subcarrier numbers.</p>
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<p>The BER of IM-LSTMNet and the traditional algorithms with or without CP.</p>
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<p>The BER of IM-LSTMNet and other neural network algorithms with or without CP.</p>
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<p>The BER of the neural network algorithm under different values of H.</p>
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15 pages, 567 KiB  
Article
Manifold Optimization-Based Data Detection Algorithm for Multiple-Input–Multiple-Output Orthogonal Frequency-Division Multiplexing Systems under Time-Varying Channels
by Yumeng Li and Die Hu
Electronics 2024, 13(13), 2555; https://doi.org/10.3390/electronics13132555 - 28 Jun 2024
Viewed by 701
Abstract
Recently, multiple-input–multiple-output (MIMO) orthogonal frequency-division multiplexing (OFDM) systems have gained significant attention in the field of wireless communications. The utilization of the Riemannian manifold has become prevalent in MIMO-OFDM systems. However, the existing data detection algorithms for MIMO-OFDM systems are mostly designed for [...] Read more.
Recently, multiple-input–multiple-output (MIMO) orthogonal frequency-division multiplexing (OFDM) systems have gained significant attention in the field of wireless communications. The utilization of the Riemannian manifold has become prevalent in MIMO-OFDM systems. However, the existing data detection algorithms for MIMO-OFDM systems are mostly designed for block fading channels. Additionally, these algorithms often suffer from high computational complexity. In this paper, we propose a data detection algorithm on the basis of Riemannian manifold optimization for MIMO-OFDM systems under time-varying channels. The core concept of this algorithm is to optimize the transmitted signals by solving the manifold optimization problem in the case of time-varying channels. In order to reduce the computational complexity of the algorithm, we improve the proposed algorithm by dividing the transmitted signals into multiple subframes for solving the optimization problem separately and using the pilots to maintain the performance of the algorithm. In the simulation, the performance of multiple proposed algorithms and the forced-zero detection algorithm under different parameter settings are compared. The simulation results show that the proposed algorithm demonstrates good bit error rate and computational complexity performances. Full article
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<p>Flow diagram of Algorithm 3.</p>
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<p>BER vs. SNR under QPSK modulation.</p>
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<p>BER vs. SNR under BPSK modulation.</p>
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15 pages, 397 KiB  
Article
Novel Waveform Design with a Reduced Cyclic Prefix in MIMO Systems
by Huanhuan Yin, Jiehao Luo, Baobing Wang, Bing Zhang, Shuang Luo and Dejin Kong
Electronics 2024, 13(10), 1968; https://doi.org/10.3390/electronics13101968 - 17 May 2024
Cited by 1 | Viewed by 1129
Abstract
For well-known orthogonal frequency division multiplexing (OFDM), the cyclic prefix (CP) is essential for coping with multipath channels. Nevertheless, CP is a pure redundant signal, which wastes valuable time–frequency resources. We propose a novel waveform based on symbol repetition, which is presented to [...] Read more.
For well-known orthogonal frequency division multiplexing (OFDM), the cyclic prefix (CP) is essential for coping with multipath channels. Nevertheless, CP is a pure redundant signal, which wastes valuable time–frequency resources. We propose a novel waveform based on symbol repetition, which is presented to cut down the CP overhead in OFDM. In the presented OFDM with symbol repetition (SR-OFDM), one CP is inserted in the front of several transmitted symbols, instead of only one symbol, as in the conventional way. As a result, it can save the overhead created by CP. Furthermore, due to the existence of the remaining CP, the multipath channel can still be converted into the frequency domain, and single-tap equalization can still be used to equalize information free from interference. In addition, we also extend the proposed SR-OFDM into multiple input–multiple output (MIMO) systems. Finally, the proposed schemes are validated by computer simulations under the various channels. Full article
(This article belongs to the Special Issue Advanced Digital Signal Processing for Future Digital Communications)
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<p>The system diagram of SR-OFDM.</p>
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<p>The transmitted SR-OFDM with CP, when <math display="inline"><semantics> <mrow> <mi>υ</mi> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>.</p>
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<p>The diagram of the proposed combination of MIMO and SR-OFDM.</p>
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<p>BER comparison in AWGN channel.</p>
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<p>Spectral efficiency comparison in AWGN channel.</p>
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<p>BER comparison for perfect channel estimation in SUI-3 and AWGN channels.</p>
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<p>BER comparison for perfect channel estimation in SUI-5 and AWGN channels.</p>
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<p>BER comparison based on <math display="inline"><semantics> <mrow> <mn>2</mn> <mo>×</mo> <mn>2</mn> </mrow> </semantics></math> MIMO in SUI-5 channel.</p>
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<p>BER comparison based on <math display="inline"><semantics> <mrow> <mn>4</mn> <mo>×</mo> <mn>4</mn> </mrow> </semantics></math> MIMO in SUI-5 channel.</p>
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22 pages, 3060 KiB  
Article
Sparse Reconstruction-Based Joint Signal Processing for MIMO-OFDM-IM Integrated Radar and Communication Systems
by Yang Wang, Yunhe Cao, Tat-Soon Yeo, Yuanhao Cheng and Yulin Zhang
Remote Sens. 2024, 16(10), 1773; https://doi.org/10.3390/rs16101773 - 16 May 2024
Cited by 4 | Viewed by 1215
Abstract
Multiple-input multiple-output orthogonal frequency division multiplexing (MIMO-OFDM) technology is widely used in integrated radar and communication systems (IRCSs). Moreover, index modulation (IM) is a reliable OFDM transmission scheme in the field of communication, which transmits information by arranging several distinguishable constellations. In this [...] Read more.
Multiple-input multiple-output orthogonal frequency division multiplexing (MIMO-OFDM) technology is widely used in integrated radar and communication systems (IRCSs). Moreover, index modulation (IM) is a reliable OFDM transmission scheme in the field of communication, which transmits information by arranging several distinguishable constellations. In this paper, we propose a sparse reconstruction-based joint signal processing scheme for integrated MIMO-OFDM-IM systems. Combining the advantages of MIMO and OFDM-IM technologies, the integrated MIMO-OFDM-IM signal design is realized through the reasonable allocation of bits and subcarriers, resulting in better intercarrier interference (ICI) resistance and a higher transmission efficiency. Taking advantage of the sparseness of OFDM-IM, an improved target parameter estimation method based on sparse signal reconstruction is explored to eliminate the influence of empty subcarriers on the matched filtering at the receiver side. In addition, an improved sequential Monte Carlo signal detection method is introduced to realize the efficient detection of communication signals. The simulation results show that the proposed integrated system is 5 dB lower in the peak sidelobe ratio (PSLR) and 1.5 ×105 lower in the number of complex multiplications than the latest MIMO-OFDM system and can achieve almost the same parameter estimation performance. With the same spectral efficiency, it has a lower bit error rate (BER) than existing methods. Full article
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Graphical abstract
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<p>Schematic diagram of the proposed MIMO-OFDM integrated system model.</p>
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<p>Schematic diagram of MIMO-OFDM-IM integrated signal design in transmitter.</p>
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<p>Flow chart of the joint signal processing schemes in the proposed system.</p>
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<p>Flowchart of the conventional processing.</p>
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<p>The PSLR performance. (<b>a</b>) The variation in PSLR with SNR. (<b>b</b>) The variation in PSLR with the number of activated subcarriers (SNR = 10 dB).</p>
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<p>The variation in PSLR with SNR under different number of activated subcarriers.</p>
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<p>The variation in MSEs of range and velocity estimation with SNR under different methods (<math display="inline"><semantics> <msub> <mi>N</mi> <mi>r</mi> </msub> </semantics></math> = <math display="inline"><semantics> <msub> <mi>N</mi> <mi>t</mi> </msub> </semantics></math> = 4, <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 4, <span class="html-italic">H</span> = 4). (<b>a</b>) Range estimation. (<b>b</b>) Velocity estimation.</p>
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<p>Complexity comparison. (<b>a</b>) The variation in number of complex multiplications with the number of activated subcarriers. (<b>b</b>) The variation in number of complex multiplications with the number of transmitting antennas.</p>
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<p>The BER performance of different information detection methods under the proposed integrated MIMO-OFDM-IM system (<math display="inline"><semantics> <msub> <mi>N</mi> <mi>r</mi> </msub> </semantics></math> = <math display="inline"><semantics> <msub> <mi>N</mi> <mi>t</mi> </msub> </semantics></math> = 4). (<b>a</b>) <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 3; (<b>b</b>) <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 6.</p>
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<p>The BER performance of different information detection methods under the proposed integrated MIMO-OFDM-IM system (<math display="inline"><semantics> <msub> <mi>N</mi> <mi>r</mi> </msub> </semantics></math> = <math display="inline"><semantics> <msub> <mi>N</mi> <mi>t</mi> </msub> </semantics></math> = 8). (<b>a</b>) <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 3; (<b>b</b>) <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 6.</p>
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<p>The variation in radar–communication trade-off curve with the number of activated subcarriers under different SNRs (<math display="inline"><semantics> <msub> <mi>N</mi> <mi>r</mi> </msub> </semantics></math> = <math display="inline"><semantics> <msub> <mi>N</mi> <mi>t</mi> </msub> </semantics></math> = 4). (<b>a</b>) SNR = 6 dB; (<b>b</b>) SNR = 12 dB.</p>
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20 pages, 1525 KiB  
Article
Evaluation of User-Centric Cell-Free Massive Multiple-Input Multiple-Output Networks Considering Realistic Channels and Frontend Nonlinear Distortion
by Marcin Hoffmann and Paweł Kryszkiewicz
Appl. Sci. 2024, 14(5), 1684; https://doi.org/10.3390/app14051684 - 20 Feb 2024
Cited by 1 | Viewed by 1241
Abstract
Future 6G networks are expected to utilize Massive Multiple-Input Multiple-Output (M-MIMO) and follow a user-centric cell-free (UCCF) architecture. In a UCCF M-MIMO network, the user can be potentially served by multiple surrounding Radio Units (RUs) and Distributed Units (DUs) controlled and coordinated by [...] Read more.
Future 6G networks are expected to utilize Massive Multiple-Input Multiple-Output (M-MIMO) and follow a user-centric cell-free (UCCF) architecture. In a UCCF M-MIMO network, the user can be potentially served by multiple surrounding Radio Units (RUs) and Distributed Units (DUs) controlled and coordinated by a single virtualized Centralized Unit (CU). Moreover, in an M-MIMO network, each transmit frontend is equipped with a Power Amplifier (PA), typically with nonlinear characteristics, that can have a significant impact on the throughput achieved by network users. This work evaluates a UCCF M-MIMO network within an advanced system-level simulator considering multicarrier transmission, using Orthogonal Frequency-Division Multiplexing (OFDM), realistic signal-processing steps, e.g., per resource block scheduling, and a nonlinear radio frontend. Moreover, both idealistic independent and identically distributed (i.i.d.) Rayleigh and 3D ray-tracing-based radio channels are evaluated. The results show that under the realistic radio channel, the novel user-centric network architecture can lead to an almost uniform distribution of user throughput and improve the rate of the users characterized by the worst radio conditions by over 3 times in comparison to a classical, network-centric design. At the same time, the nonlinear characteristics of the PA can cause significant degradation of the UCCF M-MIMO network’s performance when operating close to its saturation power. Full article
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<p>The concept and architecture of a UCCF M-MIMO network.</p>
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<p>A block diagram of the main simulation loop.</p>
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<p>Comparison of RSS averaged over RBs between network-centric and UCCF approaches. The buildings are marked in gray, whereas RUs are marked with black dots (the larger dot corresponds to the macro-RU, whereas the smaller dots correspond to the micro-RUs).</p>
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<p>CDFs depicting the ratio between the RSS averaged over RBs achieved under a UCCF network architecture and that following a network-centric approach, with varying numbers of RUs.</p>
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<p>CDFs depicting the average UE rates for the network-centric and UCCF approaches, with varying numbers of RUs, under the Rayleigh radio channel.</p>
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<p>CDFs depicting the average UE rates for the network-centric and UCCF approaches, with varying numbers of RUs, under the realistic ray-tracer radio channel.</p>
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<p>Comparison of 10th, 50th (median), and 90th percentiles from the distribution of the average UE rate for varying numbers of serving RUs and different radio channel models.</p>
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<p>CDFs depicting the average UE rates for the network-centric and UCCF approaches, with varying numbers of RUs, under the Rayleigh radio channel, considering nonlinear effects.</p>
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<p>CDFs of average UE rates for network-centric and UCCF approaches, with varying numbers of RUs, under the Rayleigh radio channel, considering nonlinear effects.</p>
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17 pages, 2488 KiB  
Article
DMCNet-Pro: A Model-Driven Multi-Pilot Convolution Neural Network for MIMO-OFDM Receivers
by Pengyuan Li, Tianlin Zhu, Yutong Xin, Gang Yuan, Xiong Yu, Zejian Lu, Zili Liu and Qing Yan
Electronics 2024, 13(2), 330; https://doi.org/10.3390/electronics13020330 - 12 Jan 2024
Viewed by 1222
Abstract
Nowadays, wireless communication technology is evolving towards high data rates, a low latency, and a high throughput to meet increasingly complex business demands. Key technologies in this direction include multiple-input multiple-output (MIMO) and orthogonal frequency division multiplexing (OFDM). This research is based on [...] Read more.
Nowadays, wireless communication technology is evolving towards high data rates, a low latency, and a high throughput to meet increasingly complex business demands. Key technologies in this direction include multiple-input multiple-output (MIMO) and orthogonal frequency division multiplexing (OFDM). This research is based on our previous work DMCNet. In this article, we focus on studying the deep learning (DL) application of neural networks to solve the reception of single-antenna OFDM signals. Specifically, in multi-antenna scenarios, the channel model is more complex compared to single-antenna cases. By leveraging the characteristics of DL, such as automatic learning of parameters using deep neural networks, we treat the reception process of MIMO-OFDM signals as a black box and utilize neural networks to accomplish the signal reception task. Moreover, we propose a data-driven multi-pilot convolution neural network for MIMO-OFDM receivers (DMCNet). By incorporating complex convolution and complex fully connected structures, we design a receiver network to recover the transmitted signals from the received signals. We validate the accuracy and robustness of DMCNet under different channel conditions, comparing the bit error rates with different schemes. Additionally, we discuss the factors influencing various channel effects. At the same time, we also propose a model-driven scheme, DMCNet-pro, which has a higher accuracy and fewer parameters in some scenarios. The experimental results demonstrate that the DL-based reception scheme exhibits promising feasibility in terms of accuracy and interference resistance when compared to traditional approaches. Full article
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<p>The link of a DL-based MIMO-OFDM receiver.</p>
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<p>The structure of DMCNet.</p>
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<p>Denoising module structure.</p>
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<p>Pilot processing structure.</p>
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<p>Model-driven MIMO-OFDM receiver.</p>
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<p>Channel estimation and signal detection model.</p>
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<p>Signal detection model.</p>
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<p>BER of MIMO-OFDM fully connected receiver under eight pilot tones.</p>
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<p>BER of MIMO-OFDM fully connected receiver under 32 pilot tones.</p>
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<p>Relationship between prediction length and BER of an MIMO-OFDM fully connected receiver.</p>
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<p>Accruacy comparison of different signal detection algorithms.</p>
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<p>Comparison of data-driven and model-driven results (<b>left</b>) and model-driven Res-Block channel numbers (<b>right</b>).</p>
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33 pages, 22277 KiB  
Article
Novel Hybrid SOR- and AOR-Based Multi-User Detection for Uplink M-MIMO B5G Systems
by Yung-Ping Tu, Pei-Shen Jian and Yung-Fa Huang
Electronics 2024, 13(1), 187; https://doi.org/10.3390/electronics13010187 - 31 Dec 2023
Viewed by 1878
Abstract
The Internet of Things (IoT) is one of the most important wireless sensor network (WSN) applications in 5G systems and requires a large amount of wireless data transmission. Therefore, massive multiple-input multiple-output (M-MIMO) has become a crucial type of technology and trend in [...] Read more.
The Internet of Things (IoT) is one of the most important wireless sensor network (WSN) applications in 5G systems and requires a large amount of wireless data transmission. Therefore, massive multiple-input multiple-output (M-MIMO) has become a crucial type of technology and trend in the future of beyond fifth-generation (B5G) wireless network communication systems. However, as the number of antennas increases, this also causes a significant increase in complexity at the receiving end. This is a challenge that must be overcome. To reduce the BER, confine the computational complexity, and produce a form of detection suitable for 4G and B5G environments simultaneously, we propose a novel multi-user detection (MUD) scheme for the uplink of M-MIMO orthogonal frequency division multiplexing (OFDM) and universal filtered multi-carrier (UFMC) systems that combines the merits of successive over-relaxation (SOR) and accelerated over-relaxation (AOR) named mixed over-relaxation (MOR). Herein, we divide MOR into the initial and collaboration stages. The former will produce the appropriate initial parameters to improve feasibility and divergence risk. Then, the latter achieves rapid convergence and refinement performance through alternating iterations. The conducted simulations show that our proposed form of detection, compared with the BER performance of traditional SOR and AOR, can achieve 99.999% and 99.998% improvement, respectively, and keep the complexity at O(N2). It balances BER performance and complexity with fewer iterations. Full article
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<p>A system block diagram of the OFDM transceiver.</p>
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<p>A system block diagram of the UFMC transceiver.</p>
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<p>A block diagram of the proposed detection scheme.</p>
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<p>An MMSE BER performance comparison for OFDM vs. UFMC with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>64</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math> and <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>.</p>
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<p>A PSD comparison for OFDM vs. UFMC.</p>
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<p>BER performance of MOR method relative to <math display="inline"><semantics> <mi>ω</mi> </semantics></math> with SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>35</mn> </mrow> </semantics></math> dB, <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>64</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and number of iterations <span class="html-italic">i</span> of 4 for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance of MOR method relative to <math display="inline"><semantics> <mi>ω</mi> </semantics></math> with SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>35</mn> </mrow> </semantics></math> dB, <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>64</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and number of iterations <span class="html-italic">i</span> of 4 for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance of MOR method relative to <math display="inline"><semantics> <mi>γ</mi> </semantics></math> with SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>35</mn> </mrow> </semantics></math> dB, <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>64</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and number of iterations <span class="html-italic">i</span> of 4 for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance comparison for different detection methods with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>64</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and number of iterations <span class="html-italic">i</span> of 3, for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance comparison for different detection methods with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>64</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and number of iterations <span class="html-italic">i</span> of 4 for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance comparison for different detection methods with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>128</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and number of iterations <span class="html-italic">i</span> of 2 for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance comparison for different detection methods with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>256</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and number of iterations <span class="html-italic">i</span> of 2 for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>(<b>a</b>) OFDM and (<b>b</b>) UFMC, BER vs. <math display="inline"><semantics> <mi>β</mi> </semantics></math> for different detection schemes when the number of iterations <span class="html-italic">i</span> was 2 and the SNR was 30 dB.</p>
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<p>(<b>a</b>) OFDM and (<b>b</b>) UFMC, BER vs. <math display="inline"><semantics> <mi>β</mi> </semantics></math> for different detection schemes when the number of iterations <span class="html-italic">i</span> was 3 and the SNR was 30 dB.</p>
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<p>BER performance vs. number of iterations with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>64</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>37</mn> </mrow> </semantics></math> dB for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance vs. number of iterations with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>64</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>37</mn> </mrow> </semantics></math> dB for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance vs. number of iterations with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>128</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>33</mn> </mrow> </semantics></math> dB for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance vs. number of iterations with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>128</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>33</mn> </mrow> </semantics></math> dB for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance vs. number of iterations with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>192</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>31</mn> </mrow> </semantics></math> dB for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>BER performance vs. number of iterations with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>R</mi> </msub> <mo>×</mo> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>192</mn> <mo>×</mo> <mn>16</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>K</mi> <mo>=</mo> <mn>8</mn> </mrow> </semantics></math>, and SNR <math display="inline"><semantics> <mrow> <mo>=</mo> <mn>31</mn> </mrow> </semantics></math> dB for (<b>a</b>) OFDM and (<b>b</b>) UFMC.</p>
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<p>Bar chart of computational complexity for different detectors with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>T</mi> </msub> <mo>=</mo> <mn>16</mn> </mrow> </semantics></math>.</p>
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18 pages, 9781 KiB  
Article
A Novel Intrapulse Beamsteering SAR Imaging Mode Based on OFDM-Chirp Signals
by Shenjing Wang, Feng He and Zhen Dong
Remote Sens. 2024, 16(1), 126; https://doi.org/10.3390/rs16010126 - 28 Dec 2023
Cited by 3 | Viewed by 1043
Abstract
The multiple-input multiple-output synthetic aperture radar (MIMO SAR) system has developed rapidly since its discovery. At the same time, the low-disturbance and high-gain requirements of the MIMO system are continuing to increase. Through the application of digital beamforming (DBF) techniques, the multidimensional waveform [...] Read more.
The multiple-input multiple-output synthetic aperture radar (MIMO SAR) system has developed rapidly since its discovery. At the same time, the low-disturbance and high-gain requirements of the MIMO system are continuing to increase. Through the application of digital beamforming (DBF) techniques, the multidimensional waveform encoding (MWE) technique can play a key role in MIMO systems, which can greatly improve the system’s performance, especially the multi-mission capability of radar. Intrapulse beamsteering in elevation is a typical form of multi-dimensional waveform encoding which can greatly improve the transmitting efficiency and multi-mission performance of radar. However, because of the high sensitivity of the DBF technique to height, there is significant deterioration in performance in the presence of terrain undulations. The OFDM (Orthogonal Frequency Division Multiplexing) technique is widely used in communication. Due to the similarity of radar and communication systems and the great waveform diversity of OFDM signals, the OFDM radar has recently begun to emerge as a new radar system, simultaneously, the orthogonality of OFDM signals is in the time and frequency domains, and is not affected by terrain undulation. So, this paper proposes a novel radar mode combining intrapulse beamsteering in elevation and OFDM-Chirp signals, that is, the combination of “beam orthogonality” and “waveform orthogonality”, which can greatly improve the performance and fault tolerance to interference signals. In this manuscript, the system working mode and signal processing flow are introduced in detail, and simulations for both point targets and distributed targets are carried out to verify the feasibility of the proposed mode. Simultaneously, a comparison experiment is carried out, which shows the high level of fault tolerance to terrain undulation and the high potential of the proposed radar mode in Earth observation. Full article
(This article belongs to the Special Issue Radar and Sonar Imaging and Processing IV)
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Graphical abstract

Graphical abstract
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<p>The schematic diagram of intrapulse beamsteering in elevation. A, B and C represents three subpulses.</p>
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<p>A brief geometric model of the antenna.</p>
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<p>Two common frequency division multiplexing modulation methods. (<b>a</b>) the transmitting signals of each channel do not overlap at all; (<b>b</b>) the frequency bands overlap but the frequency points do not overlap.</p>
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<p>Frequency domain generation method of OFDM-Chirp signals.</p>
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<p>Time domain generation method of OFDM-Chirp signals.</p>
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<p>The signal processing flow chart for the receiving end. top: proposed intrapulse beamsteering system using OFDM-Chirp signals; bottom: conventional intrapulse beamsteering system using LFM signals.</p>
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<p>The schematic diagram of circular-shift addition processing.</p>
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<p>The point target simulation results.</p>
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<p>The range and azimuth profile of one point target.</p>
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<p>Distributed target simulation and processing flow chart of intrapulse beamsteering system based on OFDM-Chirp signals.</p>
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<p>Results of distributed target simulation with different transmitting signals: (<b>a</b>) LFM signal; (<b>b</b>) OFDM-Chirp signals; (<b>c</b>) the partial enlargement of the red dotted box on the right.</p>
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<p>Results of distributed target simulation with different transmitting signals: (<b>a</b>) LFM signal; (<b>b</b>) OFDM-Chirp signals; (<b>c</b>) the partial enlargement of the red dotted box on the right.</p>
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16 pages, 680 KiB  
Article
A Novel OFDM-Based Time Domain Quadrature GSM for Visible Light Communication System
by Zichun Shi, Pu Miao, Liyuan Pang and Yudong Zhang
Electronics 2024, 13(1), 71; https://doi.org/10.3390/electronics13010071 - 22 Dec 2023
Cited by 1 | Viewed by 1158
Abstract
In order to improve the spectral efficiency (SE) as well as the receiver performance of band-limited visible light communications (VLCs), two orthogonal frequency division multiplexing (OFDM)-based quadrature generalized multiple-input multiple-output (QG-MIMO) transmission schemes, including time domain (TD) quadrature generalized spatial modulation (TD-QGSM) and [...] Read more.
In order to improve the spectral efficiency (SE) as well as the receiver performance of band-limited visible light communications (VLCs), two orthogonal frequency division multiplexing (OFDM)-based quadrature generalized multiple-input multiple-output (QG-MIMO) transmission schemes, including time domain (TD) quadrature generalized spatial modulation (TD-QGSM) and TD quadrature generalized spatial multiplexing (TD-QGSMP), are proposed in this paper. Firstly, the constellation symbols in the frequency domain are split into in-phase and quadrature components to perform the OFDM modulation separately. Then, the corresponding time domain signal is spatially mapped on different light emitting diodes (LEDs) for achieving the diversity or multiplexing. In addition, we also propose an illegal vector correction (IVC)-based orthogonal matching pursuit (OMP) detection algorithm to deal with the error propagation and noise amplification effect, where a novel correction criterion is involved for assisting the index vectors estimation and thus for improving the demodulation performance. The simulation results demonstrate that the SE can be significantly improved by the proposed schemes as compared with the existing OFDM-based generalized MIMO schemes, with the TD-QGSM increasing by at least 56.5% and the TD-QGSMP increasing by at least 72.3%. Moreover, the bit error rate (BER) performance can be further improved when applying the proposed IVC-OMP detection method, which outperforms the traditional maximum-likelihood and maximum ratio combining (ML-MRC) detection by at least 62.5%. Full article
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<p>Geometric setup of a general indoor VLC-MIMO system.</p>
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<p>Schematic diagram of TD-QGSM.</p>
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<p>Schematic diagram of TD-QGSMP.</p>
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<p>SE performance comparison for <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>.</p>
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<p>SE performance comparison for <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math>.</p>
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<p>BER performance comparison for <math display="inline"><semantics> <mrow> <mi>S</mi> <mi>E</mi> </mrow> </semantics></math> = 4 bits/s/Hz and <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>.</p>
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<p>BER performance comparison for <math display="inline"><semantics> <mrow> <mi>S</mi> <mi>E</mi> </mrow> </semantics></math> = 6 bits/s/Hz and <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>.</p>
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<p>BER performance comparison for different generalized MIMO schemes in the case of <math display="inline"><semantics> <mrow> <mi>M</mi> <mo>=</mo> <mn>64</mn> </mrow> </semantics></math>.</p>
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<p>BER performance comparison for different generalized MIMO schemes in the case of <math display="inline"><semantics> <mrow> <mi>M</mi> <mo>=</mo> <mn>256</mn> </mrow> </semantics></math>.</p>
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<p>BER performance comparison under different detection methods for <math display="inline"><semantics> <mrow> <mi>N</mi> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>.</p>
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