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Trends and Prospects in Applied Electromagnetics

A special issue of Applied Sciences (ISSN 2076-3417). This special issue belongs to the section "Electrical, Electronics and Communications Engineering".

Deadline for manuscript submissions: 20 May 2025 | Viewed by 14919

Special Issue Editors

School of Mechanical and Electrical Engineering, University of Electronic Science and Technology, Chengdu 611731, China
Interests: eddy current technique; microwave nondestructive imaging; RFID sensing and monitoring; imaging processing; structural health monitoring; computational electromagnetics
School of Mechanical and Electrical Engineering, University of Electronic Science and Technology, Chengdu 611731, China
Interests: electromagnetic compatibility; computational electromagnetics; signal and power integrity; multiphysics; bioelectromagnetics

Special Issue Information

Dear Colleagues,

We are inviting submissions to the Special Issue on the “Trends and Prospects in Applied Electromagnetics”. Electromagnetics is widely applied in various fields, such as communication, navigation, radar, measurement and instrument, as well as in electric vehicles. This Special Issue is focued on, but not limited to: advanced electromagnetic materials, such as metamaterials; electromagnetic theories, including transmission, propogation, radiation and scattering theory; nondestructive testing and evaluation, including eddy current technique, magnetic flux linkage technique, Buckhausen noise method, alternative current field measurement, and so on; computational electromagnetics, including techniques in optimization and error minimization, innovations in solution technique, and applications for electromagnetics modeling techniques; electromgantic sensing and imaging, including microwave and millimeter-wave imaging, radar imaging, RF and wireless communication and sensing, as well as THz imaging; electromagnetic compatibility and interference, including EMC and EMI modeling; EMC standards, methods of EMC measurements and signal and power integrity; as well as electromagnetic application in IOTs.

In this Special Issue, we invite submissions exploring cutting-edge research and recent advances in the fields of applied electromagnetics. Theoretical, numerical and experimental studies are welcome, as well as comprehensive review and survey papers.

Dr. Yating Yu
Dr. Baolin Nie
Guest Editors

Manuscript Submission Information

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Submitted manuscripts should not have been published previously, nor be under consideration for publication elsewhere (except conference proceedings papers). All manuscripts are thoroughly refereed through a single-blind peer-review process. A guide for authors and other relevant information for submission of manuscripts is available on the Instructions for Authors page. Applied Sciences is an international peer-reviewed open access semimonthly journal published by MDPI.

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Keywords

  • simulation and modelling
  • nondestructive testing and evaluation
  • eletromanetic imaging
  • electromagnetic compatibility (EMC)
  • electromagnetic interference (EMI)
  • RF and wireless communication
  • electromagnetic signal processing
  • IOTs and AloTs

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Published Papers (9 papers)

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Research

14 pages, 771 KiB  
Article
Nonlinear Analysis and Solution for an Overhead Line Magnetic Energy Harvester with an Active Rectifier
by Alexander Abramovitz, Moshe Shvartsas and Alon Kuperman
Appl. Sci. 2024, 14(23), 11178; https://doi.org/10.3390/app142311178 (registering DOI) - 29 Nov 2024
Abstract
Recently, there has been a significant focus on developing various energy harvesting technologies to power remote electronic sensors, data loggers, and communication devices for smart grid systems. Among these technologies, magnetic energy harvesting stands out as one straightforward method to extract substantial power [...] Read more.
Recently, there has been a significant focus on developing various energy harvesting technologies to power remote electronic sensors, data loggers, and communication devices for smart grid systems. Among these technologies, magnetic energy harvesting stands out as one straightforward method to extract substantial power from current-carrying overhead lines. Due to the relatively small size of the harvester, the high currents in the distribution system quickly saturate its magnetic core. Consequently, the magnetic harvester operates in a highly nonlinear manner. The nonlinear nature of the downstream AC to DC converters further complicates the process, making precise analytical modeling a challenging task. In this paper, a clamped type overhead line magnetic energy harvester with a controlled active rectifier generating significant DC output power is investigated. A piecewise nonlinear analytical model of the magnetic harvester is derived and reported. The modeling approach is based on the application of the Froelich equation. The chosen approximation method allowed for a complete piecewise nonlinear analytical treatise of the harvester’s behavior. The main findings of this study include a closed-form solution that accounts for both the core and rectifiers’ nonlinearities and provides an accurate quantitative prediction of the harvester’s key parameters such as the transfer window width, optimal pulse location, average DC output current, and average output power. To facilitate the study, a nonlinear model of the core was developed in simulation software, based on parameters extracted from core experimental data. Furthermore, theoretical predictions were verified through comparison with a computer simulation and experimental results of a laboratory prototype harvester. Good agreement between the theoretical, simulation, and experimental results was found. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
23 pages, 14830 KiB  
Article
Electromagnetic Interference Shielding Analysis of Hybrid Buckypaper-Reinforced Polymer Matrix Composites: A Quantum Tunneling-Informed Equivalent Circuit Approach
by Kartik Tripathi, Mohamed H. Hamza, Madeline A. Morales, Todd C. Henry, Asha Hall and Aditi Chattopadhyay
Appl. Sci. 2024, 14(19), 8960; https://doi.org/10.3390/app14198960 - 4 Oct 2024
Viewed by 993
Abstract
A novel modeling approach is developed for investigating the effectiveness of buckypaper (BP), a porous membrane made of a highly cross-linked network of carbon nanotubes, in improving the electromagnetic interference (EMI) shielding properties of carbon fiber-reinforced polymer (CFRP) composites. The methodology uses quantum [...] Read more.
A novel modeling approach is developed for investigating the effectiveness of buckypaper (BP), a porous membrane made of a highly cross-linked network of carbon nanotubes, in improving the electromagnetic interference (EMI) shielding properties of carbon fiber-reinforced polymer (CFRP) composites. The methodology uses quantum tunneling-based equivalent electrical circuits and Monte Carlo simulations to predict the frequency-dependent electrical conductivity and EMI shielding effectiveness (SE) of the hybrid BP/CFRP composites. The study examines a signal frequency range of 50 MHz to 12 GHz that includes the very high and X-band. The results show that at a frequency of 12 GHz, the transverse conductivity increases to approximately 12.67 S/m, while the longitudinal conductivity decreases to about 3300 S/m from an initial value of 40,000 S/m. These results are then integrated into the ANSYS High-Frequency Structure Simulator to predict SE by simulating the propagation of electromagnetic waves through a semi-infinite composite shield element. The numerical simulations illustrate that incorporating BP significantly improves the SE of CFRP composites beyond 2 GHz owing to its high conductivity in that frequency range. For instance, at 12 GHz signal frequency, adding a single BP interleaf enhances the SE of a [90, 0] laminate by up to ~64%. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
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Figure 1
<p>Hybrid laminate schematic showing BP microstructure obtained through SEM [<a href="#B17-applsci-14-08960" class="html-bibr">17</a>].</p>
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<p>Microstructure of a unidirectional CFRP lamina and its equivalent electrical circuit in the longitudinal direction consisting of the <span class="html-italic">N</span> fibers, each having their own resistance (<math display="inline"><semantics> <mrow> <msub> <mrow> <mi>R</mi> </mrow> <mrow> <mi>f</mi> </mrow> </msub> </mrow> </semantics></math>) and inductance (<math display="inline"><semantics> <mrow> <msub> <mrow> <mi>L</mi> </mrow> <mrow> <mi>f</mi> </mrow> </msub> </mrow> </semantics></math>).</p>
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<p>(<b>a</b>) Magnetic fields due to parallel fibers separated by a distance d and (<b>b</b>) color-coded magnetic field vectors due to the current carrying neighboring fibers.</p>
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<p>(<b>a</b>) Transverse microstructure showing the fiber distribution used for estimating the overall inductance, (<b>b</b>) Interconnected RVE with straight line connections between pairs of fibers within the threshold distance.</p>
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<p>Transverse conductivity model outline.</p>
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<p>Fiber pair schematic with an enlarged view of the contact region showing the wave functions (<math display="inline"><semantics> <mrow> <mi>Ψ</mi> </mrow> </semantics></math>) for different regions along the particle tunneling path.</p>
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<p>(<b>a</b>) Equivalent circuit of a fiber–fiber contact pair and its equivalent contact impedance (<math display="inline"><semantics> <mrow> <msub> <mrow> <mi>Z</mi> </mrow> <mrow> <mi>c</mi> </mrow> </msub> </mrow> </semantics></math>) and (<b>b</b>) contact region discretization for determining effective contact resistance (<math display="inline"><semantics> <mrow> <msub> <mrow> <mi>R</mi> </mrow> <mrow> <mi>c</mi> </mrow> </msub> </mrow> </semantics></math>) and capacitance (<math display="inline"><semantics> <mrow> <msub> <mrow> <mi>C</mi> </mrow> <mrow> <mi>c</mi> </mrow> </msub> </mrow> </semantics></math>).</p>
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<p>Schematic showing the fiber contact length (<math display="inline"><semantics> <mrow> <msub> <mrow> <mi>l</mi> </mrow> <mrow> <mi>c</mi> </mrow> </msub> </mrow> </semantics></math>) due to fiber waviness.</p>
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<p>Quantum tunneling schematic including tunneling probabilities <math display="inline"><semantics> <mrow> <msub> <mrow> <msub> <mrow> <mo>(</mo> <mi>P</mi> </mrow> <mrow> <mi>l</mi> <mi>i</mi> <mi>n</mi> <mi>k</mi> </mrow> </msub> <mo>)</mo> </mrow> <mrow> <mi>n</mi> </mrow> </msub> </mrow> </semantics></math> and resistance across the <math display="inline"><semantics> <mrow> <msup> <mrow> <mi>n</mi> </mrow> <mrow> <mi>t</mi> <mi>h</mi> </mrow> </msup> </mrow> </semantics></math> fiber cross-section <math display="inline"><semantics> <mrow> <msub> <mrow> <msub> <mrow> <mo>(</mo> <mi>R</mi> </mrow> <mrow> <mi>f</mi> <mi>t</mi> </mrow> </msub> <mo>)</mo> </mrow> <mrow> <mi>n</mi> </mrow> </msub> </mrow> </semantics></math> for the shortest conductive path.</p>
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<p>Waveguide model schematic showing the composite sample under study.</p>
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<p>(<b>a</b>) Longitudinal CFRP conductivity declining at higher frequencies due to the rise of inductive reactance and (<b>b</b>) shift in conductivity decline point for different square ply sizes showing an early decline in conductivity in larger plies.</p>
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<p>Overall inductance versus number of fibers on a log–log scale showing the saturation of the induction.</p>
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<p>Tunneling probability versus signal frequency for different barrier sizes.</p>
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<p>Tunneling probability versus signal frequency for different fiber contact lengths (contact length shown as a percentage of the entire fiber length).</p>
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<p>Transverse conductivity with a 95% confidence interval obtained from the quantum tunneling-based Monte Carlo simulations.</p>
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<p>Shielding effectiveness in the 50 MHz–12 GHz frequency range for (<b>a</b>) buckypaper (BP), (<b>b</b>) [90,0], (<b>c</b>) [BP,90,0], (<b>d</b>) [90,BP,0], and (<b>e</b>) [90,0,BP].</p>
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<p>Effect of ply orientation on the shielding effectiveness: (<b>a</b>) [90,BP,0], (<b>b</b>) [45,BP,0], and (<b>c</b>) [0,BP,0].</p>
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<p>Effect of buckypaper (BP) on the shielding effectiveness of a 12-ply laminate showing the percentage enhancement in SE by incorporating BP.</p>
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<p>Comparison between the shielding effectiveness exhibited by composites with buckypaper (BP) and copper mesh interleaves [<a href="#B24-applsci-14-08960" class="html-bibr">24</a>].</p>
Full article ">Figure A1
<p>The wave function in the three different regions.</p>
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19 pages, 2721 KiB  
Article
Observations about Propagation, Attenuation, and Radiation of EMI from HVDC Converter Stations
by John B. Schneider and Robert G. Olsen
Appl. Sci. 2024, 14(15), 6740; https://doi.org/10.3390/app14156740 - 1 Aug 2024
Viewed by 1338
Abstract
The electromagnetic interference (EMI) generated by switching operations within high-voltage DC (HVDC) converter stations is an issue that has been addressed by CIGRE, and methods to manage EMI should be considered in the design phase using electromagnetic modeling techniques. It is shown that [...] Read more.
The electromagnetic interference (EMI) generated by switching operations within high-voltage DC (HVDC) converter stations is an issue that has been addressed by CIGRE, and methods to manage EMI should be considered in the design phase using electromagnetic modeling techniques. It is shown that the methods of the moments-based techniques that have been used in many previous studies may not be sufficient. Here, a finite-difference time-domain method is used to study the properties of single switching events using a realistic model of an HVDC converter station with a special emphasis on determining the impact of the valve hall on shielding EMI. It is shown that the valve hall does not confine high-frequency electromagnetic fields to the valve hall; rather, it delays them from exiting through bushings in the wall and spreads them out in time. Further, it is shown that incorporating electromagnetic absorbing material into the valve hall’s design can significantly reduce EMI outside the converter station. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
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Figure 1
<p>Computational domain showing (<b>a</b>) a projection onto the <math display="inline"><semantics> <mrow> <mi>x</mi> <mi>y</mi> </mrow> </semantics></math> plane, (<b>b</b>) projection onto the <math display="inline"><semantics> <mrow> <mi>x</mi> <mi>z</mi> </mrow> </semantics></math> plane, and (<b>c</b>) an oblique perspective view. The red lines represent conductors, the shaded box corresponds to the valve hall, and the green-shaded plane on which the hall sits is a perfectly conducting ground plane.</p>
Full article ">Figure 2
<p>The log magnitude of the electric field measured inside and outside the valve hall when (<b>a</b>) 2 m segments of the conductors that nominally pass through the valve hall walls are removed and when (<b>b</b>) the conductors that pass through the walls are intact.</p>
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<p>The log magnitude of the spectral content of the <math display="inline"><semantics> <msub> <mi>E</mi> <mi>z</mi> </msub> </semantics></math> component of the field, measured at two points when (<b>a</b>) the observation points are inside and outside the valve hall. The reference curve shows the Fourier transform of the source function. (<b>b</b>) Fields at the observations points normalized by the source function. (<b>c</b>) The valve hall has been removed, with no other changes to the simulation.</p>
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<p>The log magnitude of the normalized spectrum of the current measured at two points along the top-most line from the valve hall to the DC hall. (<b>a</b>) The hall is present. (<b>b</b>) The hall has been removed.</p>
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<p>The electric field magnitude measured approximately 200 m from the converter station. (<b>a</b>) Field observed when the valve hall is and is not present. (<b>b</b>) Fields observed when there is and is not a lossy dielectric slab placed in the valve hall.</p>
Full article ">Figure 6
<p>The normalized spectrum of the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>x</mi> </msub> </semantics></math> field (in dB), measured approximately 200 m from the valve hall. The results are shown for an intact valve hall, when no valve hall is present, and when the valve hall is intact but contains a lossy dielectric slab.</p>
Full article ">
15 pages, 4820 KiB  
Article
An S–K Band 6-Bit Digital Step Attenuator with Ultra Low Insertion Loss and RMS Amplitude Error in 0.25 μm GaAs p-HEMT Technology
by Quanzhen Liang, Kuisong Wang, Xiao Wang, Yuepeng Yan and Xiaoxin Liang
Appl. Sci. 2024, 14(9), 3887; https://doi.org/10.3390/app14093887 - 1 May 2024
Cited by 1 | Viewed by 3092
Abstract
This paper presents an ultra-wideband, low insertion loss, and high accuracy 6-bit digital step attenuator (DSA). To improve the accuracy of amplitude and phase shift of the attenuator, two innovative compensation structures are proposed in this paper: a series inductive compensation structure (SICS) [...] Read more.
This paper presents an ultra-wideband, low insertion loss, and high accuracy 6-bit digital step attenuator (DSA). To improve the accuracy of amplitude and phase shift of the attenuator, two innovative compensation structures are proposed in this paper: a series inductive compensation structure (SICS) designed to compensate for high frequency attenuation values and a small bit compensation structure (SBCS) intended for large attenuation bits. Additionally, we propose insertion loss reduction techniques (ILRTs) to reduce insertion loss. The fabricated 6-bit DSA core area is only 0.51 mm2, and it exhibits an attenuation range of 31.5 dB in 0.5 dB steps. Measurements reveal that the root-mean-square (RMS) attenuation and phase errors for the 64 attenuation states are within 0.18 dB and 7°, respectively. The insertion loss is better than 2.54 dB; the return loss is better than −17 dB; and the input 1 dB compression point (IP1 dB) is 29 dBm at IF 12 GHz. To the best of our knowledge, this chip presents the highest attenuation accuracy, the lowest insertion loss, the best IP1dB, and a good matching performance in the range of 2–22 GHz using the 0.25 μm GaAs p-HEMT process. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
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Figure 1

Figure 1
<p>Topologies of DSAs. (<b>a</b>) Switched path attenuator. (<b>b</b>) Distributed attenuator. (<b>c</b>) Switched T/π attenuators.</p>
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<p>(<b>a</b>) Schematic diagram of the conventional T-type attenuation structure and its equivalent circuits. (<b>b</b>) Reference state. (<b>c</b>) Attenuation state.</p>
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<p>(<b>a</b>) Schematic diagram of the simplified T-type attenuation structure and its equivalent circuits. (<b>b</b>) Reference state. (<b>c</b>) Attenuation state.</p>
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<p>(<b>a</b>) Schematic diagram of the π-type attenuation structure and its equivalent circuits. (<b>b</b>) Reference state. (<b>c</b>) Attenuation state.</p>
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<p>(<b>a</b>) Schematic diagram of the modified π-type attenuator and its equivalent circuits. (<b>b</b>) Reference state. (<b>c</b>) Attenuation state.</p>
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<p>Simulated (<b>a</b>) relative attenuation and (<b>b</b>) additional phase shift using SICS for different <span class="html-italic">Ls</span> values.</p>
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<p>Schematic of 16 dB attenuator with small bit compensation structure.</p>
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<p>Simulation results of conventional structure and SBCS. (<b>a</b>) Relative attenuation and (<b>b</b>) return loss.</p>
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<p>Comparison of insertion loss between T-type and simplified T-type attenuators.</p>
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<p>(<b>a</b>) π-structure with low-pass inductive compensation and its equivalent circuit. (<b>b</b>) Reference state.</p>
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<p>Comparison of insertion loss between the π-type attenuator before and after using low-pass inductive compensation structure.</p>
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<p>Schematic of the 6-bit DSA.</p>
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<p>Micrograph of the proposed 6-bit DSA.</p>
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<p>(<b>a</b>) Measured relative attenuation. (<b>b</b>) Simulated and measured RMS amplitude and phase errors. (<b>c</b>) Simulated and measured insertion loss. (<b>d</b>) Measured input return loss. (<b>e</b>) Measured output return loss. (<b>f</b>) Simulated and measured IP1 dB at 12 GHz.</p>
Full article ">
19 pages, 4632 KiB  
Article
Compliance Assessment of the Spatial Averaging Method for Magnetic Field Leakage from a Wireless Power Transfer System in Electric Vehicles
by Masanori Okada, Keishi Miwa, Sachiko Kodera and Akimasa Hirata
Appl. Sci. 2024, 14(7), 2672; https://doi.org/10.3390/app14072672 - 22 Mar 2024
Cited by 1 | Viewed by 1087
Abstract
Wireless power transfer (WPT) via magnetic resonance offers efficient electrical power transfer, making it an increasingly attractive option for charging electric vehicles (EVs) without conventional plugs. However, EV charging requires a transfer power in order of kW or higher, resulting in a higher-leaked [...] Read more.
Wireless power transfer (WPT) via magnetic resonance offers efficient electrical power transfer, making it an increasingly attractive option for charging electric vehicles (EVs) without conventional plugs. However, EV charging requires a transfer power in order of kW or higher, resulting in a higher-leaked magnetic field than conventional wireless systems. The leaked magnetic field is nonuniform, and the assessment in terms of the limit prescribed in the guideline is highly conservative because it assumes that a person standing in free space is exposed to a uniform field. In such cases, an assessment should be performed using the limits of the internal electric field, as it is more relevant to the adverse health effects, whereas its evaluation is time-consuming. To mitigate this over-conservativeness, international product standards introduce a spatial averaging method for nonuniform exposure assessment. In this study, we investigate assessment methods, especially for measurement points of nonuniform magnetic field strength leaked from the WPT system. Various spatial averaging methods are correlated with the internal electric field derived from electromagnetic field analysis using an anatomically based human body model. Our computational results confirm a good correlation between the spatially averaged magnetic and internal electric fields. Additionally, these methods provide an appropriate compliance assessment with the exposure guidelines. This study advances our understanding of the suitability of spatial averaging methods for nonuniform exposure and contributes to the smooth assessment in WPT systems. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
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Figure 1
<p>Japanese adult male model TARO: (<b>a</b>) standing and (<b>b</b>) sitting postures.</p>
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<p>Schematic of WPT coils (unit: mm): (<b>a</b>) transmitting coils, (<b>b</b>) receiving coils, and (<b>c</b>) positions.</p>
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<p>Cross-section of the vehicle model (unit: mm): (<b>a</b>) side view and (<b>b</b>) top view. <span class="html-italic">y</span><sub>s</sub> represents the distance in the front–back direction starting from the seat position of the vehicle.</p>
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<p>Measurement points outlined in each definition for outside and inside the vehicle body (unit: m).</p>
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<p>Distributions of the magnetic field outside the vehicle with different materials: (<b>a</b>) iron and (<b>b</b>) CFRP.</p>
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<p>Distributions of the magnetic field inside the vehicle with different materials: (<b>a</b>) iron and (<b>b</b>) CFRP.</p>
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<p>Internal electric field distributions in standing human body model outside the vehicle with different materials: (<b>a</b>) iron and (<b>b</b>) CFRP.</p>
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<p>Internal electric field distributions in human body model inside the vehicle sitting on the driver’s seat for different materials: (<b>a</b>) iron and (<b>b</b>) CFRP.</p>
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<p>Assessment of three definitions for the ICNIRP guidelines and IEEE standard in terms of <span class="html-italic">a<sub>c</sub></span> outside the vehicle with different materials.</p>
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<p>Correlation between the maximum internal electric field and magnetic field strength for different vehicle seat positions: (<b>a</b>) whole-body <span class="html-italic">H</span><sub>ave</sub>, (<b>b</b>) 1-Point <span class="html-italic">H</span>, and (<b>c</b>) 3 or 4-Point <span class="html-italic">H</span><sub>ave</sub>. R<sup>2</sup> represents the coefficient of determination. (<b>a</b>) was evaluated in the volume where the human body model exists in realistic posture (the number of voxels was 8,193,397).</p>
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<p>Assessment of three definitions for the ICNIRP guidelines and IEEE standard in terms of <span class="html-italic">a<sub>c</sub></span> inside the vehicle with different materials.</p>
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<p>Variation of the compliance assessment for each definition when the vehicle seat position was changed in the front–back direction with the vehicle body made of (<b>a</b>) iron and (<b>b</b>) CFRP.</p>
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10 pages, 890 KiB  
Communication
A Filtering Switch Made by an Improved Coupled Microstrip Line
by Xiangsuo Fan, Xiaokang Chen, Wenhao Xu, Lingping Feng, Ling Yu and Haohao Yuan
Appl. Sci. 2023, 13(13), 7886; https://doi.org/10.3390/app13137886 - 5 Jul 2023
Viewed by 1192
Abstract
In this paper, we propose a new filtering switch with excellent working performance made using an optimized coupled microstrip line. Upon analyzing the RF (radio frequency) front-end’s system structure, the switching device was simplified to a diode, which was connected to the microstrip [...] Read more.
In this paper, we propose a new filtering switch with excellent working performance made using an optimized coupled microstrip line. Upon analyzing the RF (radio frequency) front-end’s system structure, the switching device was simplified to a diode, which was connected to the microstrip circuit we designed to become a filter switch with both filtering and shutdown functions. First, we obtained an equivalent schematic of this filtering switch based on the relevant microstrip line theory. This switch consists of two coupled microstrip circuits, parallel-coupled feed lines and coupled-line stub-load resonators (CLSs), and a PIN diode. Second, the operating principle is described by the switching of the operating states, with ideal shutdown performance in the off state and considerable selectivity and excellent out-of-band rejection performance in the filtered state. Finally, a prototype filtering switch with a center frequency of 0.8 GHz was designed and tested. After subsequent optimization and improvement, the simulation and test performance results were noticeably consistent, consequently verifying the performance requirements of this filtering switch in two operating states in the center frequency band. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
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Figure 1
<p>RF (radio frequency) front-end system diagram.</p>
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<p>Parallel-coupled feed lines (<b>left</b>); coupled-line stub-loaded resonators (<b>right</b>).</p>
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<p>Equivalent circuit schematic.</p>
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<p>Equivalent circuit of Skyworks SMP1345-079LF PIN diode.</p>
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<p>Filtering switch’s physical layout.</p>
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<p>Photograph of the fabricated filtering switch.</p>
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<p>Simulated and actual measured filtering switch S-parameters’ (<b>a</b>) on state (<b>b</b>) off state.</p>
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<p>Simulated and actual measured filtering switch S-parameters’ (<b>a</b>) on state (<b>b</b>) off state.</p>
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17 pages, 6645 KiB  
Article
Design of a Novel Ultra-Wideband Common-Mode Filter Using a Magnified Coupled Defected Ground Structure
by Ding-Bing Lin, Mei-Hui Wang, Aloysius Adya Pramudita and Tjahjo Adiprabowo
Appl. Sci. 2023, 13(13), 7404; https://doi.org/10.3390/app13137404 - 22 Jun 2023
Cited by 2 | Viewed by 1543
Abstract
An ultra-wideband common-mode (CM) filter for a gigahertz (GHz) data rate signal is proposed in this paper. The proposed filter was designed only on the printed circuit board (PCB) ground plane; no additional components wererequired. We took advantage of producing second-order transmission zero [...] Read more.
An ultra-wideband common-mode (CM) filter for a gigahertz (GHz) data rate signal is proposed in this paper. The proposed filter was designed only on the printed circuit board (PCB) ground plane; no additional components wererequired. We took advantage of producing second-order transmission zero by an asymmetrical magnified coupled DGS to extend the suppression bandwidth. Full-wave simulations and equivalent circuit models of the DGS resonator were established to predict the suppression performance. The measured differential-mode insertion loss (Sdd21) from direct current (DC) to 12.35 GHz was obtained within the −3 dB definitionin the frequency domain. The CM noise was suppressed by more than10 dB in the frequency range from 2.9 GHz to 16.2 GHz. The fractional bandwidth (FBW) reached 139.3%. The proposed filter blocked 62.3% of the CM noise magnitude in the time domain measurement. In addition, the eye diagram measurement proved that good transmission quality was maintained. The proposed filter can be widely implemented to reduce electromagnetic interference (EMI) in radio frequency (RF) andWi-Fi (wireless fidelitystandard) 5 and 6E wireless communication applications. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
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<p>PCB side view.</p>
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<p>PCB top view.</p>
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<p>Full-wave simulated insertion loss for the Left DGS.</p>
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<p>Full-wave simulated insertion loss for the Right DGS.</p>
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<p>Full-wave-simulated insertion loss for the proposed suppression filter.</p>
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<p>The parallel LC-equivalent circuit model of the Left DGS.</p>
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<p>S-parameter of equivalent circuit model and full-wave simulation for the Left DGS.</p>
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<p>The parallel LC-equivalent circuit model of the Right DGS.</p>
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<p>S-parameter of equivalent circuit model and full-wave simulation for the Right DGS.</p>
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<p>The single-ended microstrip line model.</p>
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<p>The S21 simulation of the single-ended microstrip line model.</p>
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<p>The equivalent circuit model of the proposed suppression filter.</p>
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<p>S-parameter of equivalent circuit model and full-wave simulation for the proposed filter.</p>
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<p>Photographs of the fabricated prototype: (<b>a</b>) the reference board and (<b>b</b>) the proposed filter board.</p>
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<p>Photographs of the fabricated prototype with a 5 mm delay line: (<b>a</b>) the reference board and (<b>b</b>) the proposed filter board.</p>
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<p>S-parameter of measurements and full-wave simulation.</p>
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<p>Measurement of the eye diagrams: (<b>a</b>) the reference board and (<b>b</b>) the proposed suppression filter board.</p>
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<p>Measurements of CM noise magnitude.</p>
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21 pages, 12662 KiB  
Article
Design of N-Way Wilkinson Power Dividers with New Input/Output Arrangements for Power-Halving Operations
by Ceyhun Karpuz, Mehmet Cakir, Ali Kursad Gorur and Adnan Gorur
Appl. Sci. 2023, 13(11), 6852; https://doi.org/10.3390/app13116852 - 5 Jun 2023
Cited by 1 | Viewed by 3225
Abstract
In this paper, new single/double-layer N-way Wilkinson power dividers (WPDs) were designed by using slow-wave structures such as narrow-slit-loaded and meandered transmission lines. For size reduction, the slit-loaded and meandered lines were used instead of the quarter-wavelength transmission lines of a conventional WPD. [...] Read more.
In this paper, new single/double-layer N-way Wilkinson power dividers (WPDs) were designed by using slow-wave structures such as narrow-slit-loaded and meandered transmission lines. For size reduction, the slit-loaded and meandered lines were used instead of the quarter-wavelength transmission lines of a conventional WPD. Based on the proposed approaches, two-, four-, and eight-way power dividers were designed, simulated, and fabricated. The fabricated 2-, 4-, and 8-way circuits were measured at the center frequencies of 2.03, 1.77, and 1.73 GHz, which are in excellent agreement with the predicted ones. The meandered transmission lines were also used to design WPD types with novel input/output port arrangements. For this purpose, two three-way WPDs were located on both sides of the same board to have different power-splitting ratios at different inputs and outputs in order to provide alternative solutions for antenna arrays. Furthermore, a five-way dual-layer WPD was introduced by locating the meandered transmission lines into two layers. The most important advantage of the proposed 3- and 5-way WPDs is that they allowed the input power at the next output port to be halved, in the order of P/2, P/4, P/8, P/16, and P/16. All the designed power-halving WPDs were simulated, fabricated, and successfully tested. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
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<p>(<b>a</b>) Equivalent circuit model of a 2-way WPD. (<b>b</b>) Equivalent circuit model for the calculation of S<sub>11</sub>.</p>
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<p>(<b>a</b>) Equivalent circuit model for the calculation of S<sub>32</sub>. (<b>b</b>) Even-mode half-circuit model. (<b>c</b>) Odd-mode half-circuit model.</p>
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<p>(<b>a</b>) Equivalent circuit model for the calculation of S<sub>32</sub>. (<b>b</b>) Even-mode half-circuit model. (<b>c</b>) Odd-mode half-circuit model.</p>
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<p>Conventional 1-to-N-way WPD.</p>
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<p>Conventional cascaded WPDs: (<b>a</b>) 2-way; (<b>b</b>) 4-way; (<b>c</b>) 8-way.</p>
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<p>Slow-wave structures. (<b>a</b>) Slit-loaded. (<b>b</b>) Meandered. (<b>c</b>) Interdigital.</p>
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<p>(<b>a</b>) Conventional 2-way WPD-loading with narrow slits, and (<b>b</b>) location of the isolation resistor.</p>
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<p>(<b>a</b>) Effects of narrow slits on the frequency response. (<b>b</b>) Effects of locations of the isolation resistor on the frequency response.</p>
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<p>(<b>a</b>) Four-way WPD loading with narrow slits. (<b>b</b>) Eight-way WPD loading with narrow slits.</p>
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<p>Meandered line model.</p>
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<p>(<b>a</b>) Conventional 2-way WPD having meandered transmission lines. (<b>b</b>) Effects of WPD meandering on the frequency response.</p>
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<p>Conventional WPDs with meandered transmission lines: (<b>a</b>) 4-way; (<b>b</b>) 8-way.</p>
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<p><b>(a)</b> Two 3-way WPDs with different inputs and outputs: (<b>b</b>) simulation results, (<b>c</b>) magnitude differences of S-parameters, and (<b>d</b>) phase responses.</p>
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<p><b>(a)</b> Two 3-way WPDs with different inputs and outputs: (<b>b</b>) simulation results, (<b>c</b>) magnitude differences of S-parameters, and (<b>d</b>) phase responses.</p>
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<p>(<b>a</b>) Two 3-way WPDs with a common ground plane: (<b>b</b>) simulation results, (<b>c</b>) magnitude differences of S-parameters, and (<b>d</b>) phase responses.</p>
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<p>(<b>a</b>) Two 3-way WPDs with a common ground plane: (<b>b</b>) simulation results, (<b>c</b>) magnitude differences of S-parameters, and (<b>d</b>) phase responses.</p>
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<p>(<b>a</b>) Layout of a 5-way dual-layer WPD: (<b>b</b>) simulation results, (<b>c</b>) magnitude differences of S-parameters, and (<b>d</b>) phase responses.</p>
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<p>(<b>a</b>) Layout of a 5-way dual-layer WPD: (<b>b</b>) simulation results, (<b>c</b>) magnitude differences of S-parameters, and (<b>d</b>) phase responses.</p>
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<p>Photographs of N-way WPDs with narrow-slit-loaded transmission lines: (<b>a</b>) 2-way; (<b>b</b>) 4-way; and (<b>c</b>) 8-way.</p>
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<p>Measurement setup for an 8-way WPD.</p>
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<p>Comparison of the measured and simulated results of the WPDs having narrow-slit-loaded transmission lines for a (<b>a</b>) 2-way WPD; (<b>b</b>) 4-way WPD; and (<b>c</b>) 8-way WPD.</p>
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<p>Meandered transmission line-based WPDs: (<b>a</b>) 2-way, (<b>b</b>) 4-way, and (<b>c</b>) 8-way.</p>
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<p>(<b>a</b>) Comparison of the measured and simulated results of the WPDs having meandered transmission lines for a 2-way WPD; (<b>b</b>) magnitude differences of S-parameters for a 2-way WPD; and (<b>c</b>) phase responses.</p>
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<p>(<b>a</b>) Comparison of the measured and simulated results of the WPDs having meandered transmission lines for a 4-way WPD; (<b>b</b>) magnitude differences of S-parameters for a 4-way WPD; and (<b>c</b>) phase responses.</p>
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<p>(<b>a</b>) Comparison of the measured and simulated results of the WPDs having meandered transmission lines for an 8-way WPD; (<b>b</b>) magnitude differences of S-parameters; and (<b>c</b>) phase responses.</p>
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<p>(<b>a</b>) Photograph of the meandered transmission lines based on two three-way WPDs. (<b>b</b>) Measured and simulated S-parameters, (<b>c</b>) magnitude differences of S-parameters, and (<b>d</b>) phase responses.</p>
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<p>(<b>a</b>) Photograph of the meandered transmission lines based on two three-way WPDs. (<b>b</b>) Measured and simulated S-parameters, (<b>c</b>) magnitude differences of S-parameters, and (<b>d</b>) phase responses.</p>
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<p>Meandered-transmission-line-based multilayer WPDs having a common ground plane: (<b>a</b>) front view, (<b>b</b>) back view. (<b>c</b>) Measured and simulated results. (<b>d</b>) Magnitude differences of S-parameters, and (<b>e</b>) phase responses.</p>
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<p>Meandered-transmission-line-based multilayer WPDs having a common ground plane: (<b>a</b>) front view, (<b>b</b>) back view. (<b>c</b>) Measured and simulated results. (<b>d</b>) Magnitude differences of S-parameters, and (<b>e</b>) phase responses.</p>
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<p>Meandered-transmission-line-based multilayer 5-way WPD: (<b>a</b>) front view and (<b>b</b>) back view. (<b>c</b>) Measured and simulated return and insertion losses and (<b>d</b>) isolation levels. (<b>e</b>) Magnitude differences of S-parameters and (<b>f</b>) phase responses.</p>
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<p>Meandered-transmission-line-based multilayer 5-way WPD: (<b>a</b>) front view and (<b>b</b>) back view. (<b>c</b>) Measured and simulated return and insertion losses and (<b>d</b>) isolation levels. (<b>e</b>) Magnitude differences of S-parameters and (<b>f</b>) phase responses.</p>
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14 pages, 3994 KiB  
Article
Discrete Wavelet Transform—Based Metal Material Analysis Model by Constant Phase Angle Pulse Eddy Current Method
by Yong Xie, Yating Yu and Liangting Li
Appl. Sci. 2023, 13(5), 3207; https://doi.org/10.3390/app13053207 - 2 Mar 2023
Cited by 1 | Viewed by 1406
Abstract
Traditional eddy current technology identifies metal information with information of single frequency of limited frequency spectrum. To solve existing problems, this paper proposes a discrete wavelet transform-based metal material analysis model by using a constant phase angle pulse eddy current (CPA-PEC) sensor which [...] Read more.
Traditional eddy current technology identifies metal information with information of single frequency of limited frequency spectrum. To solve existing problems, this paper proposes a discrete wavelet transform-based metal material analysis model by using a constant phase angle pulse eddy current (CPA-PEC) sensor which collects and depicts metal feature information from multiple dimensions; then, the quantification calculation model of metal material by CPA-PEC feature is presented; finally, an experimental platform is built to collect the CPA-PEC features of various metal samples and verify recognition accuracy of the proposed metal material analysis model. In the investigation, 1000 eddy current signals from four standard metals (Cu, Fe, Al, St) and three types of metallic irons (Fe-K162, Fe-K163, Fe-K240) are measured and the features are identified by discrete wavelet transform. The feature correlation and significance are determined by regression analysis. Finally, the calculation model of feature evaluation index is present. The experimental analysis indicates that the stability of the quantitative evaluation index of eddy current features reaches 97.1%, the comprehensive accuracy error is less than 0.32% and the average measurement speed is about 50 ms for 1000 random sampling tests on standard metals. Full article
(This article belongs to the Special Issue Trends and Prospects in Applied Electromagnetics)
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<p>The structure of CPA-PEC sensor.</p>
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<p>Photograph of the experimental setup.</p>
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<p>Identification method and steps of the eddy current method metal material analysis model.</p>
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<p>Comparison of the signals before and after wavelet transformed.</p>
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<p>Signal characteristic distribution of Fe-K162, Fe-K163 and Fe-K240.</p>
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<p>Signal characteristic distribution of air, Cu, Fe, Al and St.</p>
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<p>IBM Statistical Product Service Solutions Software statistics binary logistic regression analysis results.</p>
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